CN113424426B - Bidirectional resonant circuit and automobile - Google Patents

Bidirectional resonant circuit and automobile Download PDF

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Publication number
CN113424426B
CN113424426B CN202080011980.9A CN202080011980A CN113424426B CN 113424426 B CN113424426 B CN 113424426B CN 202080011980 A CN202080011980 A CN 202080011980A CN 113424426 B CN113424426 B CN 113424426B
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controllable switch
switch tube
bridge circuit
conducted
controllable
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CN202080011980.9A
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CN113424426A (en
Inventor
陈晓斌
张辉
宋安国
吴壬华
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Shenzhen Shinry Technologies Co Ltd
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Shenzhen Shinry Technologies Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

A bidirectional resonant circuit and an automobile comprise a first bridge circuit, a transformer, a resonant circuit and a second bridge circuit; the first bridge circuit is connected with a secondary winding of the transformer, one end of the resonant circuit is connected with a primary winding of the transformer, and the other end of the resonant circuit is connected with the second bridge circuit; under the condition that the bidirectional resonant circuit is in a reverse working state, in a set period, the controllable switch tube of the first bridge circuit is conducted at a fixed duty ratio, and the controllable switch tube of the second bridge circuit is conducted at an adjustable duty ratio. Under the condition that elements are not added, on the basis of controlling the conduction of the first bridge circuit in a reverse working state, the controllable switch tube of the second bridge circuit connected with the high-voltage battery is controlled to be conducted so as to increase the voltage range in the reverse working process. The number of elements of the product is reduced, so that the volume of the product is reduced, correspondingly, the cost is reduced, and the self loss of the circuit is also reduced.

Description

Bidirectional resonance circuit and automobile
Technical Field
The application relates to the technical field of electricity, especially, relate to a two-way resonant circuit and car.
Background
With the development of new energy vehicles, the development of power supply systems thereof is becoming more mature, wherein the application of direct current-direct current (DC-DC) converters is also common. With the increase of the functional requirements of the vehicle-mounted power supply, the bidirectional DC-DC converter is applied. When the bidirectional DC-DC converter works in the forward direction, the bidirectional DC-DC converter can convert the electricity of the high-voltage battery into low-voltage direct current and charge the low-voltage battery with the high-voltage direct current; when the bidirectional DC-DC converter works reversely, the electricity of the low-voltage battery can be converted into high-voltage direct current, and the high-voltage battery is charged by the low-voltage direct current.
In the actual use of the bidirectional DC-DC converter, sometimes the required voltage range for reverse operation is high, and in order to achieve this, an inductor and a capacitor are generally connected in series in the secondary side circuit, or a capacitor is connected in series in the secondary side circuit. The two schemes can improve the voltage range of reverse operation, but the secondary side circuit is added with components, so that the number and the volume of the components of the product are increased, and the cost is increased; on the other hand, when the circuit works reversely, the current of the secondary side circuit is large, and the current loss can be greatly increased by adding components.
Disclosure of Invention
An object of the application is to provide a bidirectional resonant circuit and car to solve above-mentioned problem, not on the basis that secondary side increases components and parts, improve reverse working's voltage range.
A first aspect of the present application provides a bidirectional resonant circuit, including a first bridge circuit, a transformer, a resonant circuit, and a second bridge circuit; the first bridge circuit is connected with the secondary winding of the transformer, one end of the resonant circuit is connected with the primary winding of the transformer, and the other end of the resonant circuit is connected with the second bridge circuit; under the condition that the bidirectional resonant circuit is in a reverse working state, in a set period, the controllable switch tube of the first bridge circuit is conducted at a fixed duty ratio, and the controllable switch tube of the second bridge circuit is conducted at an adjustable duty ratio; the first bridge circuit is used for inverting the low-voltage direct current into alternating current and transmitting the alternating current to the transformer; the transformer is used for transmitting alternating current to the resonant circuit in the form of an alternating magnetic field; the resonant circuit is used for resonating the alternating current and transmitting the resonated alternating current to the second bridge circuit; the second bridge circuit is used for rectifying alternating current into high-voltage direct current.
The bidirectional resonant circuit as described above, wherein the fixed duty cycle is 0.5, and the adjustable duty cycle range is: the adjustable duty ratio is more than 0 and less than or equal to 0.5.
A bidirectional resonant circuit as described above, wherein either or both of the controllable switching segments of the second bridge circuit are turned on with an adjustable duty cycle.
The bidirectional resonant circuit as described above, wherein the first bridge circuit comprises a half-bridge circuit, the half-bridge circuit comprising a first controllable switch and a second controllable switch; the first controllable switch tube and the second controllable switch tube are conducted complementarily at the fixed duty ratio;
the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located in the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located in the same half bridge; in the conduction period of the first controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; in the conduction period of the second controllable switch tube, the third controllable switch tube and the fifth controllable switch tube are conducted synchronously after a set time period is delayed; and the fourth controllable switch tube and the sixth controllable switch tube are not conducted.
The bidirectional resonant circuit as described above, wherein the first bridge circuit comprises a half-bridge circuit, the half-bridge circuit comprising a first controllable switch and a second controllable switch; the first controllable switch tube and the second controllable switch tube are conducted complementarily at the fixed duty ratio; the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located at the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located at the same half bridge; in the conduction period of the first controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; and in the conduction period of the second controllable switch tube, the fourth controllable switch tube and the sixth controllable switch tube are conducted synchronously after a set time period is delayed.
The bidirectional resonant circuit as described above, wherein the first bridge circuit includes a second full bridge circuit, and the second full bridge circuit includes a seventh controllable switch tube, an eighth controllable switch tube, a ninth controllable switch tube and a tenth controllable switch tube; the seventh controllable switch tube and the eighth controllable switch tube are located in the same half bridge, and the ninth controllable switch tube and the tenth controllable switch tube are located in the same half bridge; the seventh controllable switch tube and the eighth controllable switch tube are complementarily switched on at a fixed duty ratio, and the ninth controllable switch tube and the tenth controllable switch tube are complementarily switched on at a fixed duty ratio; the seventh controllable switch tube and the tenth controllable switch tube are synchronously conducted, and the eighth controllable switch tube and the ninth controllable switch tube are synchronously conducted; the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located in the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located in the same half bridge; in the conduction period of the seventh controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; in the conduction period of the eighth controllable switch tube, the third controllable switch tube and the fifth controllable switch tube are conducted synchronously after a set time period is delayed; the fourth controllable switch tube and the sixth controllable switch tube are not conducted.
The bidirectional resonant circuit as described above, wherein the first bridge circuit includes a second full bridge circuit, and the second full bridge circuit includes a seventh controllable switch tube, an eighth controllable switch tube, a ninth controllable switch tube and a tenth controllable switch tube; the seventh controllable switching tube and the eighth controllable switching tube are located at the same half bridge, and the ninth controllable switching tube and the tenth controllable switching tube are located at the same half bridge; the seventh controllable switch tube and the eighth controllable switch tube are complementarily conducted at a fixed duty ratio, and the ninth controllable switch tube and the tenth controllable switch tube are complementarily conducted at a fixed duty ratio; the seventh controllable switch tube and the tenth controllable switch tube are synchronously conducted, and the eighth controllable switch tube and the ninth controllable switch tube are synchronously conducted; the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located in the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located in the same half bridge; in the conduction period of the seventh controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; and in the conduction period of the eighth controllable switching tube, the fourth controllable switching tube and the sixth controllable switching tube are conducted synchronously after a set time period is delayed.
The bidirectional resonant circuit as described above, wherein the resonant circuit includes an inductor and a capacitor, a first end of the capacitor is connected to a first end of the primary winding of the transformer, and a second end of the capacitor is connected to the first connection node; the first connection node is positioned between the third controllable switch tube and the fourth controllable switch tube; the first end of the inductor is connected with the second end of the primary winding of the transformer, and the second end of the inductor is connected with the second connection node; the second connection node is located between the fifth controllable switch tube and the sixth controllable switch tube.
The bidirectional resonant circuit as described above, wherein when the bidirectional resonant circuit is in a forward operating state, the controllable switch of the second bridge circuit is turned on at the fixed duty cycle and the controllable switch of the first bridge circuit is turned off within a set period; the second bridge circuit is used for inverting the high-voltage direct current into alternating current and transmitting the alternating current to the resonance circuit; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the transformer; the transformer is used for transmitting alternating current to the first bridge circuit in the form of an alternating magnetic field; the first bridge circuit is used for rectifying alternating current into low-voltage direct current.
A second aspect of the present application provides an automobile comprising an on-board power supply system, the on-board power supply system comprising the bidirectional resonant circuit of any one of the first aspects of the present application.
The application provides a two-way resonance circuit, under the condition that does not increase the component, under reverse operating condition, on the basis that the first bridge circuit of control switched on, the controllable switch pipe of the second bridge circuit through control connection high voltage battery switches on to increase the voltage range of reverse during operation. The number of elements of the product is reduced, so that the volume of the product is reduced, correspondingly, the cost is reduced, and the self loss of the circuit is also reduced.
Drawings
In order to more clearly illustrate the technical solution in the embodiments of the present invention, the drawings required to be used in the embodiments will be briefly described below.
In order to more clearly illustrate the technical solutions of the present application, the drawings required to be used in the embodiments will be briefly described below, and obviously, the drawings in the following description are only some embodiments of the present application, and other drawings can be obtained by those skilled in the art without creative efforts.
Fig. 1 is a circuit diagram of a bidirectional resonant circuit provided in an embodiment of the present application;
FIG. 2 is a schematic diagram of a periodic signal of a bidirectional resonant circuit in a forward operation according to an embodiment of the present application;
fig. 3 is a schematic diagram of a periodic signal when a bidirectional resonant circuit provided in an embodiment of the present application operates in reverse;
fig. 4 is a schematic diagram of another periodic signal when the bidirectional resonant circuit provided in the embodiment of the present application operates in reverse direction;
fig. 5 is a circuit diagram of another bidirectional resonant circuit provided in an embodiment of the present application;
FIG. 6 is a schematic diagram of a periodic signal of a forward operation of another bidirectional resonant circuit provided in an embodiment of the present application;
fig. 7 is a schematic diagram of a periodic signal when another bidirectional resonant circuit provided in the embodiment of the present application operates in reverse;
fig. 8 is a schematic diagram of another periodic signal when another bidirectional resonant circuit provided in this application operates in reverse.
Detailed Description
The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
The bidirectional resonant circuit provided by the embodiment of the application comprises a first bridge circuit, a transformer, a resonant circuit and a second bridge circuit; the first bridge circuit is connected with a secondary winding of the transformer, one end of the resonant circuit is connected with a primary winding of the transformer, and the other end of the resonant circuit is connected with the second bridge circuit.
Under the condition that the bidirectional resonant circuit is in a reverse working state, in a set period, the controllable switch tube of the first bridge circuit is conducted at a fixed duty ratio, and the controllable switch tube of the second bridge circuit is conducted at an adjustable duty ratio.
The first bridge circuit is used for inverting the low-voltage direct current into alternating current and transmitting the alternating current to the transformer; the transformer is used for transmitting alternating current to the resonant circuit in the form of an alternating magnetic field; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the second bridge circuit; the second bridge circuit is used for rectifying alternating current into high-voltage direct current.
The controllable switch referred to in this application may be a metal-oxide-semiconductor (MOS) field effect transistor.
In the bidirectional resonant circuit in this embodiment, the first bridge circuit is connected to a low-voltage dc power supply, and the second bridge circuit is connected to a high-voltage dc power supply or a device requiring high-voltage power supply. For convenience of illustration, the second bridge circuit is connected to the high voltage dc power supply. The low-voltage dc power supply illustrated in fig. 1 is a rechargeable low-voltage battery, and the high-voltage dc power supply illustrated in fig. 1 is a rechargeable high-voltage battery.
In this embodiment, under the condition that no component is added, on the basis that the first bridge circuit is controlled to be turned on in the reverse operation state, the controllable switch tube of the second bridge circuit connected with the high-voltage battery is controlled to be turned on, and under the condition that the controllable switch tube of the second bridge circuit is turned on, the second bridge circuit forms a short circuit loop, at this time, the second bridge circuit has a large current, and under the condition that the controllable switch tube of the second bridge circuit is switched to be in the non-conduction state, the large current can be provided for equipment requiring high-voltage power supply, so that the voltage range in the reverse operation is increased. The number of elements of the product is reduced, so that the volume of the product is reduced, correspondingly, the cost is reduced, and the self loss of the circuit is also reduced.
Further, the fixed duty cycle in this embodiment may be 0.5, and the adjustable duty cycle range is: the adjustable duty ratio is more than 0 and less than or equal to 0.5. The adjustable duty ratio is set to be between 0 and 0.5, various different reverse working voltage ranges can be realized, and the larger the adjustable duty ratio is, the wider the reverse working voltage range is, and the applicability of the reverse working voltage range is stronger.
It will be appreciated that the resonant circuit described above comprises an inductance and a capacitance, the set period of the bidirectional resonant circuit being determined in dependence on the inductance and capacitance. Specifically, the set period of the bidirectional resonant circuit is calculated according to the following formula:
Figure BDA0003189210290000071
wherein Ts is a set period, L1 is an inductance of the inductor, and C1 is a capacitance of the capacitor.
The structure of the bidirectional resonant circuit in this embodiment is explained below, and in this embodiment, the structure of the bidirectional resonant circuit has two specific implementations, one of which is that the first bridge circuit is a half-bridge circuit (as shown in fig. 1), and the second bridge circuit is a full-bridge circuit; in another embodiment, the first bridge circuit and the second bridge circuit are full-bridge circuits (as shown in fig. 5), and the following details are provided:
first embodiment
Referring to fig. 1, in the embodiment, the bidirectional resonant circuit includes a low-voltage battery, a first bridge circuit, a transformer T, a resonant circuit, a second bridge circuit, and a high-voltage battery. The first bridge circuit is a half-bridge circuit, and the second bridge circuit is a first full-bridge circuit.
Specifically, the half-bridge circuit includes a first controllable switch transistor S1 and a second controllable switch transistor S2. The transformer T includes a primary winding and a secondary winding. The resonant circuit comprises a capacitor C and an inductor L. The first full-bridge circuit comprises a third controllable switch tube S3, a fourth controllable switch tube S4, a fifth controllable switch tube S5 and a sixth controllable switch tube S6; the third controllable switch tube S3 and the fourth controllable switch tube S4 are located in the same half bridge, and the fifth controllable switch tube S5 and the sixth controllable switch tube S6 are located in the same half bridge.
One end of the first controllable switching tube S1 is connected with the negative electrode of the low-voltage battery, and the other end of the first controllable switching tube S1 is connected with one end of the primary winding; the other end of the primary winding is connected with one end of a second controllable switching tube S2, and the other end of the second controllable switching tube S2 is connected with the negative electrode of the low-voltage battery; the middle part of the primary winding is connected with the positive pole of the low-voltage battery.
One end of the capacitor C is connected to one end of the primary winding, and the other end of the primary winding is connected to one end of the inductor L. The other end of the capacitor C is connected with the first connection node, and the other end of the inductor L is connected with the second connection node. The first connection node is arranged between the third controllable switch tube S3 and the fourth controllable switch tube S4, and the second connection node is arranged between the fifth controllable switch tube S5 and the sixth controllable switch tube S6. The third controllable switch tube S3 and the fourth controllable switch tube S4 form a half bridge, in which the third controllable switch tube S3 is connected to the positive pole of the high voltage battery, and the fourth controllable switch tube S4 is connected to the negative pole of the high voltage battery. The fifth controllable switch transistor S5 and the sixth controllable switch transistor S6 form a half bridge, in which the fifth controllable switch transistor S5 is connected to the positive pole of the high-voltage battery and the sixth controllable switch transistor S6 is connected to the negative pole of the high-voltage battery.
The following describes a bidirectional resonant circuit according to a first embodiment, a control method in forward operation:
when the circuit works in the forward direction, the second bridge circuit is used for inverting the high-voltage direct current provided by the high-voltage battery into alternating current and transmitting the alternating current to the resonance circuit; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the transformer T; the transformer T is used for transmitting alternating current to the first bridge circuit in the form of an alternating magnetic field; the first bridge circuit is used for rectifying alternating current into low-voltage direct current.
Under the condition of forward working, the controllable switch tube of the first bridge circuit is not conducted, and the controllable switch tube of the second bridge circuit is conducted according to a fixed duty ratio. Referring to fig. 2, in the first bridge circuit, the first controllable switch S1 and the second controllable switch S2 are not conducted. The third controllable switch tube S3 and the fourth controllable switch tube S4 are complementarily conducted with a duty ratio of 0.5, and the fifth controllable switch tube S5 and the sixth controllable switch tube S6 are complementarily conducted with a duty ratio of 0.5; the third controllable switch tube S3 and the sixth controllable switch tube S6 are turned on synchronously, and the fourth controllable switch tube S4 and the fifth controllable switch tube S5 are turned on synchronously.
By adopting the control method, the high-voltage direct current of the high-voltage battery can be converted into the low-voltage direct current to be supplied to the low-voltage battery, so that the effect of charging the low-voltage battery is achieved, the low-voltage battery can provide the low-voltage direct current for other equipment, and the normal work of the other equipment is ensured.
Besides the forward operation, the bidirectional resonant circuit can also operate in reverse direction, and the following explains the working flow of the reverse operation: the first bridge circuit is used for inverting the low-voltage direct current into alternating current and transmitting the alternating current to the transformer T; the transformer T is used for transmitting alternating current to the resonant circuit in the form of an alternating magnetic field; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the second bridge circuit; the second bridge circuit is used for rectifying alternating current into high-voltage direct current.
Two control methods in reverse operation are described below:
the first method comprises the following steps:
and in a set period Ts, the controllable switch tube of the first bridge circuit is conducted at a fixed duty ratio of 0.5, and the controllable switch tube of the second bridge circuit is conducted at an adjustable duty ratio.
Referring to fig. 3, in the first bridge circuit, the first controllable switch S1 and the second controllable switch S2 are turned on complementarily according to a fixed duty ratio of 0.5. That is, in a set period TS, the first controllable switch tube S1 is firstly switched on, the first set period T1 is Ts/2, and the rest Ts/2 is cut off; the second controllable switch S2 turns off Ts/2 first, and then turns on for a first setting period T1.
In the second bridge circuit, under the condition that the first controllable switching tube S1 is in a conduction period T1 in a set period Ts, the third controllable switching tube S3 and the fifth controllable switching tube S5 are conducted synchronously after a set time period T3 is delayed; under the condition that the second controllable switch tube S2 is in a conduction period T1, the third controllable switch tube S3 and the fifth controllable switch tube S5 are conducted synchronously after a set time period T3 is delayed; the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are not conducted. Synchronous conduction refers to that: the time point of starting conduction, the duration of conduction and the time point of finishing conduction are the same.
Specifically, referring to fig. 3, during a set period: after the first controllable switching tube S1 is firstly conducted for Ts/2 duration, the rest Ts/2 duration is cut off; the second controllable switch tube S2 is firstly turned off for Ts/2 time, and then the rest Ts/2 time is turned on. In a conduction period T1 of the first controllable switch tube S1, after the first controllable switch tube S1 starts to be conducted, the third controllable switch tube S3 and the fifth controllable switch tube S5 are conducted after the time length of T3 is delayed; after the third controllable switch tube S3 and the fifth controllable switch tube S5 are turned on for the second setting period T2, the period T3 is cut off. In the on-period T1 of the second controllable switch tube S2, after the second controllable switch tube S2 starts to be turned on, the third controllable switch tube S3 and the fifth controllable switch tube S5 start to be turned on after the duration of T3 is delayed, and after the third controllable switch tube S3 and the fifth controllable switch tube S5 are turned on for the second set period T2, the duration of T3 is cut off. In the whole process, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are not conducted.
Wherein 2 T3 T2 +Ts/2; t3= (0.5-D) × Ts/2, T2= D × Ts. Wherein D is the duty cycle of the third controllable switching tube S3 and the fifth controllable switching tube S5, and the range of the duty cycle is: d is more than 0 and less than or equal to 0.5. T3 is the conduction delay time of the third controllable switch tube S3 and the fifth controllable switch tube S5, and T2 is the conduction time of the third controllable switch tube S3 and the fifth controllable switch tube S5.
That is, the third controllable switch tube S3 and the fifth controllable switch tube S5 start to be turned on again after the time length T3 that the first controllable switch tube S1 starts to be turned on is delayed, and start to be turned on again after the time length T3 that the second controllable switch tube S2 starts to be turned on is delayed.
By adopting the first control method, aiming at the condition that the first bridge circuit is a half-bridge circuit, no element is added, and the voltage range in reverse operation is increased by controlling the conduction of the third controllable switch tube S3 and the fifth controllable switch tube S5, so that a wider voltage range is provided for the high-voltage battery. In addition, if any one of the third controllable switch tube S3 or the fifth controllable switch tube S5 fails, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 may be controlled to conduct according to the conducting modes of the third controllable switch tube S3 and the fifth controllable switch tube S5, respectively, so as to ensure that the circuit can continue to be used normally. Especially when the circuit is applied to equipment such as automobiles, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are used as standby controllable switch tubes, so that danger can be avoided.
And the second method comprises the following steps:
referring to fig. 4, specifically, in the first bridge circuit, the first controllable switch S1 and the second controllable switch S2 are complementarily turned on according to a duty ratio of 0.5. That is, in a set period TS, the first controllable switch tube S1 is firstly switched on, the first set period T1 is Ts/2, and the rest Ts/2 is cut off; the second controllable switch S2 is turned off Ts/2 first, and then turned on for a first set period T1.
In the second bridge circuit, in the on period T1 of the first controllable switch tube S1, the third controllable switch tube S3 and the fifth controllable switch tube S5 start to be turned on after a set time period T3; in the conduction period of the second controllable switch tube S2, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are conducted synchronously after a set time period T3.
Specifically, referring to fig. 4, in one setting period: after the first controllable switching tube S1 is firstly conducted for Ts/2 duration, the rest Ts/2 duration is cut off; after the second controllable switch tube S2 is cut off for Ts/2 time, the rest Ts/2 time is conducted. In a conducting period T1 of the first controllable switch tube S1, after the first controllable switch tube S1 starts to be conducted, the third controllable switch tube S3 and the fifth controllable switch tube S5 start to be conducted after the time length of T3 is delayed; after the third controllable switch tube S3 and the fifth controllable switch tube S5 are turned on for the second setting period T2, the period T3 is cut off. In the on period T1 of the second controllable switch tube S2, after the second controllable switch tube S2 starts to be turned on, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 start to be turned on after a time period of T3 is delayed, and after the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are turned on in the second setting period T2, the time period of T3 is cut off.
Wherein 2 t3+ t2= ts/2; t3= (0.5-D) × Ts/2, T2= D =. Wherein D is the duty cycle of the third controllable switching tube S3 and the fifth controllable switching tube S5, and the range of the duty cycle is: d is more than 0 and less than or equal to 0.5. T3 is the conduction delay time of the third controllable switch tube S3 and the fifth controllable switch tube S5, and T2 is the conduction time of the third controllable switch tube S3 and the fifth controllable switch tube S5. In addition, D is also the duty cycle of the fourth controllable switching tube S4 and the sixth controllable switching tube S6, and the duty cycle ranges from: d is more than 0 and less than or equal to 0.5; t3 is also the conduction delay time of the fourth controllable switch tube S4 and the sixth controllable switch tube S6, and T2 is also the conduction time of the fourth controllable switch tube S4 and the sixth controllable switch tube S6.
That is, the third controllable switch tube S3 and the fifth controllable switch tube S5 need to be turned on again after the time length T3 elapses from the turning on of the first controllable switch tube S1. The fourth controllable switch tube S4 and the sixth controllable switch tube S6 need to be turned on at the second controllable switch tube S2 to start to delay for a time period of T3, and then turn on again.
By adopting the second control method, elements are not added, and the voltage range in reverse operation can be increased by controlling the conduction of the third controllable switch tube S3, the fourth controllable switch tube S4, the fifth controllable switch tube S5 and the sixth controllable switch tube S6, so that a wider voltage range is provided for the high-voltage battery. In addition, in the second control method, the third to sixth controllable switching tubes S6 are all turned on, so that the service conditions of the four controllable switching tubes are relatively balanced, and the service lives of the four controllable switching tubes are relatively close to each other, thereby preventing part of the controllable switching tubes from being turned on and part of the controllable switching tubes from being turned off, which causes unequal service lives and affects the overall service life of the circuit.
Second embodiment
Referring to fig. 5, in this embodiment, the bidirectional resonant circuit includes a low-voltage battery, a first bridge circuit, a transformer T, a resonant circuit, a second bridge circuit, and a high-voltage battery. The first bridge circuit is a second full bridge circuit, and the second bridge circuit is a first full bridge circuit. The second bridge circuit in fig. 5 is the same as that in the first embodiment, except for the first bridge circuit.
Specifically, the second full-bridge circuit includes a seventh controllable switch transistor S7, an eighth controllable switch transistor S8, a ninth controllable switch transistor S9 and a tenth controllable switch transistor S10. The transformer T includes a primary winding and a secondary winding. The resonant circuit comprises a capacitor C and an inductor L. The first full-bridge circuit comprises a third controllable switch tube S3, a fourth controllable switch tube S4, a fifth controllable switch tube S5 and a sixth controllable switch tube S6; the seventh controllable switch tube S7 and the eighth controllable switch tube S8 are located in the same half bridge, in which the seventh controllable switch tube S7 is connected to the positive electrode of the low-voltage battery, and the eighth controllable switch tube S8 is connected to the negative electrode of the low-voltage battery. The ninth controllable switch tube S9 and the tenth controllable switch tube S10 are located in the same half bridge, in which the ninth controllable switch tube S9 is connected to the positive electrode of the low-voltage battery, and the tenth controllable switch tube S10 is connected to the negative electrode of the low-voltage battery. One end of the primary winding is connected with the third connecting node, and the other end of the primary winding is connected with the fourth connecting node; the third connection node is located between the seventh controllable switch tube S7 and the eighth controllable switch tube S8, and the fourth connection node is located between the ninth controllable switch tube S9 and the tenth controllable switch tube S10.
The resonant circuit comprises a capacitor C and an inductor L, one end of the capacitor C is connected with one end of the primary winding, and the other end of the primary winding is connected with one end of the inductor L. The other end of the capacitor C is connected with the first connection node, and the other end of the inductor L is connected with the second connection node. The first connection node is arranged between the third controllable switch tube S3 and the fourth controllable switch tube S4, and the second connection node is arranged between the fifth controllable switch tube S5 and the sixth controllable switch tube S6. The third controllable switch transistor S3 and the fourth controllable switch transistor S4 form a half bridge, in which the third controllable switch transistor S3 is connected to the positive pole of the high-voltage battery and the fourth controllable switch transistor S4 is connected to the negative pole of the high-voltage battery. The fifth controllable switch transistor S5 and the sixth controllable switch transistor S6 form a half bridge, in which the fifth controllable switch transistor S5 is connected to the positive pole of the high-voltage battery and the sixth controllable switch transistor S6 is connected to the negative pole of the high-voltage battery.
The following describes a bidirectional resonant circuit according to a first embodiment, a control method in forward operation:
when the circuit works in the forward direction, the second bridge circuit is used for inverting the high-voltage direct current provided by the high-voltage battery into alternating current and transmitting the alternating current to the resonance circuit; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the transformer T; the transformer T is used for transmitting alternating current to the first bridge circuit in the form of an alternating magnetic field; the first bridge circuit is used for rectifying alternating current into low-voltage direct current.
Under the condition of forward operation, in a set period Ts, the controllable switch tube of the first bridge circuit is not conducted, and the controllable switch tube of the second bridge circuit is conducted according to a fixed duty ratio. Referring to fig. 6, in the first bridge circuit, the seventh to tenth controllable switches S7 to S10 are not turned on. The third controllable switch tube S3 and the fourth controllable switch tube S4 are complementarily turned on at a duty ratio of 0.5, and the fifth controllable switch tube S5 and the sixth controllable switch tube S6 are complementarily turned on at a duty ratio of 0.5; the third controllable switch tube S3 and the sixth controllable switch tube S6 are synchronously conducted, and the fourth controllable switch tube S4 and the fifth controllable switch tube S5 are synchronously conducted.
By adopting the control method, the high-voltage direct current of the high-voltage battery can be converted into the low-voltage direct current to be supplied to the low-voltage battery, so that the effect of charging the low-voltage battery is achieved, the low-voltage battery can provide the low-voltage direct current for other equipment, and the normal work of the other equipment is ensured.
Besides the forward operation, the bidirectional resonant circuit can also operate in reverse direction, and the following explains the working flow of the reverse operation: the first bridge circuit is used for inverting the low-voltage direct current into alternating current and transmitting the alternating current to the transformer T; the transformer T is used for transmitting alternating current to the resonant circuit in the form of an alternating magnetic field; the resonant circuit is used for resonating the alternating current and transmitting the resonated alternating current to the second bridge circuit; the second bridge circuit is used for rectifying alternating current into high-voltage direct current.
Two control methods in reverse operation are described below:
the first method comprises the following steps:
and in a set period Ts, the controllable switch tube of the first bridge circuit is conducted at a fixed duty ratio of 0.5, and the controllable switch tube of the second bridge circuit is conducted at an adjustable duty ratio.
Referring to fig. 7, specifically, in the first bridge circuit, the seventh controllable switch S7 and the eighth controllable switch are complementarily turned on according to a fixed duty ratio of 0.5; the ninth controllable switch tube S9 and the tenth controllable switch tube S10 are complementarily turned on according to the fixed duty ratio of 0.5. The seventh controllable switch tube S7 and the tenth controllable switch tube S10 are turned on synchronously, and the eighth controllable switch tube S8 and the ninth controllable switch tube S9 are turned on synchronously.
In the following description, the controllable switching tube in the second bridge circuit is described with reference to the seventh controllable switching tube S7 and the eighth controllable switching tube.
In a set period, under the condition that the seventh controllable switch tube is in a conduction period, in the second bridge circuit, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; in the conduction period of the eighth controllable switch tube, the third controllable switch tube and the fifth controllable switch tube are conducted synchronously after a set time period is delayed; the fourth controllable switch tube and the sixth controllable switch tube are not conducted.
Specifically, referring to fig. 7, in one setting period: after the pilot switch of the seventh controllable switching tube S7 is turned on for Ts/2, the rest Ts/2 is cut off; after the eighth controllable switch tube is firstly cut off for Ts/2 time, the rest Ts/2 time is conducted. In the conduction period of the seventh controllable switch tube S7, after the seventh controllable switch tube S7 starts to conduct, the third controllable switch tube S3 and the fifth controllable switch tube S5 start to conduct after a delay of T3; after the third controllable switch tube S3 and the fifth controllable switch tube S5 are turned on for the second setting period T2, the period T3 is cut off. In the conduction period of the eighth controllable switch tube, after the eighth controllable switch tube starts to be conducted, the time length of the third controllable switch tube S3 and the time length of the fifth controllable switch tube S5 delay T3 to start to be conducted, and after the third controllable switch tube S3 and the fifth controllable switch tube S5 are conducted for the second set period T2, the time length of the T3 is cut off. In the whole process, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are not conducted.
Wherein 2 T3 T2 +Ts/2; t3= (0.5-D) × Ts/2, T2= D × Ts. Wherein D is the duty cycle of the third controllable switching tube S3 and the fifth controllable switching tube S5, and the range of the duty cycle is: d is more than 0 and less than or equal to 0.5. T3 is the conduction delay time of the third controllable switch tube S3 and the fifth controllable switch tube S5, and T2 is the conduction time of the third controllable switch tube S3 and the fifth controllable switch tube S5.
That is, in a set period, the third controllable switch S3 and the fifth controllable switch S5 are turned on twice, the turn-on of the seventh controllable switch S7 is turned on once after a delay of time duration T3, and the turn-on of the eighth controllable switch is turned on once after a delay of time duration T3.
By adopting the first control method, aiming at the condition that the first bridge circuit is a full bridge circuit, no element is added, and the voltage range in reverse operation is increased by controlling the conduction of the third controllable switch tube S3 and the fifth controllable switch tube S5, so that a wider voltage range is provided for the high-voltage battery. And in case of failure of the third controllable switch S3 or the fifth controllable switch S5, the fourth controllable switch S4 and the sixth controllable switch S6 may be used. Thereby avoiding the trouble in the circuit use, causing danger.
And the second method comprises the following steps:
referring to fig. 8, in the first bridge circuit, specifically, the seventh controllable switch S7 and the eighth controllable switch are complementarily turned on according to a duty ratio of 0.5; the ninth controllable switch tube and the tenth controllable switch tube are conducted complementarily according to the duty ratio of 0.5. The seventh controllable switch tube S7 and the tenth controllable switch tube are turned on synchronously, and the eighth controllable switch tube S8 and the ninth controllable switch tube are turned on synchronously.
In the following description of the controllable switching devices in the second bridge circuit, the seventh controllable switching device S7 and the eighth controllable switching device S8 will be referred to as reference.
In the second bridge circuit, in the conduction period of the seventh controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; and in the conduction period of the eighth controllable switch tube, the fourth controllable switch tube and the sixth controllable switch tube are synchronously conducted after a set time period is delayed.
Specifically, referring to fig. 8, in one setting period: after the pilot switch of the seventh controllable switching tube S7 is turned on for Ts/2, the rest Ts/2 is cut off; after the eighth controllable switch tube is firstly cut off for Ts/2 time, the rest Ts/2 time is conducted. In the conduction period of the seventh controllable switch tube S7, after the seventh controllable switch tube S7 starts to conduct, the third controllable switch tube S3 and the fifth controllable switch tube S5 start to conduct after a time period of T3; and after the third controllable switch tube S3 and the fifth controllable switch tube S5 are conducted for the second set period T2, the time length of T3 is cut off. In the turn-on period of the eighth controllable switch tube S8, after the eighth controllable switch tube S8 starts to be turned on, the fourth controllable switch tube S4 and the sixth controllable switch tube S6 start to be turned on after a time period of T3 is delayed, and after the fourth controllable switch tube S4 and the sixth controllable switch tube S6 are turned on for a second setting period T2, the time period of T3 is cut off.
Wherein 2 T3 T2 +Ts/2; t3= (0.5-D) × Ts/2, T2= D × Ts. Wherein D is the duty cycle of the third controllable switching tube S3 and the fifth controllable switching tube S5, and the range of the duty cycle is: d is more than 0 and less than or equal to 0.5. T3 is the conduction delay time of the third controllable switch tube S3 and the fifth controllable switch tube S5, and T2 is the conduction time of the third controllable switch tube S3 and the fifth controllable switch tube S5. D is also the duty cycle of the fourth controllable switch tube S4 and the sixth controllable switch tube S6, and the range of the duty cycle is: d is more than 0 and less than or equal to 0.5; t3 is also the conduction delay time of the fourth controllable switch tube S4 and the sixth controllable switch tube S6, and T2 is also the conduction time of the fourth controllable switch tube S4 and the sixth controllable switch tube S6.
That is, within a set period: the third controllable switch tube S3 and the fifth controllable switch tube S5 are turned on once, and it is necessary to turn on the seventh controllable switch tube S7 and start to delay for a time period of T3, and then turn on again. The fourth controllable switch tube S4 and the sixth controllable switch tube S6 are turned on once, and the time length T3 needs to be delayed after the tenth controllable switch tube S10 is turned on, and then the turn-on is started again.
By adopting the second control method, elements are not added, and the voltage range in reverse operation can be increased by controlling the conduction of the third controllable switch tube S3, the fourth controllable switch tube S4, the fifth controllable switch tube S5 and the sixth controllable switch tube S6, so that a wider voltage range can be provided for the high-voltage battery. In addition, in the second control method, the third to sixth controllable switching tubes S6 are all turned on, so that the service conditions of the four controllable switching tubes are relatively balanced, and the service lives of the four controllable switching tubes are relatively close to each other, thereby preventing part of the controllable switching tubes from being turned on and part of the controllable switching tubes from being turned off, which causes unequal service lives and affects the overall service life of the circuit.
It can be seen from above that, this application embodiment provides bidirectional resonant circuit, and its first bridge circuit who connects the low-voltage battery no matter be half-bridge circuit or full-bridge circuit, all can switch on through the controllable switch tube of the second bridge circuit of control connection high-voltage battery under the prerequisite that does not increase all the other components to increase the voltage range of reverse during operation. The number of elements of the product is reduced, so that the volume of the product is reduced, correspondingly, the cost is reduced, and the self loss of the circuit is also reduced.
In addition, the controllable switch tubes of the second bridge circuit can be completely conducted or only partially conducted. Therefore, the application range is wide.
As can be seen from the two reverse operation control methods in the first and second embodiments, the controllable switch transistors of the second bridge circuit may be partially or fully turned on. When a control method of conducting part of the controllable switching tubes is adopted, the rest controllable switching tubes can be used as standby parts to avoid danger. The mode that all controllable switch tubes are conducted is adopted, so that the service lives of all controllable switch tubes are balanced, and the service life of a product is prolonged.
It is understood that, in the above embodiment, the resonant circuit includes an inductor L and a capacitor C, a first end of the capacitor C is connected to a first end of the primary winding of the transformer T, and a second end of the capacitor C is connected to the first connection node; the first connection node is located between the third controllable switch tube S3 and the fourth controllable switch tube S4. A first end of the inductor L is connected with a second end of the primary winding of the transformer T, and a second end of the inductor L is connected with a second connection node; the second connection node is located between the fifth controllable switch tube S5 and the sixth controllable switch tube S6. By adopting the resonant circuit, the number of components is small, the structure is simple, the cost is low, the cost of the whole product is reduced, and the loss of the circuit can be reduced.
Further, the embodiment of the application also provides an automobile which comprises a vehicle-mounted power supply system, wherein the vehicle-mounted power supply system comprises the bidirectional resonant circuit in any embodiment of the application.
The foregoing embodiments have been described in detail, and specific examples are used herein to explain the principles and implementations of the present application, where the above description of the embodiments is only intended to help understand the method and its core ideas of the present application; meanwhile, for a person skilled in the art, according to the idea of the present application, the specific implementation manner and the application scope may be changed, and in summary, the content of the present specification should not be construed as a limitation to the present application.

Claims (10)

1. A bidirectional resonant circuit is characterized by comprising a first bridge circuit, a transformer, a resonant circuit and a second bridge circuit; the first bridge circuit is connected with the secondary winding of the transformer, one end of the resonant circuit is connected with the primary winding of the transformer, and the other end of the resonant circuit is connected with the second bridge circuit;
under the condition that the bidirectional resonant circuit works in the forward direction, the controllable switch tube of the first bridge circuit is not conducted, and the controllable switch tube of the second bridge circuit is conducted according to a fixed duty ratio;
under the condition that the bidirectional resonant circuit is in a reverse working state, in a set period, the controllable switch tube of the first bridge circuit is conducted at a fixed duty ratio, and the controllable switch tube of the second bridge circuit is conducted at an adjustable duty ratio; the first bridge circuit comprises a half-bridge circuit, and the half-bridge circuit comprises a first controllable switch tube and a second controllable switch tube; the first controllable switch tube and the second controllable switch tube are conducted complementarily at the fixed duty ratio;
the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located at the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located at the same half bridge;
in the conduction period of the first controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; in the conduction period of the second controllable switch tube, the third controllable switch tube and the fifth controllable switch tube are conducted synchronously after a set time period is delayed;
the first bridge circuit is used for inverting the low-voltage direct current into alternating current and transmitting the alternating current to the transformer; the transformer is used for transmitting alternating current to the resonant circuit in the form of an alternating magnetic field; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the second bridge circuit; the second bridge circuit is used for rectifying alternating current into high-voltage direct current.
2. The bi-directional resonant circuit of claim 1, wherein the fixed duty cycle is 0.5 and the adjustable duty cycle range is: the adjustable duty ratio is more than 0 and less than or equal to 0.5.
3. The bidirectional resonant circuit of claim 1, wherein part or all of the controllable switching segments of the second bridge circuit are turned on at an adjustable duty cycle.
4. The bi-directional resonant circuit of claim 1, wherein the fourth controllable switch and the sixth controllable switch are non-conductive.
5. The bidirectional resonant circuit of claim 1, wherein the first bridge circuit comprises a half-bridge circuit including a first controllable switch and a second controllable switch; the first controllable switch tube and the second controllable switch tube are conducted complementarily at the fixed duty ratio;
the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located in the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located in the same half bridge;
in the conduction period of the first controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; and in the conduction period of the second controllable switch tube, the fourth controllable switch tube and the sixth controllable switch tube are synchronously conducted after a set time period is delayed.
6. The bidirectional resonant circuit of claim 1, wherein the first bridge circuit comprises a second bridge circuit, and the second bridge circuit comprises a seventh controllable switch, an eighth controllable switch, a ninth controllable switch, and a tenth controllable switch; the seventh controllable switch tube and the eighth controllable switch tube are located in the same half bridge, and the ninth controllable switch tube and the tenth controllable switch tube are located in the same half bridge; the seventh controllable switch tube and the eighth controllable switch tube are complementarily switched on at a fixed duty ratio, and the ninth controllable switch tube and the tenth controllable switch tube are complementarily switched on at a fixed duty ratio; the seventh controllable switch tube and the tenth controllable switch tube are synchronously conducted, and the eighth controllable switch tube and the ninth controllable switch tube are synchronously conducted;
the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located at the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located at the same half bridge;
in the conduction period of the seventh controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; in the conduction period of the eighth controllable switch tube, the third controllable switch tube and the fifth controllable switch tube are conducted synchronously after a set time period is delayed; the fourth controllable switch tube and the sixth controllable switch tube are not conducted.
7. The bidirectional resonant circuit of claim 1, wherein the first bridge circuit comprises a second bridge circuit, and the second bridge circuit comprises a seventh controllable switch, an eighth controllable switch, a ninth controllable switch, and a tenth controllable switch; the seventh controllable switch tube and the eighth controllable switch tube are located in the same half bridge, and the ninth controllable switch tube and the tenth controllable switch tube are located in the same half bridge; the seventh controllable switch tube and the eighth controllable switch tube are complementarily conducted at a fixed duty ratio, and the ninth controllable switch tube and the tenth controllable switch tube are complementarily conducted at a fixed duty ratio; the seventh controllable switch tube and the tenth controllable switch tube are synchronously conducted, and the eighth controllable switch tube and the ninth controllable switch tube are synchronously conducted;
the second bridge circuit comprises a first full bridge circuit, and the first full bridge circuit comprises a third controllable switch tube, a fourth controllable switch tube, a fifth controllable switch tube and a sixth controllable switch tube; the third controllable switch tube and the fourth controllable switch tube are located in the same half bridge, and the fifth controllable switch tube and the sixth controllable switch tube are located in the same half bridge;
in the conduction period of the seventh controllable switch tube, the third controllable switch tube and the fifth controllable switch tube start to conduct after a set time period; and in the conduction period of the eighth controllable switch tube, the fourth controllable switch tube and the sixth controllable switch tube are synchronously conducted after a set time period is delayed.
8. The bidirectional resonant circuit of any of claims 4 to 7, wherein the resonant circuit comprises an inductor and a capacitor, a first end of the capacitor being connected to a first end of the primary winding of the transformer, a second end of the capacitor being connected to a first connection node; the first connection node is positioned between the third controllable switch tube and the fourth controllable switch tube;
the first end of the inductor is connected with the second end of the primary winding of the transformer, and the second end of the inductor is connected with the second connection node; the second connection node is located between the fifth controllable switch tube and the sixth controllable switch tube.
9. The bidirectional resonant circuit of claim 1, wherein in a forward operation state of the bidirectional resonant circuit, the controllable switch of the second bridge circuit is turned on at the fixed duty cycle and the controllable switch of the first bridge circuit is turned off during a set period;
the second bridge circuit is used for inverting the high-voltage direct current into alternating current and transmitting the alternating current to the resonance circuit; the resonance circuit is used for resonating the alternating current and transmitting the resonated alternating current to the transformer; the transformer is used for transmitting alternating current to the first bridge circuit in the form of an alternating magnetic field; the first bridge circuit is used for rectifying alternating current into low-voltage direct current.
10. An automobile comprising an on-board power supply system, characterized in that the on-board power supply system comprises a bidirectional resonant circuit as claimed in any one of claims 1 to 9.
CN202080011980.9A 2020-10-14 2020-10-14 Bidirectional resonant circuit and automobile Active CN113424426B (en)

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