CN113169663A

CN113169663A - Drive circuit of channel switch, charging control method and charger

Info

Publication number: CN113169663A
Application number: CN202080005978.0A
Authority: CN
Inventors: 金军骞; 林宋荣; 李鹏
Original assignee: SZ DJI Technology Co Ltd
Current assignee: SZ DJI Technology Co Ltd
Priority date: 2020-08-05
Filing date: 2020-08-05
Publication date: 2021-07-23
Also published as: WO2022027264A1

Abstract

A drive circuit, a charge control method and a charger for a channel switch, the drive circuit (20) comprising: the circuit comprises an isolation circuit (21), a regulating circuit (22) and a push-pull circuit (23), wherein the isolation circuit (21) is used for receiving a control signal, and the control signal comprises a switch-on signal or a switch-off signal; the adjusting circuit (22) is used for adjusting the response time of the channel switch (10); the push-pull circuit (23) is connected with the isolation circuit (21) through the adjusting circuit (22) and is also connected with the channel switch (10); the push-pull circuit (23) is used for converting a preset power supply voltage into a driving signal according to the control signal so as to drive the channel switch (10) to be switched on or switched off according to the response time.

Description

Drive circuit of channel switch, charging control method and charger

Technical Field

The present disclosure relates to the field of charging technologies, and in particular, to a driving circuit of a channel switch, a charging control method, and a charger.

Background

The channel switch of unmanned aerial vehicle's charger, it constitutes to adopt two field effect transistor (MOS pipe) to connect back to back usually, owing to adopt back to connect the MOS pipe and can't directly drive through little the control Unit (MCU), need use special drive IC or optical coupler to drive, to the lithium cell that needs great charge-discharge current, for example large-scale agricultural unmanned aerial vehicle's lithium cell, if the response time (the time that switches on or turn off and correspond) overlength of MOS pipe can lead to the MOS pipe long term to be in linear region, thereby can lead to the MOS pipe damage of generating heat, the danger of "blasting pipe" can appear even.

Disclosure of Invention

Based on this, the embodiment of the application provides a driving circuit of a channel switch, a charging control method and a charger, which can adapt to the response time of an MOS transistor of the channel switch, thereby improving the safety and reliability of the channel switch during charging.

In a first aspect, an embodiment of the present application provides a driving circuit of a channel switch, where the driving circuit includes:

an isolation circuit for receiving a control signal, the control signal comprising a switch on signal or a switch off signal;

a regulating circuit for regulating a response time of the channel switch;

a push-pull circuit connected to the isolation circuit through the regulating circuit and also connected to the channel switch;

the push-pull circuit is used for converting preset power supply voltage into a driving signal according to the control signal received by the isolation circuit so as to drive the channel switch to be switched on or switched off according to the response time.

In a second aspect, an embodiment of the present application provides a charger, where the charger includes a main control circuit, at least one channel switch, and a driving circuit for driving the channel switch to be turned on or off; the drive circuit includes:

the isolation circuit is used for receiving a control signal sent by the main control circuit, and the control signal comprises a switch on signal or a switch off signal;

a regulating circuit for regulating a response time of the channel switch;

In a third aspect, an embodiment of the present application further provides a charging control method, which is applied to the charger provided in the embodiment of the present application, and the charging control method includes:

and sending a control signal to the drive circuit, wherein an isolation circuit of the drive circuit receives the control signal, and a push-pull circuit of the drive circuit converts a preset power supply voltage into a drive signal according to the control signal received by the isolation circuit so as to drive the channel switch to be switched on or switched off according to the response time, thereby charging or stopping charging the battery.

In a fourth aspect, an embodiment of the present application further provides a charger, where the charger includes: one or more processors, working individually or collectively, for performing the charging control method provided by the embodiments of the present application.

The channel switch driving circuit, the charging control method and the charger can adapt to the response time of the MOS tube of the channel switch, so that the MOS tube can be prevented from being in a linear region for a long time when the battery is charged or the battery is powered, and the safety and the reliability of the battery are improved.

It is to be understood that both the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the application.

Drawings

In order to more clearly illustrate the technical solutions of the embodiments of the present application, the drawings needed to be used in the description of the embodiments are briefly introduced below, and it is obvious that the drawings in the following description are some embodiments of the present application, and it is obvious for those skilled in the art to obtain other drawings based on these drawings without creative efforts.

Fig. 1 is a schematic circuit diagram of a charger according to an embodiment of the present disclosure;

fig. 2a is a schematic diagram of a simulation effect when a channel switch provided in the embodiment of the present application is turned on;

fig. 2b is a schematic diagram of a simulation effect when the channel switch is turned off according to the embodiment of the present application;

fig. 3 is a schematic circuit diagram of a charger according to an embodiment of the present disclosure;

fig. 4 is a schematic circuit structure diagram of a driving circuit provided in an embodiment of the present application;

fig. 5 is a schematic circuit diagram of an isolated power supply module according to an embodiment of the present disclosure;

fig. 6 is a schematic circuit diagram of a charge pump circuit according to an embodiment of the present disclosure;

fig. 7 is a schematic circuit diagram of a charge pump circuit according to an embodiment of the present disclosure;

fig. 8 is a schematic circuit diagram of an isolated power supply module according to an embodiment of the present disclosure;

fig. 9 is a schematic circuit structure diagram of a driving circuit according to an embodiment of the present application;

fig. 10 is a schematic circuit structure diagram of another driving circuit provided in an embodiment of the present application;

fig. 11a is a schematic diagram of a simulation effect when a channel switch provided in the embodiment of the present application is turned on;

fig. 11b is a schematic diagram of a simulation effect when the channel switch is turned off according to the embodiment of the present application;

fig. 12 is a schematic flow chart of a charging control method provided by an embodiment of the present application;

fig. 13 is a schematic block diagram of a charger provided in an embodiment of the present application.

Detailed Description

The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are some, but not all, embodiments of the present application. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.

It is also to be understood that the terminology used in the description of the present application herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the application. As used in the specification of the present application and the appended claims, the singular forms "a," "an," and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise.

It should be further understood that the term "and/or" as used in this specification and the appended claims refers to and includes any and all possible combinations of one or more of the associated listed items.

The flow diagrams depicted in the figures are merely illustrative and do not necessarily include all of the elements and operations/steps, nor do they necessarily have to be performed in the order depicted. For example, some operations/steps may be decomposed, combined or partially combined, so that the actual execution sequence may be changed according to the actual situation.

At present, a channel switch of a charger is generally formed by connecting two field effect transistors (MOS transistors) back to back, and the back-to-back MOS transistors cannot be directly driven by a Micro Control Unit (MCU), and a special driving IC or an optical coupler is required to be used for driving, such as a charger of a large-scale agricultural unmanned aerial vehicle, an industrial multi-power system, or an industrial lithium battery charging and discharging cabinet.

For the charger of the large-scale agricultural unmanned aerial vehicle, because the lithium battery of the large-scale agricultural unmanned aerial vehicle has larger charging and discharging current, if the response time (the time corresponding to the on or off) of the MOS tube is too long, the MOS tube is in a linear region for a long time, so that the MOS tube is heated and damaged, and even the danger of tube explosion can occur.

For industrial multi-power supply systems, it is generally required that the multi-power supply system can stably operate for a long time, and it is generally required that the multi-power supply system can be uninterrupted. The multi-power system is generally powered by a plurality of power sources, and different power sources are connected in parallel through channel switches (back-to-back connected MOS tubes). When a multi-power-supply system works normally, only one power supply is used for supplying power, when the power supply stops outputting due to some external factors, a standby power supply needs to be started immediately, the higher requirement is provided for the switching-on speed (response time) of a channel switch, the faster the switching-on speed of an MOS (metal oxide semiconductor) tube is, the more the system stability can be kept, otherwise, the MOS tube is heated and damaged, and even the danger of tube explosion can occur.

For an industrial lithium battery charging and discharging cabinet, because the industrial lithium battery charging and discharging cabinet needs to charge and discharge multiple lithium batteries simultaneously, a power supply of one path often has a design with multiple output channels, and the multiple output channels all comprise channel switches (MOS (metal oxide semiconductor) tubes connected back to back). Because the industrial lithium battery charging and discharging cabinet needs to charge and discharge different lithium batteries, the driving of the industrial lithium battery charging and discharging cabinet needs to be isolated, and then if a battery with larger capacity is charged and discharged, the switching speed is also needed to be higher, otherwise, the MOS tube is damaged because the MOS tube is heated in a linear region for a long time.

However, the MOS transistor of the channel switch is generally driven by an application specific integrated IC or by an optocoupler. The application of the special integrated IC is limited, different special integrated ICs are required to be adopted for driving different MOS transistors, the special integrated IC is generally high in cost and expensive in price, few in alternatives and prone to shortage of supply, and the special integrated IC is high in integration level, so that when some integrated ICs are failed, debugging and maintenance difficulty is high. The driving mode of the optical coupler is adopted, the driving capability of the optical coupler is weak, the purpose of rapidly switching the MOS tube cannot be realized, and the MOS tube often encounters the problem of tube explosion due to being in a linear region in the switching process.

Referring to fig. 1, fig. 1 is a schematic circuit structure diagram of a charger according to an embodiment of the present disclosure. The charger 100 includes a channel switch 10, a main control circuit 11, a power interface 12, and a battery interface 13. The power interface 12 is used for connecting a charging power source, and the battery interface 13 is used for connecting a battery.

The channel switch 10 includes two MOS transistors coupled back to back, the channel switch 10 is connected between the power interface 12 and the battery interface 13, and the optical coupler 14 is connected between the main control circuit 11 and the channel switch 10, that is, a driving method of the optical coupler is adopted. In particular, the corresponding driving principle is as follows:

the main control circuit 11 outputs a control signal, such as a high level V1, to the optical coupler 14, the optical coupler 14 receives the high level V1 to turn on and outputs a driving signal to the gate of the MOS transistor of the channel switch 10, where the driving signal is, for example, a high level V2, and the gate of the MOS transistor receives the high level V2 to turn on, so as to charge the battery; the main control circuit 11 outputs a control signal, such as a low level V3, to the optical coupler 14, the optical coupler 14 is turned off, and outputs a low level driving signal, such as a low level V4, to the gate of the MOS transistor of the channel switch 10, and the MOS transistor of the channel switch is turned off to stop charging the battery.

Based on the driving method of the optocoupler provided in fig. 1, the inventor selects two MOS transistors for simulation, the voltage of the high-level driving signal selected by simulation is 12V, the voltage of the low-level driving signal is 0V, the voltage of the charging power supply is 60V, and the simulation results are shown in fig. 2a and fig. 2b, where fig. 2a is the simulation result when the channel switch is turned on, and the response time (i.e., the on-time) corresponding to the turn-on of the channel switch is found to be about 7.2419 μ s from the simulation result; fig. 2b shows the simulation result when the channel switch is turned off, and it is found from the simulation result that the response time (i.e. turn-off time) corresponding to the turn-off of the channel switch is about 833.71 μ s. Therefore, the conventional driving mode of the optical coupler causes the response time of the MOS tube of the channel switch to be longer, further causes the MOS tube to generate heat, and causes the problem of tube explosion in serious cases.

In fig. 2a and 2b, V _ R6 represents the amount of time that the battery changes over time when the channel switch is turned on or off; v1 represents the level change of the drive signal, corresponding to 12V and 0V; m1_ Vgs represents the amount of voltage change of the channel switch when it is turned on or off.

Therefore, embodiments of the present application provide a driving circuit of a channel switch, a charging control method, and a charger to solve the above problems. The drive circuit of the channel switch can be applied to a charger, and the charging control method is also applied to the charger to adjust the response time of the channel switch so as to ensure the safety of the battery during charging. Under the scene of charging such as heavy current such as agricultural unmanned aerial vehicle, can use the heavy current to charge to the battery, use this drive circuit when improving charge efficiency, security and reliability when can also improving to charge.

Some embodiments of the present application will be described in detail below with reference to the accompanying drawings. The embodiments described below and the features of the embodiments can be combined with each other without conflict.

Referring to fig. 3, fig. 3 is a schematic block diagram of a circuit structure of a charger according to an embodiment of the present disclosure. The charger 100 includes a channel switch 10, a main control circuit 11, a power interface 12, a battery interface 13, and a driving circuit 20. The power interface 12 is used for connecting a charging power source, and the battery interface 13 is used for connecting a battery.

The channel switch 10 includes two MOS transistors coupled back to back, the channel switch 10 is connected between the power interface 12 and the battery interface 13, and the driving circuit 20 is connected between the main control circuit 11 and the channel switch 10, and is configured to receive a control signal from the main control circuit 11 and drive the channel switch 10 to turn on or off according to the control signal, so as to charge the battery or stop charging.

Referring to fig. 4, fig. 4 is a schematic circuit structure diagram of a driving circuit of a channel switch according to an embodiment of the present disclosure. As shown in fig. 4, the driving circuit 20 includes: an isolation circuit 21, a regulation circuit 22, and a push-pull circuit 23.

The isolation circuit 21 is configured to receive a control signal, specifically, to receive a control signal sent by the main control circuit 11, where the control signal includes a switch on signal or a switch off signal, the switch on signal is used to control the channel switch 10 to be turned on, such as a high level signal, which may be 3.3V for example, and the switch off signal is used to control the channel switch 10 to be turned off, such as a low level signal, which may be 0V for example.

The adjusting circuit 22 is used for adjusting the response time of the channel switch 10, and specifically is used for adjusting the response time of two MOS transistors of the channel switch 10, including the response time when the MOS transistor is turned on and the response time when the MOS transistor is turned off.

The push-pull circuit 23 is connected to the isolation circuit 21 via the regulating circuit 22, and is also connected to the channel switch 10, specifically to the gates of the two MOS transistors of the channel switch 10. And is configured to convert the preset power supply voltage VCC2 into a driving signal according to the control signal received by the isolation circuit 21, so as to drive the channel switch 10 to turn on or off according to the response time.

Specifically, when the isolation circuit 21 receives the switch conducting signal, the push-pull circuit 23 is controlled to convert the preset power supply voltage VCC2 into a driving signal, for example, the push-pull circuit 23 is controlled to be conducting to use the preset power supply voltage VCC2 as the driving signal (i.e., amplification of the control signal is achieved), and meanwhile, the response time is adjusted by the adjusting circuit 22, so that the MOS transistor of the drive channel switch 10 is conducted according to the corresponding response time, and further, the battery is charged.

In the embodiment of the present application, the predetermined power voltage VCC2 is 12V, but may have other values. In some embodiments, the predetermined power voltage VCC2 is related to different types of MOS transistors, such as MOS transistors requiring larger driving capability requiring a larger voltage of the predetermined power voltage VCC 2.

It should be noted that the power supply voltage VCC1 in fig. 4 is used as a charging power supply, for example, 60V, for charging the battery.

The driving circuit provided by the above embodiment firstly isolates the control signal through the isolation circuit, and adjusts the response time of the channel switch through the adjusting circuit, and then amplifies the control signal through the push-pull circuit to obtain the driving signal for driving the channel switch, thereby realizing the on-off of the driving channel switch, and thus avoiding the channel switch from being in a linear region for a long time, and further improving the charging safety. For a lithium battery requiring larger charging and discharging current, such as an agricultural unmanned aerial vehicle battery, the charging safety is greatly improved.

In some embodiments, the isolation circuit 21 includes a control switch, and the control switch is connected to the preset power voltage VCC2 and turned on or off according to a control signal of the main control circuit 11 to output the preset power voltage VCC2 to the push-pull circuit 23, so as to generate the driving signal. In particular, the control switch comprises an optocoupler or a transformer.

In some embodiments, to further improve the safety of the circuit, the driving circuit 20 includes: an isolated power supply module including a first isolated power supply and a second isolated power supply. Illustratively, as shown in fig. 4, the first isolated power source is VCC1, and the second isolated power source is VCC2, where the first isolated power source VCC1 is used as a charging power source to charge a battery, and the second isolated power source VCC2 is used as the preset power voltage. The isolation circuit 21 and the push-pull circuit 23 are both connected to the second isolation power source VCC2, and are configured to convert the voltage of the second isolation power source VCC2 into a driving signal according to the control signal.

In some embodiments, the first isolated power supply and the second isolated power supply are different voltages, such as 60V for the first isolated power supply and 12V for the second isolated power supply. In other embodiments, the voltage level of the second isolated power supply is related to a corresponding parameter of the fet of the channel switch, and specifically related to the response time of the fet, for example, if the response time of the fet is longer, the corresponding voltage is larger, and thus the voltage level is used to adjust the response time of the channel switch. For a lithium battery requiring larger charging and discharging current, such as an agricultural unmanned aerial vehicle battery, the charging safety is greatly improved.

Although the isolation power supply can improve the safety of the circuit, the isolation power supply is high in price and long in purchase period, and the isolation power supply is large in size, needs to occupy a large PCB area, is limited in height space, and is inconvenient for PCB layout and element placement, so that the isolation power supply is not beneficial to product design and miniaturization.

In view of this, the embodiments of the present application also provide an alternative solution. Specifically, as shown in fig. 5, fig. 5 is a schematic circuit structure diagram of an isolated power supply module according to an embodiment of the present application. The isolated power supply module 110 has a power input terminal Vin and a power output terminal Vout, and the isolated power supply module 110 includes a charge pump circuit 111, wherein the power input terminal Vin is connected to the power output terminal Vout through the charge pump circuit 111. The power input terminal Vin is connected to a voltage source VCC for receiving an input voltage, and the input voltage provided by the voltage source VCC is, for example, 12V. The power output terminal Vout is used for outputting an output voltage, and the charge pump circuit 111 is used for isolating the output voltage from the input voltage. The term "isolated" means that there is no direct electrical connection between the input and output circuits of the power supply, and there is no current circuit between the input and output in an insulated high-impedance state.

Fig. 6 discloses a schematic diagram of the operation of a charge pump circuit. As shown in fig. 6, the charge pump circuit comprises a pumping capacitor Cp and an output capacitor Cout, and the pumping capacitor Cp can be charged by the input voltage Uin when the switches K1, K3 are simultaneously turned on by the pumping capacitor Cp as an intermediate transfer station of charge. When the switches K1 and K3 are turned off and the switches K2 and K4 are turned on, the pumping capacitor Cp is connected in parallel with the output capacitor Cout, the pumping capacitor Cp discharges, and the charge of the pumping capacitor Cp is transferred to the output capacitor Cout, thereby outputting an output voltage Uout. In order to stabilize the input voltage Uin, the charge pump circuit further comprises an input capacitance Cin.

The embodiment of the application designs the isolation power module 110 by using the charge transfer principle of the pumping capacitor Cp of the charge pump circuit 111, so that the isolation power module is suitable for a high-end MOS drive circuit.

It should be noted that the first isolated power supply and the second isolated power supply provided in the above embodiments may both adopt the isolated power supply module provided in fig. 5.

Referring to fig. 4 and fig. 5, for example, taking the second isolation power VCC2 as an example, the control switch is electrically connected to the power output terminal Vout of the isolation power module 110 and receives a control signal of the main control circuit. The channel switch 10 is connected with the control switch through the push-pull circuit 23 and the adjusting circuit, and the channel switch 10 is connected to the battery, the channel switch 10 is used for being switched on and off under the control of the control switch to control whether the battery is charged or not.

It should be noted that the first isolated power source VCC1 may also be the isolated power source module provided in fig. 5, and the connection mode and operation principle thereof refer to the second isolated power source VCC 2.

When the control switch is closed based on the control signal, the active channel switch 10 of the push-pull circuit 23 is turned on under the trigger of the output voltage outputted by the isolation power supply module 110, thereby charging the battery.

The drive circuit of the embodiment of the application utilizes the charge pump circuit 111 to design the isolation power supply module 110, and output isolated output voltage is realized, so that high material cost for purchasing an isolation power supply can be saved.

In one embodiment, the output voltage may be equal to the input voltage. Of course, in other embodiments, the output voltage may be greater than the input voltage, and the charge pump circuit 111 may provide a multiplied output voltage.

Fig. 7 discloses a circuit structure diagram of the charge pump circuit 111 according to an embodiment of the present application. As shown in fig. 7, the charge pump circuit 111 includes a pumping capacitor Cp, an output capacitor Cout connected to the power output terminal Vout, a first switch module 112, and a second switch module 113.

When the first switch module 112 is closed, the voltage source VCC is connected to both ends of the pumping capacitor Cp, and the input voltage charges the pumping capacitor Cp. When the first switch module 112 is turned off and the second switch module 113 is turned on, the pumping capacitor Cp is connected in parallel with the output capacitor Cout, and the pumping capacitor Cp charges the output capacitor Cout.

In some embodiments, the charge pump circuit 111 further comprises an input capacitor Cin connected to the power supply input Vin. The input capacitance Cin is in parallel with the pumping capacitance Cp when the first switching module 112 is closed. The input capacitance Cin may be used to stabilize the input voltage. When the voltage alternates, the voltage at the two ends of the input capacitor Cin can not change suddenly due to the charging action of the input capacitor Cin, so that the stability of the input voltage is ensured.

In some embodiments, the pumping capacitance Cp, the output capacitance Cout, and the input capacitance Cin may comprise ceramic capacitances. In the charge pump circuit 111 according to the embodiment of the present application, the pumping capacitor Cp, the output capacitor Cout, and/or the input capacitor Cin are patch ceramic capacitors, and the capacitance value of the ceramic capacitors does not need to be large. For example, the capacitance of the ceramic capacitor may be 100NF (nano farad) -1 μ F (micro farad).

Therefore, the isolated power module 110 using the charge pump circuit 111 has a small volume, occupies a small area of a PCB, and facilitates the layout of the PCB and the placement of components.

Fig. 8 discloses a circuit structure diagram of an isolated power module according to an embodiment of the present application. As shown in fig. 8 and in conjunction with fig. 7, the first switch module 112 includes a first diode D1, an anode of the first diode D1 is connected to the voltage source VCC, and a cathode of the first diode D1 is connected to the positive terminal of the pumping capacitor Cp. The second switching module 113 includes a second diode D2, an anode of the second diode D2 is connected to the positive terminal of the pumping capacitor Cp, and a cathode of the second diode D2 is connected to the positive terminal of the output capacitor Cout.

The first diode D1 and the second diode D2 may function as switches because of the unidirectional conductivity, forward direction conduction and reverse direction cutoff of the diodes. For example, the first diode D1 and the second diode D2 may function as the switches K1 and K2 in the operation schematic diagram of the charge pump circuit shown in fig. 6.

The isolated power supply module 110 of the embodiment of the present application skillfully adopts the first diode D1 and the second diode D2 in the charge pump circuit 111 to serve as switches, so that the triggering operation of the switches can be omitted, and the structure is very simple.

In some embodiments, the first switch module 112 has a first control terminal T1, the first control terminal T1 is used for receiving a first control signal S1, and the first switch module 112 is controlled to open and close by a first control signal S1. The first switch module 112 may include a first switch tube, and the first switch module 112 is controlled to be turned on and off by a first control signal S1.

In one embodiment, the first switch tube includes a first field effect transistor, a gate of the first field effect transistor is connected to the first control terminal T1, a drain of the first field effect transistor is connected to a negative terminal of the pumping capacitor, and a source of the first field effect transistor is grounded. And a resistor is arranged between the grid electrode and the source electrode of the first field effect transistor, so that the voltage division protection effect is realized.

Illustratively, the first switch tube includes a first NMOS tube Q50. The gate G of the first NMOS is connected to the first control terminal T1 of the first switch module 112 for receiving the first control signal S1. The drain D of the first NMOS is connected to the negative terminal of the pumping capacitor Cp, and the source S of the first NMOS is grounded to GND.

Optionally, a first resistor R1 is disposed between the gate G and the source S of the first NMOS transistor Q50, and the first resistor R1 is a voltage dividing resistor and can perform a voltage dividing function.

Optionally, the gate G of the first NMOS transistor Q50 is connected to the first control terminal T1 of the first switch module 112 through a second resistor R2. Optionally, the drain D of the first NMOS transistor Q50 is connected to the negative terminal of the pumping capacitor Cp through a third resistor R3. The second resistor R2 and the third resistor R3 are current limiting resistors and can play a role in limiting current.

In some embodiments, the second switch module 113 has a second control terminal T2, and the second control terminal T2 is used for receiving a second control signal S2, and controlling the opening and closing of the second switch module 113 by the second control signal S2. The second switch module 113 may include a second switch tube and a third switch tube, the second switch tube is connected between the negative terminal of the pumping capacitor Cp and the negative terminal of the output capacitor Cout, and the second switch tube is controlled by controlling the third switch tube to be turned on and off by the second control signal S2.

In one embodiment, the second field effect transistor comprises a second field effect transistor, and the third field effect transistor comprises a third field effect transistor, wherein the second field effect transistor comprises a PMOS transistor, and the third field effect transistor comprises an NMOS transistor; the drain electrode of the second field effect transistor is connected with the negative electrode end of the pumping capacitor, the source electrode of the second field effect transistor is connected with the negative electrode end of the output capacitor, the grid electrode of the second field effect transistor is connected with the drain electrode of the third field effect transistor, the source electrode of the third field effect transistor is grounded, and the grid electrode of the third field effect transistor is connected with the second control end. And a resistor is arranged between the grid electrode and the source electrode of the second field effect transistor, and a resistor is arranged between the grid electrode and the source electrode of the third field effect transistor, so that the voltage division protection effect is realized.

Illustratively, the second switch tube comprises a PMOS tube Q51, and the third switch tube comprises a second NMOS tube Q52. The drain D of the PMOS transistor Q51 is connected to the negative terminal of the pumping capacitor Cp, the source S of the PMOS transistor Q51 is connected to the negative terminal of the output capacitor Cout, the gate G of the PMOS transistor Q51 is connected to the drain D of the second NMOS transistor Q52, the source S of the second NMOS transistor Q52 is grounded GND, and the gate G of the second NMOS transistor Q52 is connected to the second control terminal T2 of the second switch module 113, so as to receive the second control signal S2.

In one embodiment, the first control signal S1 received by the first control terminal T1 of the first switch module 112 and the second control signal S2 received by the second control terminal T2 of the second switch module 113 are complementary signals. For example, the first control signal S1 and the second control signal S2 are both PWM (Pulse Width Modulation) signals with 50% duty ratio and 100KHz to 1MHz frequency.

When the first control signal S1 is at a high level, the first NMOS transistor Q50 is turned on, the input voltage, e.g., 12V, provided by the voltage source VCC charges the pumping capacitor Cp, and the pumping capacitor Cp is charged to 12V. Since the first control signal S1 and the second control signal S2 have opposite phases and are complementary, the second control signal S2 is low, and the second NMOS transistor Q52 is turned off.

When the first control signal S1 is at a low level, the first NMOS transistor Q50 is turned off. Since the first control signal S1 and the second control signal S2 are complementary in phase, the second control signal S2 is high at this time, the second NMOS transistor Q52 is turned on, the gate G of the PMOS transistor Q51 is low, the PMOS transistor Q51 is turned on, the pumping capacitor Cp is connected in parallel with the output capacitor Cout, the pumping capacitor Cp charges the output capacitor Cout, and the output capacitor Cout is charged to 12V. Therefore, an output voltage of 12V can be output.

Alternatively, a fourth resistor R4 is disposed between the gate G and the source S of the PMOS transistor Q51, and a fifth resistor R5 is disposed between the gate G and the source S of the second NMOS transistor Q52. The fourth resistor R4 and the fifth resistor R5 are voltage dividing resistors and can play a role in voltage division protection.

Optionally, the gate G of the second NMOS transistor Q52 is connected to the second control terminal T2 through a sixth resistor R6. Optionally, the gate G of the PMOS transistor Q51 is connected to the drain D of the second NMOS transistor Q52 through a seventh resistor R7. The sixth resistor R6 and the seventh resistor R7 are current limiting resistors and can play a role in limiting current.

In the embodiment described above, the isolated power supply module 110 is powered using a voltage source VCC of 12V. In other embodiments, the voltage source VCC providing higher voltage may also be used to supply power, and therefore, in this case, the isolated power module 110 of the embodiment of the present application may further include a voltage boost circuit (not shown), which may be used to boost the voltage of the voltage source VCC.

In one embodiment, the power input terminal Vin of the isolated power module 110 is connected to the voltage source VCC through a voltage boosting circuit, and the voltage boosting circuit provides the boosted voltage to the power input terminal Vin of the isolated power module 110.

It is understood that in some embodiments, a lower voltage source VCC may also be provided to supply power, and therefore, in this case, the isolated power module 110 of the embodiment of the present application may further include a voltage dropping circuit (not shown), which may be used to drop the voltage of the voltage source VCC.

Referring to fig. 9, the channel switch includes a fourth fet M4 and a fifth fet M5, and the fourth fet M4 and the fifth fet M5 are electrically coupled back to back. Specifically, the drain D of the fourth fet M4 is connected to the first isolation power source VCC1, the source S of the fourth fet M4 is connected to the drain of the fifth fet M5, the source S of the fifth fet M5 is used for connecting a battery, the drain D of the fifth fet M5 is connected to the source S of the fourth fet M4, and the gates of the fourth fet M4 and the fifth fet are both connected to the output terminal of the push-pull circuit 23.

In some embodiments, the gate G of the fourth fet M4 is connected to the output terminal of the push-pull circuit 23 through the first resistor R13, and the gate G of the fifth fet M5 is connected to the output terminal of the push-pull circuit 23 through the second resistor R15. The resistance value of the first resistor R13 is related to the response parameter of the fourth field effect transistor M4, and is used for adjusting the response time of the fourth field effect transistor M4; and/or the resistance value of the second resistor R15 is related to the response parameter of the fifth field effect transistor M5 and is used for adjusting the response time of the fifth field effect transistor M5.

The response parameters specifically refer to parameters of the field effect transistor, and determine the response time of the field effect transistor. Such as a longer response time, a larger resistance resistor may be selected.

In some embodiments, the source S of the fourth fet M4 or the drain D of the fifth fet M5 is connected to the output terminal of the push-pull circuit 23 through a resistor R14, so as to perform a voltage division protection function.

In some embodiments, referring to fig. 9, the isolation circuit 21 includes a control switch, which may include an optocoupler U11, wherein the optocoupler U11 includes a light emitting diode and a phototransistor. The anode of the led is connected to a dc power supply terminal, which may be the power supply terminal of the main control circuit, for example, the voltage may be 3.3V as a switch-on control signal, and the cathode of the led is grounded through a resistor R11. The collector C of the phototransistor is connected to the positive terminal Vout + of the power output terminal of the second isolated power supply VCC to receive the output voltage outputted from the isolated power supply module, and the emitter E of the phototransistor is connected to the regulating circuit 22 and to ground through a resistor R12.

In some embodiments, the push-pull circuit comprises two switching tubes of the same type and different polarities; one of the switch tubes is in a conducting state or a blocking state, and correspondingly, the other switch tube is in a blocking state or a conducting state. And further realize the amplification effect of the push-pull circuit on the control signal. The switching tube comprises a triode or a field effect tube.

In some embodiments, referring to fig. 9, the two transistors are a first transistor Q11 and a second transistor Q12, respectively, wherein the first transistor Q11 is an NPN transistor, and the second transistor Q12 is a PNP transistor. The base electrodes of the first triode Q11 and the second triode Q12 are connected as the control end of the push-pull circuit 23, and are connected with the isolation circuit 21 through the adjusting circuit 22 and grounded, the collector electrode of the first triode Q11 is connected with the preset power supply voltage VCC2, the emitter electrode of the first triode Q11 is connected with the emitter electrode of the second triode Q12, and the collector electrode of the second triode Q12 is grounded.

In some embodiments, the control terminal of the push-pull circuit 23 may also be grounded through a third resistor (not shown) to perform a voltage division protection function.

In some embodiments, as shown in FIG. 9, the adjustment circuit 22 includes an adjustable resistor R10, and the adjustable resistor R10 is used to adjust the response time of the channel switch. In particular, the response time of the MOS tube for adjusting the channel switch. Therefore, for the MOS tubes with different parameters, the corresponding response time of the MOS tubes with different parameters is different, the application of different scenes can be realized by adjusting the resistance value of the adjustable resistor, and the back-to-back MOS tube channel switch can be a general platform scheme for forming the channel switch; meanwhile, for lithium batteries which need larger charging and discharging current, such as agricultural unmanned aerial vehicle batteries, the charging safety is greatly improved.

In some embodiments, as shown in fig. 10, the adjustment circuit 22 includes a first adjustable resistor R101 and a second adjustable resistor R102. One end of the first adjustable resistor R101 is connected with the base electrode of the first triode Q11, one end of the second adjustable resistor R102 is connected with the base electrode of the second triode Q12, and the other end of the first adjustable resistor R101 is connected with the other end of the second adjustable resistor R102 and is connected with the isolation circuit 21 after being connected. The first adjustable resistor R101 and the second adjustable resistor R102 are respectively used for adjusting the on-response time and the off-response time.

In some embodiments, the regulating circuit 21 comprises a resistor having a preset resistance value determined according to a response parameter of a field effect transistor of the channel switch.

For the operating principle of the drive circuit in fig. 9 and 10: the optical coupler receives a control signal sent by the main control circuit 11, where the control signal includes a switch on signal or a switch off signal, the switch on signal is at a high level, and the switch off signal is at a low level. When receiving the high level, the light emitting diode of the optical coupler U11 is turned on to emit light, the transistor of the optical coupler U11 senses the light emitting diode to emit light and is turned on, the adjusting circuit 22 is used for adjusting the response time of the channel switch, the base electrodes (the base electrodes of the first transistor Q11 and the second transistor Q12) of the push-pull circuit 23 input the high level, the first transistor Q11 is turned on, the second transistor Q11 is turned off, the gate voltages Vgs of the fourth field effect transistor M4 and the fifth field effect transistor M5 are rapidly increased, that is, the MOS transistors M4 and M5 are turned on, and the channel switch 10 outputs the high voltage to charge the battery. When receiving a low level, the light emitting diode of the optocoupler U11 is turned off, the transistor of the optocoupler U11 is turned off, the base (the base of the first transistor Q11 and the base of the second transistor Q12) of the push-pull circuit 23 inputs a low level, the first transistor Q11 is turned off, the second transistor Q11 is turned on, the gate voltages Vgs of the fourth field-effect transistor M4 and the fifth field-effect transistor M5 are rapidly reduced, that is, the MOS transistors M4 and M5 are turned off, and the channel switch 10 is turned off to stop charging the battery.

For the driving circuit of the channel switch provided in the embodiment of the present application, specifically, the driving circuit of the channel switch in fig. 10, the inventor selects two identical MOS transistors in fig. 1 to perform simulation, where the simulation is that the voltage corresponding to the selected driving signal is 12V when the driving signal is at a high level, the voltage corresponding to the driving signal is 0V when the driving signal is at a low level, and the voltage of the charging power supply is 60V, and the simulation results are shown in fig. 11a and 11b, fig. 2a is a simulation result when the channel switch is turned on, and the response time (i.e., the on time) corresponding to the turn-on of the channel switch is 2.2013 μ s; fig. 2b shows the simulation result when the channel switch is turned off, and the response time (i.e. turn-off time) corresponding to the turn-off of the channel switch is 32.323 μ s. Therefore, by adopting the driving circuit provided by the embodiment of the application, the response time of the channel switch can be effectively reduced, and the charging safety of the battery is further improved. For a lithium battery requiring larger charging and discharging current, such as an agricultural unmanned aerial vehicle battery, the charging safety is greatly improved.

In fig. 11a and 11b, V _ R6 represents the amount of time that the battery changes over time when the channel switch is turned on or off; v1 represents the level change of the driving signal, corresponding to 12V and 0V, respectively; m1_ Vgs represents the amount of voltage change of the channel switch when it is turned on or off.

Table 1 shows comparison of simulation results of response times corresponding to different driving schemes

It can be seen from table 1 that, by using the driving circuit provided by the embodiment of the present application, the response time of the MOS transistor can be greatly reduced, thereby avoiding the occurrence of "tube explosion" of the MOS transistor, and improving the safety of battery charging.

In some embodiments, the driving circuit of the channel switch may be applied to a charger, which is a high current charger, such as a charger of an unmanned aerial vehicle, that is, the charging current of the charger is greater than a preset current threshold, such as greater than 3A; or a charger for unmanned vehicle batteries. Due to the large-current charger, if the MOS tube works in a linear region for a long time, the accident of tube explosion is more likely to occur. By using the driving circuit provided by the embodiment of the application, the safety and the reliability of the battery during charging can be improved.

In some application scenarios, for example agricultural unmanned aerial vehicle, agricultural unmanned aerial vehicle need carry out the circulation operation, consequently need improve the charge efficiency of battery, consequently need use heavy current to charge the battery to improve the charge efficiency of battery, and when using this drive circuit when improving charge efficiency, security and reliability when can also improving to charge.

In some embodiments, when the charger is used to charge a battery, the main control circuit of the charger is further configured to: acquiring a charging request current of the battery, and determining the charging current of the charger according to the charging request current; and determining a safe response time range of the channel switch according to the charging current so as to adjust the response time of the channel switch through the adjusting circuit according to the safe response time range.

In particular, the battery may be a smart battery, i.e. the battery comprises an MCU, and in particular the requested charging current (e.g. 3A) of the battery may be transmitted to the charger when the battery is connected to the charger. When the charger receives the requested charging current, the charger determines the charging current of the charger according to the requested charging current, for example, the charging current is set to be equal to the requested charging current, that is, the charging current is equal to 3A, but may also be greater than the requested charging current, for example, the charging current is set to be 3.1A. Then, the safe response time range of the channel switch (MOS tube) is determined according to the charging current, and the safe response time range can ensure that the response time of the MOS tube is not to cause the MOS tube to explode when the charging current is used for charging the battery. And after the safe response time range of the channel switch is determined, adjusting the response time of the channel switch through the adjusting circuit according to the safe response time range, for example, adjusting the response time of the channel switch to be within the safe response time range.

It should be noted that the adjusting circuit includes an adjustable resistor, so that the response time of the channel switch can be adjusted by adjusting the resistance of the adjustable resistor.

For example, if the resistance value of the adjustable resistor needs to be adjusted manually, the adjustment mode of the adjustable resistor corresponding to the response time of the channel switch may be determined according to the safe response time range, the current resistance value of the adjustable resistor is adjusted to be larger or smaller according to the adjustment mode, adjustment prompt information is generated according to the adjustment mode, and the adjustment prompt information is output to a user, for example, the adjustment prompt information is displayed through a display screen of a charger, or the adjustment prompt information is broadcasted in a voice mode.

For another example, if the resistance value of the adjustable resistor does not need to be adjusted manually, such as a thermistor or a photo resistor, the adjustment mode of the adjustable resistor corresponding to the response time of the channel switch may be determined according to the safe response time range, the current resistance value of the adjustable resistor is adjusted to be larger or smaller by the adjustment mode, and the main control circuit adjusts the adjustable resistor according to the adjustment mode.

In some embodiments, a preset mapping relationship table between the charging current and the safe response time range corresponding to the MOS transistor of the channel switch may be tested in advance through experiments, specifically as shown in table 2.

Table 2 is a preset mapping relation table between the charging current and the safe response time range

Charging current (A)	Safe response time Range (us)
		i1	a11～a21
i2	a12～a22
		i3	a13～a23

In table 2, i1, i2, and i3 represent different charging currents, a11-a13 and a21-a23 represent different times, and the correspondence in table 2 is obtained by experimental tests performed on MOS in a channel switch of a charger, and even when charging is performed using a corresponding charging current, if the response time is ensured within a safe response time range corresponding to the charging current, it can be ensured that "pipe explosion" does not occur.

Therefore, the safety response time range corresponding to the charging current can be inquired according to the preset mapping relation table between the charging current and the safety response time range and is used as the safety response time range of the channel switch.

Therefore, to the charger of heavy current, for example agricultural unmanned aerial vehicle's charger, use the drive circuit that above-mentioned embodiment provided, can effectively avoid being in linear region for a long time of the MOS pipe of charger channel switch, and then the phenomenon of "exploding the pipe" can not appear, security and reliability when having improved the charger and charging from this.

In some embodiments, the charger has a charging position, i.e. the device to be powered can only be charged by one current and/or voltage.

In some embodiments, the charger has a plurality of charging positions, and in each charging position, the charger can provide corresponding charging current and/or voltage to charge the device to be charged. Therefore, the power supply device can be suitable for devices to be supplied with different charging requirements.

In some embodiments, the charger may have a charging function, and/or a discharging function, and/or a power balancing function for the device to be powered.

In some embodiments, the charger may power batteries, the drone fuselage, the handheld cradle head, the drone vehicle, and the waiting power supply.

Fig. 12 discloses a schematic flowchart of a charging control method provided in an embodiment of the present application. The charging control method is applied to the charger provided in each of the above embodiments, and the charger completes charging of the battery by operating the charging control method.

As shown in fig. 12, the charge control method includes step S101.

S101, sending a control signal to the driving circuit, receiving the control signal by an isolation circuit of the driving circuit, converting a preset power supply voltage into a driving signal by a push-pull circuit of the driving circuit according to the control signal received by the isolation circuit, and driving the channel switch to be switched on or switched off according to the response time so as to charge or stop charging the battery.

Specifically, a main control circuit of the charger sends a control signal to an isolation circuit of the driving circuit, wherein the control signal comprises a switch on signal or a switch off signal; after the isolating circuit receives the switch conducting signal or the switch closing signal, the response time of the channel switch is adjusted through the adjusting circuit, and meanwhile, the push-pull circuit is used for presetting power supply voltage according to the switch conducting signal or the switch closing signal and converting the power supply voltage into a driving signal so as to drive the channel switch to be conducted or closed according to the response time, and further, the battery is charged or the charging is stopped. The charging control method is simple and easy to implement, and meanwhile, the response time of the channel switch can be adjusted, and the safety of the charger when the charger charges the battery is ensured.

Fig. 13 discloses a schematic block diagram of a charger of an embodiment of the present application. As shown in fig. 13, the charger includes one or more processors 101. The processor 101 may be, for example, a Micro-controller Unit (MCU), a Central Processing Unit (CPU), a Digital Signal Processor (DSP), or the like. The processor 41 works individually or collectively for executing the charging control method as described above.

The charger of the embodiment of the present application has similar beneficial technical effects to the charger of each embodiment described above, and therefore, the description thereof is omitted.

While the invention has been described with reference to specific embodiments, the scope of the invention is not limited thereto, and those skilled in the art can easily conceive various equivalent modifications or substitutions within the technical scope of the invention. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.

Claims

1. A driving circuit for a channel switch, comprising:

a regulating circuit for regulating a response time of the channel switch;

2. The circuit of claim 1, wherein the isolation circuit comprises a control switch, and the control switch is connected to the preset power voltage and turned on or off according to the control signal to output the preset power voltage to the push-pull circuit, so as to generate the driving signal.

3. The circuit of claim 2, wherein the control switch comprises an optocoupler or a transformer.

4. The circuit of claim 1, wherein the push-pull circuit comprises two switching tubes of the same type with different polarities; one of the switch tubes is in a conducting state or a blocking state, and correspondingly, the other switch tube is in a blocking state or a conducting state.

5. The circuit of claim 4, wherein the switching tube comprises a triode or a field effect transistor.

6. The circuit of claim 5, wherein the two transistors are a first transistor and a second transistor, respectively, wherein the first transistor is an NPN transistor and the second transistor is a PNP transistor;

the base electrodes of the first triode and the second triode are connected to be used as the control end of the push-pull circuit, and are connected with the isolation circuit through the adjusting circuit and grounded, the collector electrode of the first triode is connected with preset power voltage, the emitter electrode of the first triode is connected with the emitter electrode of the second triode, and the collector electrode of the second triode is grounded.

7. The circuit of claim 6, wherein a control terminal of the push-pull circuit is coupled to ground through a third resistor.

8. The circuit of claim 1, wherein the adjustment circuit comprises an adjustable resistance for adjusting a response time of the channel switch.

9. The circuit of claim 6, wherein the adjustment circuit comprises a first adjustable resistance and a second adjustable resistance; one end of the first adjustable resistor is connected with the base electrode of the first triode, one end of the second adjustable resistor is connected with the base electrode of the second triode, and the other end of the first adjustable resistor is connected with the other end of the second adjustable resistor and connected with the isolation circuit.

10. The circuit of claim 1, wherein the regulating circuit comprises a resistor having a predetermined resistance value determined based on a response parameter of a field effect transistor of the channel switch.

11. The circuit of claim 1, further comprising:

the isolation power supply module comprises a first isolation power supply and a second isolation power supply;

the first isolation power supply is used as a charging power supply to charge a battery; the second isolation power supply is used as the preset power supply voltage, and the isolation circuit and the push-pull circuit are connected with the second isolation power supply and used for converting the voltage of the second isolation power supply into a driving signal according to the control signal.

12. The circuit of claim 11, wherein the isolated power supply module comprises:

a charge pump circuit;

power input end and power output end, power input end passes through charge pump circuit is connected to power output end, power input end connects the voltage source for receive an input voltage, power output end is used for exporting an output voltage, charge pump circuit be used for with output voltage with input voltage keeps apart.

13. The circuit of claim 12, wherein the output voltage is equal to the input voltage.

14. The circuit of claim 12, wherein the charge pump circuit comprises: the pumping capacitor, the output capacitor connected with the power output end, the first switch module and the second switch module;

wherein when the first switch module is closed, the voltage source is connected across the pumping capacitor, and the input voltage charges the pumping capacitor;

when the first switch module is switched off and the second switch module is switched on, the pumping capacitor is connected with the output capacitor in parallel, and the pumping capacitor charges the output capacitor.

15. The circuit of claim 14, wherein the charge pump circuit further comprises an input capacitor coupled to the power input, wherein the input capacitor is coupled in parallel with the pumping capacitor when the first switch module is closed.

16. The circuit of claim 15, wherein the pumping capacitance, the output capacitance, and the input capacitance comprise: a ceramic capacitor.

17. The circuit of claim 14, wherein the first switching module comprises a first diode, an anode of the first diode being connected to the voltage source, and a cathode of the first diode being connected to the positive terminal of the pumping capacitor.

18. The circuit of claim 17, wherein the second switching module comprises a second diode, an anode of the second diode being connected to the positive terminal of the pumping capacitor, and a cathode of the second diode being connected to the positive terminal of the output capacitor.

19. The circuit of claim 14, wherein the first switch module has a first control terminal, and the first control terminal is configured to receive a first control signal, and the first switch module is controlled to open and close by the first control signal.

20. The circuit of claim 19, wherein the first switch module comprises a first switch tube, and the first switch module is controlled to be turned on or off by the first control signal.

21. The circuit of claim 20, wherein the first switch comprises a first fet, a gate of the first fet is connected to the first control terminal, a drain of the first fet is connected to the negative terminal of the pumping capacitor, and a source of the first fet is grounded.

22. The circuit of claim 21, wherein a resistor is disposed between the gate and the source of the first fet.

23. The circuit of claim 14, wherein the second switch module has a second control terminal, and the second control terminal is configured to receive a second control signal, and the second control signal controls the second switch module to open and close.

24. The circuit of claim 23, wherein the second switch module comprises a second switch tube and a third switch tube, the second switch tube is connected between the negative terminal of the pumping capacitor and the negative terminal of the output capacitor, and the second switch tube is controlled by the second control signal to control the third switch tube to be turned on or off.

25. The circuit of claim 24, wherein the second fet comprises a second fet and the third fet comprises a third fet, wherein the second fet comprises a PMOS transistor and the third fet comprises an NMOS transistor;

the drain electrode of the second field effect transistor is connected with the negative electrode end of the pumping capacitor, the source electrode of the second field effect transistor is connected with the negative electrode end of the output capacitor, the grid electrode of the second field effect transistor is connected with the drain electrode of the third field effect transistor, the source electrode of the third field effect transistor is grounded, and the grid electrode of the third field effect transistor is connected with the second control end.

26. The circuit of claim 25, wherein a resistor is disposed between the gate and the source of the second fet and a resistor is disposed between the gate and the source of the third fet.

27. The circuit of claim 12, wherein the isolated power supply module further comprises a boost circuit for boosting the voltage of the voltage source.

28. The circuit of claim 27, wherein the power supply input is coupled to the voltage source through the boost circuit, the boost circuit providing a boosted voltage to the power supply input.

29. The circuit of claim 11, wherein the first and second isolated power supplies are at different voltages.

30. The circuit of claim 11, wherein the voltage magnitude of the second isolated power supply is related to a corresponding parameter of a field effect transistor of the channel switch.

31. The circuit of claim 1, wherein the channel switch comprises a fourth field effect transistor and a fifth field effect transistor electrically coupled back to back.

32. The circuit of claim 31, wherein a drain of the fourth fet is connected to a first isolated power supply, a source of the fourth fet is connected to a drain of the fifth fet, and a gate of the fourth fet is connected to an output of the push-pull circuit;

the source electrode of the fifth field effect transistor is used for being connected with a battery, the drain electrode of the fifth field effect transistor is connected with the source electrode of the fourth field effect transistor, and the grid electrode of the fifth field effect transistor is connected with the output end of the push-pull circuit.

33. The circuit of claim 31, wherein a gate of the fourth fet is coupled to the output of the push-pull circuit through a first resistor, and a gate of the fifth fet is coupled to the output of the push-pull circuit through a second resistor.

34. The circuit of claim 33 wherein the magnitude of the first resistor is related to a response parameter of the fourth fet for adjusting a response time of the fourth fet; and/or the resistance value of the second resistor is related to the response parameter of the fifth field effect transistor and is used for adjusting the response time of the fifth field effect transistor.

35. The circuit of claim 33, wherein the source of the fourth fet or the drain of the fifth fet is coupled to the output of the push-pull circuit through a resistor.

36. The circuit of claim 1, further comprising:

and the master control circuit is connected with the isolation circuit and is used for sending the control signal to the isolation circuit.

37. The circuit of claim 36, wherein the driving circuit is applied to a charger having a charging current greater than or equal to a preset current threshold.

38. The circuit of claim 37, wherein when the charger is used to charge a battery, the master control circuit is further configured to:

acquiring a charging request current of the battery, and determining the charging current of the charger according to the charging request current;

and determining a safe response time range of the channel switch according to the charging current so as to adjust the response time of the channel switch through the adjusting circuit according to the safe response time range.

39. The circuit of claim 38, wherein said determining a safe response time range for said channel switch from said charging current comprises:

and acquiring a preset mapping relation table between the charging current and the safety response time range, and inquiring the safety response time range corresponding to the charging current according to the mapping relation table to be used as the safety response time range of the channel switch.

40. A charger is characterized by comprising a main control circuit, at least one channel switch and a driving circuit for driving the channel switch to be switched on or switched off; the drive circuit includes:

a regulating circuit for regulating a response time of the channel switch;

41. The charger according to claim 40, wherein the isolation circuit comprises a control switch, and the control switch is connected to the preset power voltage and turned on or off according to the control signal to output the preset power voltage to the push-pull circuit, so as to generate the driving signal.

42. The charger according to claim 41, wherein the control switch comprises an optocoupler or a transformer.

43. The charger according to claim 40, wherein the push-pull circuit comprises two switching tubes of the same type and different polarities; one of the switch tubes is in a conducting state or a blocking state, and correspondingly, the other switch tube is in a blocking state or a conducting state.

44. The charger according to claim 43, wherein the switching tube comprises a triode or a field effect transistor.

45. The charger according to claim 44, wherein the two transistors are a first transistor and a second transistor, respectively, wherein the first transistor is an NPN transistor and the second transistor is a PNP transistor;

46. The charger of claim 45, wherein the control terminal of the push-pull circuit is coupled to ground through a third resistor.

47. The charger of claim 40, wherein the adjustment circuit comprises an adjustable resistor for adjusting a response time of the channel switch.

48. The charger of claim 45, wherein the adjustment circuit comprises a first adjustable resistance and a second adjustable resistance; one end of the first adjustable resistor is connected with the base electrode of the first triode, one end of the second adjustable resistor is connected with the base electrode of the second triode, and the other end of the first adjustable resistor is connected with the other end of the second adjustable resistor and connected with the isolation circuit.

49. The charger according to claim 40, wherein the regulating circuit comprises a resistor having a predetermined resistance value, the predetermined resistance value being determined according to a response parameter of a field effect transistor of the channel switch.

50. The charger of claim 40, further comprising:

51. The charger according to claim 50, wherein the isolated power module comprises:

a charge pump circuit;

52. The charger of claim 51, wherein the output voltage is equal to the input voltage.

53. The charger according to claim 51, wherein the charge pump circuit comprises: the pumping capacitor, the output capacitor connected with the power output end, the first switch module and the second switch module;

54. The charger of claim 53, wherein the charge pump circuit further comprises an input capacitor coupled to the power input, wherein the input capacitor is coupled in parallel with the pumping capacitor when the first switching module is closed.

55. The charger according to claim 54, wherein the pumping capacitance, the output capacitance and the input capacitance comprise: a ceramic capacitor.

56. The charging unit according to claim 53, wherein the first switching module comprises a first diode, an anode of the first diode is connected to the voltage source, and a cathode of the first diode is connected to the positive terminal of the pumping capacitor.

57. The electrical charger according to claim 56, wherein the second switching module comprises a second diode, an anode of the second diode being connected to the positive terminal of the pumping capacitor, and a cathode of the second diode being connected to the positive terminal of the output capacitor.

58. The charger according to claim 53, wherein the first switch module has a first control terminal, the first control terminal is configured to receive a first control signal, and the first switch module is controlled to be opened or closed by the first control signal.

59. The charger according to claim 58, wherein the first switch module comprises a first switch tube, and the first switch module is controlled to be switched on or off by the first control signal.

60. The charging unit according to claim 59, wherein the first switch tube comprises a first FET, a gate of the first FET is connected to the first control terminal, a drain of the first FET is connected to the negative terminal of the pumping capacitor, and a source of the first FET is grounded.

61. The electrical charger according to claim 60, wherein a resistor is provided between the gate and the source of the first FET.

62. The charger according to claim 53, wherein the second switch module has a second control terminal, the second control terminal is configured to receive a second control signal, and the second switch module is controlled to be opened or closed by the second control signal.

63. The charger according to claim 62, wherein the second switch module comprises a second switch tube and a third switch tube, the second switch tube is connected between the negative terminal of the pumping capacitor and the negative terminal of the output capacitor, and the second switch tube is controlled by the second control signal to control the third switch tube to be turned on or off.

64. The charger according to claim 63, wherein the second fet comprises a second fet and the third fet comprises a third fet, wherein the second fet comprises a PMOS transistor and the third fet comprises an NMOS transistor;

65. The electrical charger according to claim 64, wherein a resistor is provided between the gate and the source of the second FET and a resistor is provided between the gate and the source of the third FET.

66. The charger of claim 51, wherein the isolated power module further comprises a boost circuit for boosting the voltage of the voltage source.

67. The electrical charger according to claim 66, wherein said power input is connected to said voltage source through said boost circuit, said boost circuit providing a boosted voltage to said power input.

68. The charger of claim 50, wherein the first isolated power supply and the second isolated power supply have different voltages; and/or the presence of a gas in the gas,

the voltage of the second isolation power supply is related to the corresponding parameter of the field effect transistor of the channel switch.

69. The charger of claim 40, wherein the charger is provided with a charging position; alternatively, the first and second electrodes may be,

the charger is provided with a plurality of charging gears, and under each charging gear, the power supply equipment can be charged by corresponding current and/or voltage.

70. The electrical charger according to claim 40, wherein the channel switch comprises a fourth FET and a fifth FET, the fourth FET and the fifth FET being electrically coupled back to back.

71. The charger according to claim 70, wherein a drain of the fourth FET is connected to a first isolated power supply, a source of the fourth FET is connected to a drain of the fifth FET, and a gate of the fourth FET is connected to an output terminal of the push-pull circuit;

72. The charger according to claim 70, wherein the gate of the fourth FET is connected to the output terminal of the push-pull circuit through a first resistor, and the gate of the fifth FET is connected to the output terminal of the push-pull circuit through a second resistor.

73. The charger according to claim 72, wherein the magnitude of the resistance of the first resistor is related to a response parameter of the fourth FET for adjusting a response time of the fourth FET; and/or the resistance value of the second resistor is related to the response parameter of the fifth field effect transistor and is used for adjusting the response time of the fifth field effect transistor; and/or the presence of a gas in the gas,

and the source electrode of the fourth field effect transistor or the drain electrode of the fifth field effect transistor is connected with the output end of the push-pull circuit through a resistor.

74. The charger of claim 40, wherein a charging current of the charger is greater than or equal to a preset current threshold.

75. A charging control method applied to the charger according to any one of claims 40 to 74, the charging control method comprising:

76. A charger, comprising: one or more processors, working individually or collectively, to perform the charge control method of claim 75.