CN113049340A - Inductive coupling model for pulse current injection test system - Google Patents
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Abstract
An inductive coupling model for a pulse current injection test system is characterized in that a pulse source signal is input to an input end of an inductive coupling device through a transmission line, the input end is a primary loop of the coupling device, a coil in the loop is wound along the axial direction of a magnetic core, energy in the primary loop excites the magnetic flux of the magnetic core, pulse current is generated on a tested equipment cable of a secondary loop and is transmitted to the injection loop of the coupling device through a tested cable, and therefore the injection process of the pulse current is achieved. Is suitable for wide popularization and application.
Description
Technical Field
The invention relates to an inductive coupling model, in particular to an inductive coupling model for a pulse current injection test system.
Background
As is known, in a pulse current injection test system, a current injection coupling model is a very important part of the system, and the current output by a pulse source needs to enter a cable of a device to be tested through a coupling device. However, the GJB8848 specification does not provide specific requirements for the scheme of the coupling model, and how to provide an inductive coupling model for the pulsed current injection test system becomes a long-term technical appeal for those skilled in the art to meet the requirements of the PCI injection test.
Disclosure of Invention
In order to overcome the defects in the background art, the invention provides an inductive coupling model for a pulse current injection test system, which is applied to an inductive coupling device in a non-saturated state, and whether a magnetic core of the coupling device is saturated or not is verified according to a volt-second product formula after calculation.
In order to achieve the above purpose, the invention adopts the following technical scheme:
an inductive coupling model for a pulse current injection test system comprises a pulse source for generating high-voltage pulses, a transmission line between the pulse source and a coupling device, a coupling device primary loop, a coupling device secondary loop and a coupling device injection loop, wherein signals of the pulse source are input into the coupling device primary loop through the transmission line, a coil in the coupling device primary loop is wound along the axial direction of a magnetic core, energy in the coupling device primary loop excites the magnetic flux of the magnetic core, pulse current is generated on a tested cable in the coupling device secondary loop and is transmitted into the coupling device injection loop through the tested cable, and therefore the injection process of the pulse current is achieved.
The inductive coupling model for the pulse current injection test system is characterized in that the primary loop of the coupling device is a primary loop of the coupling device containing structural parameters, the primary loop of the coupling device containing the structural parameters is a primary winding of a magnetic core, the primary loop comprises three stray parameters including winding resistance, parasitic capacitance and parasitic inductance and self inductance of the primary winding, and the parasitic capacitance and the parasitic inductance generated by the winding are estimated by adopting a single ground power transmission line formula due to the equal distance from the winding in the winding to the metal shell, namely the parasitic capacitance and the parasitic inductance are estimated by adopting a single ground power transmission line formula, namely
In the formula, LwdParasitic inductance of the windings, CwdIs parasitic capacitance of winding, RwdIs a resistance of a wire winding,. lwdIs the length of the winding, rwdIs the winding radius, hwdIs the distance of the primary winding from the housing;
self-inductance of primary winding
The magnetic core is mainly determined by the complex permeability of the magnetic core and the winding structure, and is shown as the following formula:
in the formula
Complex magnetic permeability of the magnetic core; l is0Is a winding hollow inductor, i.e. an inductor with the same winding structure but with a vacuum core position, when the inductor is usedIn the structure of the sexual coupling device, an air core inductor L is wound0The following equation is obtained:
in the formula N1Is the number of primary winding turns; lfIs the thickness of the magnetic core; r isf1Is the inner radius of the magnetic core; r isf2The self-inductance is directly obtained for the outer radius of the magnetic core under the condition of known magnetic core materials and winding structures; when unknown, the impedance of the inlet is measured and obtained by using a de-embedding method.
The inductive coupling model for the pulse current injection test system is characterized in that a secondary loop of the coupling device comprises self inductance and leakage inductance of a secondary winding, and the number of primary turns of the pulse transformer model of the inductive coupling device is N1The number of secondary turns is N2Taking 1, since the secondary air gap is large, the secondary leakage inductance is mainly considered, and for simplifying the calculation, the magnetic material is considered as a boundary of the magnetic leakage integral calculation, and the leakage inductance can be calculated by the following formula:
in the formula, rf1Is the inner radius of the magnetic core, /)fIs the thickness of the magnetic core, rwFor the radius of the injected cable, the primary winding inductance, the secondary winding inductance and the mutual inductance have the following relationships:
in the formula N1Number of turns of primary winding, N2Is the number of turns of the secondary winding,
for the magnetic resistance, it is not necessary to know the magnetic resistance from the formula (14)
The self inductance and mutual inductance of the secondary winding can be calculated through the inductance of the primary winding.
The inductive coupling model for the pulse current injection test system is characterized in that the injection loop of the coupling device represents the part of the injected cable outside the coupling device and the loads at two ends of the injected cable, and the two-end transmission line and the Z-shaped transmission line are respectively usedL1And ZL2When the coupling process of the inductive coupling device is analyzed and solved, the inductive coupling device can be partially expressed in a chain parameter matrix form, and the transmission line, the winding stray parameter and the chain parameter matrix of the magnetic core coupling process can be respectively expressed as phiTL、ΦWDAnd phiFC；
The chain parameter matrixes are respectively as follows:
according to the chain parameter matrix, the relation of the voltage currents at the first end and the tail end of the inductive coupling device is obtained as follows:
according to the inductive coupling model for the pulse current injection test system, the external dimension of the inductive coupling device is 750mm multiplied by 185mm, and the inner diameter of the magnetic core is 90 mm.
In the inductive coupling model for the pulsed current injection test system, the magnetic core in the primary loop of the coupling device uses complex permeability to represent the frequency-variable characteristic of the magnetic material, wherein the magnetic material is represented by a series connection of a frequency-variable resistor and a frequency-variable inductor, and the input impedance of the magnetic core in the series connection model is as follows:
Zin(ω)＝Rf(ω)+jωLf(ω)
the complex permeability at this time is defined as:
in the formula, the real part μ' (ω) represents relative permeability, and the imaginary part μ ″ (ω) represents magnetic loss, for a magnetic core inductor L having an air core inductance0A core of the winding, the input impedance of the core being expressed as:
Zin(ω)＝jωL0[μ′(ω)-jμ″(ω)]＝ωL0μ″(ω)+jωL0μ′(ω)
Rf(ω)＝ωL0μ″(ω)
Lf(ω)＝L0μ′(ω)
when the hollow inductance of the winding is known, the real part and the imaginary part of the complex permeability are calculated by measuring the input impedance, when the input impedance of the magnetic core winding is measured, stray parameters are inevitably introduced into the winding, when the winding for measurement is selected, the stray parameters need to be smaller, the influence on the measurement result is reduced, and when the number of turns of the winding is larger, the stray capacitance is increased, so that the resonant frequency of the whole winding is reduced; when the winding distribution is scattered, the leakage inductance is increased, and the energy distribution of the magnetic core is uneven.
The inductive coupling model for the pulse current injection test system is characterized in that the winding is of a single-turn full-coverage structure, a copper-clad adhesive tape is wrapped outside the magnetic core to serve as a winding material, the material is tightly attached to the outer side of the magnetic core and a narrow gap is reserved only at the outer side of the magnetic core, and coaxial interfaces are led out of two sides of the gap to conduct measurement.
The inductive coupling model for the pulse current injection test system is characterized in that the magnetic core is of a single-turn full-coverage structure, the input impedance of the magnetic core is measured, the impedance is a winding parasitic parameter, and the real part of the impedance is a winding resistor RwImaginary part is hollow inductance L0Input impedance Z at the winding coreinMiddle deduction winding resistance RwThe effect of this component is compensated and the complex permeability is calculated according to the following equation:
Zin(ω)＝jωL0[μ′(ω)-jμ″(ω)]＝ωL0μ″(ω)+jωL0μ′(ω)；
according to the frequency range of the inductive coupling device model, input impedance of the magnetic core below 100MHz is measured by using a Wayne Kerr 6500B impedance measuring instrument (0-20MHz) and an AV36580A vector network analyzer (300kHz-3 GHz).
By adopting the technical scheme, the invention has the following advantages:
in the invention, a clock pulse source signal is input to the input end of an inductive coupling device through a transmission line, the input end is a primary loop of the coupling device, a coil in the loop is wound along the axial direction of a magnetic core, energy in the primary loop excites the magnetic flux of the magnetic core, and pulse current is generated on the tested equipment cable of the secondary loop and is transmitted to the coupling device through the tested cable to be injected into the loop, thereby realizing the injection process of the pulse current, the inductive coupling device adopts the idea of integrated design, at the moment, the magnetic ring of the coupler is a complete circular ring, the invention has the advantages that the magnetic core does not need to be cut, the aligned tangent plane does not exist, the installation and the fixation are facilitated, the invention is applied to the inductive coupling device in the unsaturated state, and after calculation, whether the magnetic core of the coupling device is saturated or not is verified according to a volt-second product formula, and the like, so that the method is suitable for large-scale popularization and application.
Drawings
FIG. 1 is a broad-band model of an inductive coupling device according to the present invention;
FIG. 2 is a schematic diagram of an inductive coupler according to the present invention;
FIG. 3 is a schematic diagram of an injection test configuration of an inductive coupling device according to the present invention;
FIG. 4 is a chain parameter matrix form of an inductive coupling device according to the present invention;
FIG. 5 is a frequency-dependent resistor-inductor series model of a magnetic material according to the present invention;
fig. 6 is a core winding model of the present invention that takes into account stray parameters.
Detailed Description
The present invention will be explained in more detail by the following examples, which are not intended to limit the invention;
the invention relates to an inductive coupling model for a pulse current injection test system, which comprises a pulse source for generating high-voltage pulses, a transmission line between the pulse source and a coupling device, a primary loop of the coupling device, a secondary loop of the coupling device and an injection loop of the coupling device, wherein signals of the pulse source are input into the primary loop of the coupling device through the transmission line, a coil in the primary loop of the coupling device is wound along the axial direction of a magnetic core, energy in the primary loop of the coupling device excites the magnetic flux of the magnetic core, pulse current is generated on a tested cable in the secondary loop of the coupling device and is transmitted into the injection loop of the coupling device through the tested cable, and therefore the injection process of the pulse current is realized.
The basic principle of the inductive coupling device of the present invention is as follows:
when the PCI test is performed, different injection coupling methods need to be adopted according to different test conditions, and generally, an inductive coupling device is used when the electrical contact cannot be achieved or the whole wiring harness cannot be separated and the whole common mode injection is performed. The coupler now behaves as a pulse transformer with only one turn on the secondary side, the principle of which is shown in fig. 2.
The inductive coupling device is composed of a magnetic core, a metal shell, a winding and the like, is generally designed into a caliper type, and can be regarded as the reverse use of the current measuring probe. The tested cable is usually placed in the center of the coupling device, when in use, a pulse source signal is input to the input end of the inductive coupling device through a high-voltage wire, the input end is a primary loop of the coupling device, a coil in the loop is wound along the axial direction of a magnetic core, energy in the primary loop excites the magnetic flux of the magnetic core, pulse current is generated on a tested equipment cable of a secondary loop and is transmitted to the inside of the tested equipment through the tested cable, and therefore the injection process of the pulse current is achieved.
The injection process of the inductive coupling device can be regarded as a broadband pulse transformer, and the main flux phi of the transformer0Magnetic coreClosing and interlinking with the primary winding (the winding of the injection clamp) and the secondary winding (the injected cable) is the most dominant process in inductive coupling. Leakage flux phi of primary winding1dOnly linked with the primary winding and closed along the air gap between the winding and the magnetic core; leakage magnetic flux phi of secondary winding2dCross-linked with the secondary winding (injected cable) but pass through a large air gap in the closure. Therefore, the leakage magnetic flux Φ of the secondary winding in the inductive coupling2dCompared to phi1dIs far more pronounced.
In view of the above analysis, the model parameters of the inductive coupling device should primarily take into account the magnetizing inductances of the primary and secondary windings, as well as the leakage inductances of the secondary windings. In addition, the parasitic capacitance and inductance of the structural elements of the coupling device also affect the performance of the inductive coupling device, and must be considered, so that a broadband model of the inductive coupling device can be built as shown in fig. 1. The inductive coupling model consists of five parts, namely a pulse source for generating high-voltage pulses, a transmission line between the pulse source and the coupling device, a primary loop of the coupling device including structural parameters, a secondary loop including secondary leakage inductance and an injection loop where a coupling load is located.
It is noted that the present invention is directed to the injection of a single wire by an inductive coupling device. The problem of common mode injection of multiple cables is greatly influenced by parameters such as cable distribution and the like, is complex, and is difficult to accurately model and solve the current distribution on each cable. For the multi-cable common-mode injection test, the sum of currents of the multi-cable relative to the ground is generally more concerned, so that an equivalent wiring harness method or a fast wiring harness equivalent model can be adopted to simplify the multi-cable into a single cable, a load matrix and the like into a single lumped load, and then an inductive coupling device model is used for researching the total current injected into a cable port. The inductive coupling device is mainly used for coupling double-exponential waves with single polarity, and the situations of large voltage and current, long waveform duration and easy occurrence of saturation are easily caused. The method is applied to the inductive coupling device in the unsaturated state, and whether the magnetic core of the coupling device is saturated or not is verified according to a volt-second product formula after calculation.
In the implementation of the present invention, the size of the inductive coupling device is usually within 1m, and for the high frequency injection pulse not exceeding 100MHz, the devices in the coupling device can be regarded as the collective parameters, so the wave process inside the inductive coupling device is not considered. The loop model of the inductive coupling device comprises a transmission line, a primary loop, a secondary loop and the like, and a pulse waveform generated by a pulse source enters a primary winding of the coupling device through the transmission line. The transmission line generally adopts a high-voltage coaxial line or adopts a mode that the high-voltage line and the ground line are respectively connected, the coaxial line is easy to control the impedance to be uniform, and the distortion to the waveform is small.
In implementation, the primary loop of the coupling device is a primary loop of the coupling device containing structural parameters, the primary loop of the coupling device containing the structural parameters is a primary winding of a magnetic core, the primary loop comprises three stray parameters of winding resistance, parasitic capacitance and parasitic inductance and self inductance of the primary winding, and the distances from windings in the windings to a metal shell are equal, so that the parasitic capacitance and the parasitic inductance generated by the windings are estimated by adopting a single-ground-based power transmission line formula, namely the parasitic capacitance and the parasitic inductance are estimated by adopting a single-ground-based power transmission line formula
In the formula, LwdParasitic inductance of the windings, CwdIs parasitic capacitance of winding, RwdIs a resistance of a wire winding,. lwdIs the length of the winding, rwdIs the winding radius, hwdIs the distance of the primary winding from the housing;
self-inductance of primary winding
The magnetic core is mainly determined by the complex permeability of the magnetic core and the winding structure, and is shown as the following formula:
in the formula
Complex magnetic permeability of the magnetic core; l is0In the case of a wound air core inductor, i.e. an inductor of the same winding structure but with a vacuum core position, the wound air core inductor L is constructed in the case of an inductive coupling device0The following equation is obtained:
in the formula N1Is the number of primary winding turns; lfIs the thickness of the magnetic core; r isf1Is the inner radius of the magnetic core; r isf2The self-inductance is directly obtained for the outer radius of the magnetic core under the condition of known magnetic core materials and winding structures; when unknown, the impedance of the inlet is measured and obtained by using a de-embedding method.
Further, the secondary loop of the coupling device comprises self inductance and leakage inductance of the secondary winding, and the number of primary turns is N for a pulse transformer model of the inductive coupling device1The number of secondary turns is N2Taking 1, since the secondary air gap is large, the secondary leakage inductance is mainly considered, and for simplifying the calculation, the magnetic material is considered as a boundary of the magnetic leakage integral calculation, and the leakage inductance can be calculated by the following formula:
in the formula, rf1Is the inner radius of the magnetic core, /)fIs the thickness of the magnetic core, rwFor the radius of the injected cable, the primary winding inductance, the secondary winding inductance and the mutual inductance have the following relationships:
in the formula N1Number of turns of primary winding, N2Is the number of turns of the secondary winding,
for the magnetic resistance, it is not necessary to know the magnetic resistance from the formula (14)
The self inductance and mutual inductance of the secondary winding can be calculated through the inductance of the primary winding.
Furthermore, the injection loop of the coupling device represents the part of the injected cable outside the coupling device and the load at two ends, and respectively uses a two-end transmission line and a ZL1And ZL2When the coupling process of the inductive coupling device is analyzed and solved, the inductive coupling device can be partially expressed in a chain parameter matrix form, and the transmission line, the winding stray parameter and the chain parameter matrix of the magnetic core coupling process can be respectively expressed as phiTL、ΦWDAnd phiFCAs shown in fig. 4 in particular;
the chain parameter matrixes are respectively as follows:
according to the chain parameter matrix, the relation of the voltage currents at the first end and the tail end of the inductive coupling device is obtained as follows:
further, with the thinking of inductive coupling device adoption integral type design, the magnetic ring of this coupler is complete ring this moment, and its advantage lies in that does not need to cut the magnetic core, does not have the alignment tangent plane yet, and does benefit to installation and fixed, wraps up the nylon shell outside the magnetic ring, and the outermost end lining is with metal casing in order to guarantee intensity. The winding and the high-voltage pulse wire are both high-voltage wires (wire diameter is 1 mm)2150kV direct currentWithstand voltage), the winding and the high-voltage pulse line are the same continuous high-voltage line in consideration of insulation at the inlet, and no high voltage is exposed except for the pulse source interface. The high-voltage pulse line is characterized in that two silica gel lines are arranged in parallel, the characteristic impedance is kept consistent, and the waterproof joint is adopted to fix the high-voltage pulse line at the inlet of the coupler. The two ends of the coupler use nylon parts to fix the winding, the front and back sliding is prevented, and the winding is fixed through a wire slot in the middle. The external dimension of the inductive coupling device is 750mm multiplied by 185 mm; the diameter in the magnet core is 90mm, wherein the available inner diameter exceeds 75mm, and the injection test of more than 5 injected cables can be accommodated. The shell is treated by grey spraying plastics. The input of the inductive coupling device is two high-voltage cables, wherein the red cable is connected to the high-voltage output of the pulse source, and the black cable is grounded.
Further, the magnetic core in the primary loop of the coupling device uses complex permeability to represent the frequency-dependent characteristic of the magnetic material, where the magnetic material is represented by a series connection of a frequency-dependent resistor and a frequency-dependent inductor (as shown in fig. 5 in particular), and the input impedance of the magnetic core in the series connection model is:
Zin(ω)＝Rf(ω)+jωLf(ω)
the complex permeability at this time is defined as:
in the formula, the real part μ' (ω) represents relative permeability, and the imaginary part μ ″ (ω) represents magnetic loss, for a magnetic core inductor L having an air core inductance0A core of the winding, the input impedance of the core being expressed as:
Zin(ω)＝jωL0[μ′(ω)-jμ″(ω)]＝ωL0μ″(ω)+jωL0μ′(ω)
Rf(ω)＝ωL0μ″(ω)
Lf(ω)＝L0μ′(ω)
when the winding air core inductance is known, the real part and the imaginary part of the complex permeability are calculated by measuring the input impedance, so that accurate measurement of the core input impedance and the winding air core inductance is the key to calculating the complex permeability. When input impedance measurements are made on the core winding, the winding inevitably introduces stray parameters, and a model of the core winding that takes into account the stray parameters is shown in fig. 6.
In FIG. 6LdFor leakage inductance, LwParasitic inductance of the windings, CwIs parasitic capacitance of winding, RwIs the resistance of the wire. These parameters are related to the winding structure dimensions. When the winding for measurement is selected, the stray parameters are made to be smaller as much as possible, and the influence on the measurement result is reduced. In particular, when the number of winding turns is large, the parasitic capacitance becomes large, so that the resonance frequency of the entire winding decreases; when the winding distribution is scattered, the leakage inductance is increased, and the energy distribution of the magnetic core is uneven.
In consideration of the characteristics, the invention adopts the winding with a single-turn full-coverage structure, namely, the copper-clad adhesive tape is coated outside the magnetic core as the winding material, the material is tightly attached, a narrow gap is reserved only at the outer side, and the coaxial interfaces are led out from the two sides of the gap for measurement. In the structure, the winding almost completely covers the magnetic core, so that the leakage inductance, parasitic inductance and parasitic capacitance are small and can be ignored.
Selecting a nylon skeleton with the same size as the magnetic core, and measuring the input impedance of the winding by adopting a single-turn full-coverage structure as the magnetic core. The impedance is a winding parasitic parameter, and further, the real part of the impedance is a winding resistance RwImaginary part is hollow inductance L0. Input impedance Z at winding coreinMiddle deduction winding resistance RwThe effect of this part is compensated. According to the formula Zin(ω)＝jωL0[μ′(ω)-jμ″(ω)]＝ωL0μ″(ω)+jωL0μ' (ω) was calculated as complex permeability. According to the frequency range of the inductive coupling device model, the input impedance of the magnetic core below 100MHz can be measured by using a Wayne Kerr 6500B impedance measuring instrument (0-20MHz) and an AV36580A vector network analyzer (300kHz-3 GHz).
The present invention is not described in detail in the prior art.
The embodiments selected for the purpose of disclosing the invention, are presently considered to be suitable, it being understood, however, that the invention is intended to cover all variations and modifications of the embodiments which fall within the spirit and scope of the invention.
Claims (8)
1. An inductive coupling model for a pulsed current injection test system, comprising a pulse source for generating high voltage pulses, a transmission line between the pulse source and a coupling device, a primary loop of the coupling device, a secondary loop of the coupling device and an injection loop of the coupling device, characterized in that: the signal of the pulse source is input into a primary loop of the coupling device through a transmission line, a coil in the primary loop of the coupling device is wound along the axial direction of a magnetic core, energy in the primary loop of the coupling device excites the magnetic flux of the magnetic core, pulse current is generated on a tested cable in a secondary loop of the coupling device and is transmitted into an injection loop of the coupling device through the tested cable, and therefore the injection process of the pulse current is achieved.
2. The inductive coupling model for a pulsed current injection testing system according to claim 1, wherein: the primary loop of the coupling device is a primary loop of the coupling device containing structural parameters, the primary loop of the coupling device containing the structural parameters is a primary winding of a magnetic core, the primary loop comprises three stray parameters of winding resistance, stray capacitance and stray inductance and self inductance of the primary winding, and the distances from windings in the windings to a metal shell are equal, so the stray capacitance and the stray inductance generated by the windings are estimated by adopting a single-earth power transmission line formula, namely the parasitic capacitance and the stray inductance are estimated by adopting a single-earth power transmission line formula
In the formula, LwdParasitic inductance of the windings, CwdIs parasitic capacitance of winding, RwdIs a resistance of a wire winding,. lwdIs the length of the winding, rwdIs the winding radius, hwdIs the distance of the primary winding from the housing;
self-inductance of primary winding
The magnetic core is mainly determined by the complex permeability of the magnetic core and the winding structure, and is shown as the following formula:
in the formula
Complex magnetic permeability of the magnetic core; l is0In the case of a wound air core inductor, i.e. an inductor of the same winding structure but with a vacuum core position, the wound air core inductor L is constructed in the case of an inductive coupling device0The following equation is obtained:
in the formula N1Is the number of primary winding turns; lfIs the thickness of the magnetic core; r isf1Is the inner radius of the magnetic core; r isf2The self-inductance is directly obtained for the outer radius of the magnetic core under the condition of known magnetic core materials and winding structures; when unknown, the impedance of the inlet is measured and obtained by using a de-embedding method.
3. The inductive coupling model for a pulsed current injection testing system according to claim 1, wherein: the secondary loop of the coupling device comprises the self inductance and leakage inductance of the secondary winding, and the number of primary turns is N for a pulse transformer model of the inductive coupling device1The number of secondary turns is N2Taking 1, since the secondary air gap is large, the secondary leakage inductance is mainly considered, and for simplifying the calculation, the magnetic material is considered as a boundary of the magnetic leakage integral calculation, and the leakage inductance can be calculated by the following formula:
in the formula (I), the compound is shown in the specification,rf1is the inner radius of the magnetic core, /)fIs the thickness of the magnetic core, rwFor the radius of the injected cable, the primary winding inductance, the secondary winding inductance and the mutual inductance have the following relationships:
in the formula N1Number of turns of primary winding, N2Is the number of turns of the secondary winding,
for the magnetic resistance, it is not necessary to know the magnetic resistance from the formula (14)
The self inductance and mutual inductance of the secondary winding can be calculated through the inductance of the primary winding.
4. The inductive coupling model for a pulsed current injection testing system according to claim 1, wherein: the injection loop of the coupling device represents the part of the injected cable outside the coupling device and the load at two ends, and respectively uses a two-end transmission line and a ZL1And ZL2When the coupling process of the inductive coupling device is analyzed and solved, the inductive coupling device can be partially expressed in a chain parameter matrix form, and the transmission line, the winding stray parameter and the chain parameter matrix of the magnetic core coupling process can be respectively expressed as phiTL、ΦWDAnd phiFC；
The chain parameter matrixes are respectively as follows:
according to the chain parameter matrix, the relation of the voltage currents at the first end and the tail end of the inductive coupling device is obtained as follows:
5. the inductive coupling model for a pulsed current injection testing system according to claim 1, wherein: the external dimensions of the inductive coupling device are 750mm x 185mm, and the inner diameter of the magnetic core is 90 mm.
6. The inductive coupling model for a pulsed current injection testing system according to claim 1, wherein: the magnetic core in the primary loop of the coupling device uses complex permeability to express the frequency-variable characteristic of a magnetic material, wherein the magnetic material is expressed by the series connection of a frequency-variable resistor and a frequency-variable inductor, and the input impedance of the magnetic core in a series connection model is as follows:
Zin(ω)＝Rf(ω)+jωLf(ω)
the complex permeability at this time is defined as:
in the formula, the real part μ' (ω) represents relative permeability, and the imaginary part μ ″ (ω) represents magnetic loss, for a magnetic core inductor L having an air core inductance0A core of the winding, the input impedance of the core being expressed as:
Zin(ω)＝jωL0[μ′(ω)-jμ″(ω)]＝ωL0μ″(ω)+jωL0μ′(ω)
Rf(ω)＝ωL0μ″(ω)
Lf(ω)＝L0μ′(ω)
when the hollow inductance of the winding is known, the real part and the imaginary part of the complex permeability are calculated by measuring the input impedance, when the input impedance of the magnetic core winding is measured, stray parameters are inevitably introduced into the winding, when the winding for measurement is selected, the stray parameters need to be smaller, the influence on the measurement result is reduced, and when the number of turns of the winding is larger, the stray capacitance is increased, so that the resonant frequency of the whole winding is reduced; when the winding distribution is scattered, the leakage inductance is increased, and the energy distribution of the magnetic core is uneven.
7. The inductive coupling model for a pulsed current injection testing system according to claim 6, wherein: the winding is of a single-turn full-coverage structure, a copper-clad adhesive tape is wrapped outside the magnetic core to serve as a winding material, the material is tightly attached to the outer side of the winding, a narrow gap is reserved only at the outer side of the winding, and coaxial interfaces are led out of two sides of the gap to conduct measurement.
8. The inductive coupling model for a pulsed current injection testing system according to claim 7, wherein: the magnetic core is a single-turn full-coverage structure, the input impedance of the magnetic core is measured, the impedance is a winding parasitic parameter, and the real part of the impedance is a winding resistance RwImaginary part is hollow inductance L0Input impedance Z at the winding coreinMiddle deduction winding resistance RwThe effect of this component is compensated and the complex permeability is calculated according to the following equation:
Zin(ω)＝jωL0[μ′(ω)-jμ″(ω)]＝ωL0μ″(ω)+jωL0μ′(ω)；
according to the frequency range of the inductive coupling device model, input impedance of the magnetic core below 100MHz is measured by using a Wayne Kerr 6500B impedance measuring instrument (0-20MHz) and an AV36580A vector network analyzer (300kHz-3 GHz).
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