CN112887230B - Channel estimation method of space-time block coding MSK system under flat fading channel - Google Patents

Channel estimation method of space-time block coding MSK system under flat fading channel Download PDF

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CN112887230B
CN112887230B CN202110022932.6A CN202110022932A CN112887230B CN 112887230 B CN112887230 B CN 112887230B CN 202110022932 A CN202110022932 A CN 202110022932A CN 112887230 B CN112887230 B CN 112887230B
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CN112887230A (en
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张学达
孙锦华
张春晖
郑浩然
刘玉涛
魏萌
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Xidian University
CETC 54 Research Institute
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    • H04L25/0224—Channel estimation using sounding signals
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    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
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    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0204—Channel estimation of multiple channels
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    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
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Abstract

The invention discloses a channel estimation method of a space-time block coding (MSK) system under a flat fading channel, which mainly solves the problems of inaccurate response estimation of the flat fading channel and higher complexity of a receiver in the conventional STBC-MSK system. The implementation scheme is as follows: 1) dividing an initial bit sequence generated by a transmitting end into a plurality of data blocks; 2) adding a phase continuous symbol at the tail of the data block to obtain a pre-modulation sequence; 3) decomposing the pre-modulation sequence into amplitude modulation pulse signals to obtain modulation signals; 4) carrying out STBC coding on the modulation signal, and adding a training sequence to obtain a transmitting signal; 5) transmitting signals to a receiving end through a flat fading channel; 6) and calculating the reliability variable of the training sequence at the receiving end, and estimating the channel response in sections. The invention improves the channel estimation precision and reduces the complexity, and can be used for signal transmission in the minimum frequency shift keying STBC-MSK system under the space-time block coding.

Description

Channel estimation method of space-time block coding MSK system under flat fading channel
Technical Field
The invention belongs to the technical field of communication, and particularly relates to a channel estimation method which can be used for signal transmission in a minimum frequency shift keying STBC-MSK system under space-time block coding.
Background
The minimum frequency shift keying (MSK) modulation mode is a modulation mode which is very advantageous under a nonlinear band-limited channel. The phase is continuous, phase jump can not occur during symbol switching, so that the side lobe of the power spectrum is attenuated quickly, the power spectrum is mainly concentrated in the main lobe, the interference of the side lobe on signals of adjacent frequency bands is small, and the utilization efficiency of the frequency band is high. Meanwhile, the phase carries transmission bit information, so that the system performance is insensitive to the attenuation of the signal amplitude.
M.P Fitz and X.Zhang put forward a space-time trellis coding (STTC) coding mode in 2003, which is applied to an MIMO-CPM system, and constructs a coding mode under the condition of Rayleigh flat fading channel, and in addition, the two people also put forward a calculation method for measuring the symmetric information rate of the MIMO system performance as the lower bound of the channel capacity, and a joint channel estimation algorithm and a data detection method aiming at soft output. Space-time trellis coding, however, introduces greater complexity to the system receiver.
Shenli introduces a predistortion circuit for processing aiming at the nonlinearity of a channel of the MIMO system, and researches a symbol timing synchronization method of the MIMO-CPM system. In forestry, chenghandong et al, further extend the OST-CPM coding method of g.y.wang to any number of antennas, and prove from the aspect of rank criterion that the OST-CPM system has complete diversity gain, and further research the non-coherent demodulation algorithm of the OST-CPM system, but these methods do not discuss the problem of CPM signal phase continuity during coding, and the phase discontinuity may affect the orthogonality of the transmitted signal on the transmitting antennas, so that the signal may be subject to self-interference during transmission, which affects the system receiving error performance.
G.y.wang et al propose an orthogonal-like construction method similar to Alamouti orthogonal space-time coding, which can use orthogonal space-time coding continuous phase modulation OST-CPM transmitted by two antennas to combat flat fading channels. But the construction method thereof increases the channel estimation complexity, and the STBC-MSK system can estimate the flat fading channel at the receiving end of the system and reduce the calculation complexity due to the characteristic of the coding block. The beam-Han-Sai researches the STBC-MSK coding structure and carries out channel estimation at the receiving end, but the channel estimation method adopts integral average, so that the channel response precision is low and the system error code performance is poor.
Disclosure of Invention
The invention aims to provide a channel estimation method of a space-time block coding MSK system under a flat fading channel aiming at the defects of the prior art so as to improve the channel response precision and the system error code performance.
The technical idea of the invention is as follows: the initial bit sequence is processed in a blocking mode at a sending end, a phase return-to-zero symbol is added, amplitude modulation pulse decomposition is carried out, STBC coding is carried out, and a training sequence credibility variable is introduced to a receiving end to carry out sectional estimation on channel response.
According to the above thought, the implementation steps of the invention include the following:
(1) randomly generating a data frame with length of L bits at a transmitting end of a space-time coding minimum frequency shift keying STBC-MSK system
Figure BDA0002889302550000021
Duration per bit of Ts；
(2) The data frame is partitioned into two transmitting antennas to obtain the data frame of each antenna
Figure BDA0002889302550000022
Has a length of
Figure BDA0002889302550000023
Dividing the data frame on each antenna into three sub-data blocks
Figure BDA0002889302550000024
Calculating phase continuation symbols d from the three sub-data blocks respectivelyxAdding phase continuous symbols to the tail of each subdata block to obtain the 1 st antenna premodulation data block
Figure BDA0002889302550000025
Figure BDA0002889302550000025
2 nd antenna premodulation data block
Figure BDA0002889302550000026
(3) For the pre-modulated data block after adding phase continuous symbols
Figure BDA0002889302550000027
And
Figure BDA0002889302550000028
amplitude modulation pulse decomposition is carried out to obtain modulation signals s on two antennasm,1(t)、sm,2(t)；
(4) Modulating signals s on two antennasm,1(t)、sm,2(t) the heads are each added with a length LcpTo obtain sm1(t)、sm2(t); and to sm1(t)、sm2(t) performing STBC coding to obtain a transmission signal s on the 1 st antenna1(t) and the transmitted signal s on the 2 nd antenna2(t)；
(5) Transmitting signal s on the 1 st transmitting antenna1(t) adding a training sequence p before1(t), obtaining the transmitting signal s with training sequence on the 1 st transmitting antennap1(t) transmitting signal s on the 2 nd transmitting antenna2(t) adding a training sequence p before2(t), obtaining the transmitting signal s with training sequence on the 2 nd transmitting antennap2(t) wherein p1(t)、p2(t) all have a length of Lp；
(6) Transmitting signals s with training sequences on two transmitting antennasp1(t) and sp2(t) obtaining a receiving signal r (t) on a receiving antenna at a receiving end through a flat fading channel;
r(t)＝h1sp1(t)+h2sp2(t)+n(t)
h1for the 1 st transmitting antenna to receiving antenna flat fading channel response, h2Is as followsFlat fading channel response of 2 transmitting antennas to receiving antennas;
(7) using training sequence of received signal r (t) on receiving antenna to make channel estimation:
(7a) dividing the training sequence p (t) on the received signal into
Figure BDA0002889302550000031
Segment interval with duration of 2TsCalculating the confidence level delta of the nth section of the training sequence p (t) on the received signali,n：
Figure BDA0002889302550000032
Figure BDA0002889302550000033
(7b) The reliability δ obtained from (7a)i,nTraining sequence p in (1) and (5)1(t)、p2And (t) calculating the average channel response estimated value from the ith transmitting antenna to the receiving antenna according to the received signal r (t) in (t) and (6)
Figure BDA0002889302550000034
Figure BDA0002889302550000035
Compared with the prior art, the invention has the following advantages:
firstly, the method comprises the following steps: because the invention introduces the pulse amplitude decomposition before the STBC coding of the signal, the complexity of the receiving end is reduced compared with the prior Viterbi demodulation while approaching the CPM signal as much as possible, the realization is simple, and the simulation result shows that the signal decomposed by the amplitude modulation pulse is completely consistent with the signal generated by the original MSK modulation, and the energy is not lost after the approach.
Secondly, the method comprises the following steps: the invention combines the STBC block coding requirement and the CPM signal characteristic to add the phase continuous symbol, maintains the MSK signal phase continuity, and simultaneously reduces the reduction of the frequency spectrum utilization rate caused by adding the phase continuous symbol to the maximum extent.
Thirdly, the method comprises the following steps: when the invention estimates the flat fading channel by using the training sequence, the channel estimation is more accurate because the training sequence credibility is introduced to take weighted average for the received training sequence segmental estimation, and the channel fading factor obtained by estimation is used for restoring the transmitted signal at the receiving end, so that the signal-to-noise ratio of the improved channel estimation is improved by 0.2dB compared with the signal-to-noise ratio when the bit error rate of the existing channel estimation reaches 10 e-6.
Drawings
FIG. 1 is a diagram of a MIMO-MSK system scenario for use with the present invention;
FIG. 2 is a flow chart of an implementation of the present invention;
FIG. 3 is a time comparison of the present invention with a prior art channel estimation;
FIG. 4 is a graph comparing an AM pulse decomposition modulated signal of the present invention with a conventional MSK modulated signal;
fig. 5 is a comparison of error performance curves of the channel estimation of the present invention and the existing channel estimation algorithm.
Detailed Description
Embodiments and effects of the present invention will be further described below with reference to the accompanying drawings.
Referring to fig. 1, an application scenario of this example is a MIMO-MSK system model, where the system includes a transmitting end and a receiving end, and a flat fading channel is used as a channel. Wherein:
the transmitting end sequentially adds phase continuous symbols, amplitude modulation pulse decomposition and STBC coding to a binary data bit sequence, adds a cyclic prefix and finally adds a training sequence to form a transmitting signal;
at a receiving end, performing channel estimation by using the received signal;
referring to fig. 2, the specific implementation steps of this example are as follows:
step 1, generating a transmitted modulation signal.
(1.1) constructing a randomly generated binary bit sequence data frame at a transmitting end
Figure BDA0002889302550000041
Duration per bit of TsThe bit sequence
Figure BDA0002889302550000042
The length L is 3994 bits,
Figure BDA0002889302550000043
expressed as:
Figure BDA0002889302550000044
wherein d ishTo represent
Figure BDA0002889302550000045
The h-th bit;
(1.2) data frame constructed by (1.1)
Figure BDA0002889302550000046
Performing block processing with length of each block being Ld1997, cyclic prefix length LcpGet 400 data frame on the 1 st transmitting antenna
Figure BDA0002889302550000047
Data frame on 2 nd transmitting antenna
Figure BDA0002889302550000048
Then will be
Figure BDA0002889302550000049
Each divided into three sub-data blocks:
Figure BDA00028893025500000410
Figure BDA00028893025500000411
wherein, the 1 st sub-data block of the 1 st transmitting antenna is set as:
Figure BDA00028893025500000412
in the formula diTo represent
Figure BDA00028893025500000413
The ith bit in the bit, i is more than or equal to 1 and less than or equal to Lcp-1；
The 2 nd sub data block of the 1 st transmitting antenna is set as:
Figure BDA00028893025500000414
in the formula djTo represent
Figure BDA00028893025500000415
Middle j-th bit, Lcp≤j≤Ld-Lcp+1；
The 3 rd sub-data block of the 1 st transmitting antenna is set as:
Figure BDA00028893025500000416
in the formula dkTo represent
Figure BDA00028893025500000417
Middle k bit, Ld-Lcp+2≤k≤Ld；
The 1 st sub-data block of the 2 nd transmitting antenna is set as:
Figure BDA0002889302550000051
in the formula dlTo represent
Figure BDA0002889302550000052
Middle L bit, Ld+1≤l≤Ld+Lcp-1；
The 2 nd sub data block of the 2 nd transmitting antenna is set as:
Figure BDA0002889302550000053
in the formula dmTo represent
Figure BDA0002889302550000054
M-th bit, Ld+Lcp≤m≤2Ld-Lcp+1；
The 3 rd sub-data block of the 2 nd transmitting antenna is set as:
Figure BDA0002889302550000055
in the formula dnTo represent
Figure BDA0002889302550000056
Middle nth bit 2Ld-Lcp+2≤n≤2Ld；
(1.3) calculating the phase continuation symbol dxPhase continuation symbol at tail of ith sub-data block on nth transmitting antenna
Figure BDA0002889302550000057
Figure BDA0002889302550000058
Wherein
Figure BDA0002889302550000059
For the L bit, L, of the ith sub-data block on the nth transmitting antennan,iThe length of the ith sub-data block on the nth transmitting antenna is obtained;
(1.4) addition of dxThe pre-modulated data sequence on the 1 st transmitting antenna
Figure BDA00028893025500000510
And 2 pre-modulation data sequence on transmitting antenna
Figure BDA00028893025500000511
The following were used:
Figure BDA00028893025500000512
Figure BDA00028893025500000513
(1.5) carrying out pulse amplitude decomposition on the premodulation data added with the phase continuous symbols to obtain the 1 st antenna modulation signal sm,1(t) and 2 nd antenna modulation signal sm,2(t) are respectively represented as follows:
Figure BDA00028893025500000514
Figure BDA00028893025500000515
wherein
Figure BDA00028893025500000516
Denotes the modulation index, Lo＝Ld+ 3-2000 denotes the modulation signal length,
Figure BDA00028893025500000517
to represent
Figure BDA00028893025500000518
The upper i-th bit of the data,
Figure BDA00028893025500000519
to represent
Figure BDA00028893025500000520
Upper ith bit, c0(t) is a shaping function, expressed as follows:
Figure BDA0002889302550000061
(1.6) the tail length of the modulation signal on the first transmitting antenna is LcpData of 400 is copied as cyclic prefix to the 1 st transmitting antenna modulation signalHeader portion for obtaining a modulated signal s to which a cyclic prefix is addedm1(t)：
Figure BDA0002889302550000062
Modulating the 2 nd transmitting antenna with the tail length of LcpThe data is copied to the head of the modulation signal of the 2 nd transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm2(t)：
Figure BDA0002889302550000063
(1.7) adding the cyclic prefix to the 1 st transmitting antennam1(t) and modulated signal s with cyclic prefix added to 2 nd transmitting antennam2(t) space-time block coding to obtain the transmission signal s on the 1 st transmitting antenna1(t) and the transmission signal s on the 2 nd transmitting antenna2(t)，s1(t)、s2(t) are respectively represented as follows:
s1(t)＝[sm1(t) sm2(t)]
Figure BDA0002889302550000064
and 2, adding training sequences to the transmitting signals of the two transmitting antennas.
(2.1) the lengths produced are all LpDuration of Tp＝LpTsThe 1 st transmitting antenna transmits a training sequence p of signals1(t) and training sequence p of the 2 nd transmitting antenna transmitting signal2(t), the training sequence in this example is:
[1,-1,1,-1,...,1,-1]，Lp＝100；
(2.2) transmitting the signal s at the 1 st transmitting antenna1(t) and 2 nd transmitting antenna transmitting signal s2Before (t), the training sequences generated in (2.1) are added respectively to obtain the 1 st transmitting antennaHas a transmitted signal s with a training sequencep1(t) and the transmitted signal s with training sequence on the 2 nd transmitting antennap2(t)：
sp1(t)＝[p1(t) s1(t)]
sp2(t)＝[p2(t) s2(t)]。
Step 3, obtaining a receiving signal r (t) on a receiving antenna
Transmitting signal s with training sequence on the 1 st transmitting antennap1(t) flat fading channel response h to receive antenna via the 1 st transmit antenna1Reaches a receiving antenna to obtain a signal h after fading channel response1sp1(t)；
Transmitting signal s with training sequence on 2 nd transmitting antennap2(t) flat fading channel response h to receive antenna via 2 nd transmit antenna2Reaches a receiving antenna to obtain a signal h after fading channel response2sp2(t)；
The receiving antenna superposes the signals of the two transmitting antennas after the flat fading channel response to obtain a receiving signal r (t);
r(t)＝h1sp1(t)+h2sp2(t)+n(t)
wherein n (t) is additive white Gaussian noise.
And 4, the receiving end obtains the received signal and estimates the channel.
In an emulated system, the experienced fading channel response h1、h2Unknown and not directly measurable, but the receiving signal after passing through the flat fading channel can be obtained on the receiving antenna of the receiving end, and the training sequence p (t) of the receiving signal and the training sequence p of the transmitting signal on the ith transmitting antenna can be utilizedi(t) estimating the fading channel response, which is achieved as follows:
(4.1) dividing the training sequence p (t) on the received signal into
Figure BDA0002889302550000071
Segment interval with duration of 2TsCalculating the reliability delta between the n-th segments of the training sequence p (t) on the received signali,n：
Figure BDA0002889302550000072
Figure BDA0002889302550000073
Wherein p isi(t) is the training sequence of the nth interval on the ith transmitting antenna, and p (t) is the training sequence of the nth interval on the receiving signal;
(4.2) calculating the estimated channel response of the ith transmitting antenna to the receiving antenna under the condition of neglecting the influence of noise
Figure BDA0002889302550000074
Figure BDA0002889302550000075
Wherein L ispFor the length of the transmit-end training sequence, pi(T) is the training sequence on the ith transmit antenna, r (T) is the received signal on the receive antenna, TsFor each duration of a bit of the data stream,
Figure BDA0002889302550000081
is the conjugate of the training sequence on the ith transmit antenna.
The effects of the present invention can be further illustrated by the following simulations:
firstly, setting simulation system parameters
MATLAB R2020a simulation software is used, the MIMO-MSK system is a double-transmitting single-receiving system, and the length of original data of a transmitting end is 3994 bits; the training sequence length is 100 bits, the cyclic prefix length is 400 bits, and the duration of each bit is 2 x 10 e-7.
The multipath channel parameters apply flat fading to the signal using the comm.
Second, simulation content
Simulation 1, comparing the running time of the channel estimation of the present invention with the existing STBC coding channel estimation system under the conditions of signal-to-noise ratio of 1dB, 2dB, 3dB, 4dB, 5dB, 6dB, the result is shown in FIG. 3.
As can be seen from fig. 3, the existing channel estimation running time exceeds the channel estimation algorithm of the present invention by 30% in the case of a signal-to-noise ratio of 5dB, and exceeds the estimation algorithm running time of the present invention by 40% in the case of 6dB, indicating that the estimation time of the present invention is short.
Simulation 2 compares the am-pwm signal with the existing MSK signal under the condition of a signal-to-noise ratio of 6dB, and the result is shown in fig. 4. It can be seen from fig. 4 that the two modulation signals are completely identical, which indicates that the modulation signal obtained after the decomposition of the amplitude modulation pulse of the present invention has no loss of energy with the original MSK modulation signal.
Simulation 3, comparing the error code performance of the channel estimation method of the invention and the existing channel estimation method on the MIMO-MSK system under the condition of the signal-to-noise ratio of 1dB to 12dB, the result is shown in FIG. 5.
As can be seen from FIG. 5, the error code performance of the channel estimation of the invention is better than that of the existing channel estimation algorithm, when the signal-to-noise ratio is 10dB, the signal-to-noise ratio is improved by 0.2dB when the error code rate of the channel estimation of the invention reaches 10e-6 compared with the existing channel estimation, which shows that the channel response estimated by the invention is more accurate.

Claims (7)

1. A channel estimation method based on a space-time block coding (MSK) system under a flat fading channel is characterized by comprising the following steps:
(1) randomly generated data frame with length of L bits at transmitting end of space-time coding minimum frequency shift keying STBC-MSK system
Figure FDA0003301872360000011
Duration per bit of Ts；
(2) The data frame is partitioned into two transmitting antennas to obtain the data frame of each antenna
Figure FDA0003301872360000012
Has a length of
Figure FDA0003301872360000013
Dividing the data frame on each antenna into three sub-data blocks
Figure FDA0003301872360000014
And calculating and adding phase continuation symbols at the tail of each sub-data block
Figure FDA0003301872360000015
Obtaining the 1 st antenna premodulation data block
Figure FDA0003301872360000016
2 nd antenna premodulation data block
Figure FDA0003301872360000017
Wherein the phase continuation symbol added at the tail of each sub data block
Figure FDA0003301872360000018
Is determined by the following formula:
Figure FDA0003301872360000019
wherein
Figure FDA00033018723600000110
For the ith bit, L, of the jth sub-block on the ith transmit antennai,jThe length of the jth sub data block on the ith transmitting antenna is shown;
(3) for the pre-modulated data block after adding phase continuous symbols
Figure FDA00033018723600000111
And
Figure FDA00033018723600000112
amplitude modulation pulse decomposition is carried out to obtain modulation signals s on two antennasm,1(t)、sm,2(t); respectively, as follows:
Figure FDA00033018723600000113
Figure FDA00033018723600000114
wherein
Figure FDA00033018723600000115
Denotes the modulation index, Lo＝Ld+3 represents the length of the modulation signal,
Figure FDA00033018723600000116
to represent
Figure FDA00033018723600000117
The upper i' th bit of the data,
Figure FDA00033018723600000118
to represent
Figure FDA00033018723600000119
Upper i' bit, c0(t) is a shaping function, expressed as follows:
Figure FDA00033018723600000120
(4) modulating signals s on two antennasm,1(t)、sm,2(t) the heads are each added with a length LcpTo obtain sm1(t)、sm2(t); and areTo sm1(t)、sm2(t) performing STBC coding to obtain a transmission signal s on the 1 st antenna1(t) and the transmitted signal s on the 2 nd antenna2(t)；
(5) Transmitting signal s on the 1 st transmitting antenna1(t) adding a training sequence p before1(t), obtaining the transmitting signal s with training sequence on the 1 st transmitting antennap1(t) transmitting signal s on the 2 nd transmitting antenna2(t) adding a training sequence p before2(t), obtaining the transmitting signal s with training sequence on the 2 nd transmitting antennap2(t) wherein p1(t)、p2(t) all have a length of Lp；
(6) Transmitting signals s with training sequences on two transmitting antennasp1(t) and sp2(t) obtaining a receiving signal r (t) on a receiving antenna at a receiving end through a flat fading channel;
r(t)＝h1sp1(t)+h2sp2(t)+n(t)
h1for the 1 st transmitting antenna to receiving antenna flat fading channel response, h2For the flat fading channel response from the 2 nd transmitting antenna to the receiving antenna, n (t) is additive white gaussian noise;
(7) using training sequence of received signal r (t) on receiving antenna to make channel estimation:
(7a) dividing the training sequence p (t) on the received signal into
Figure FDA0003301872360000021
Segment interval with duration of 2TsCalculating the confidence level delta of the nth section of the training sequence p (t) on the received signali,n：
Figure FDA0003301872360000022
Figure FDA0003301872360000023
Wherein p isi(t) represents the training sequence on the ith transmit antenna;
(7b) the reliability δ obtained from (7a)i,nTraining sequence p in (1) and (5)1(t)、p2And (t) calculating the average channel response estimated value from the ith transmitting antenna to the receiving antenna according to the received signal r (t) in (t) and (6)
Figure FDA0003301872360000024
Figure FDA0003301872360000031
2. The method of claim 1, wherein the data frame in (1)
Figure FDA0003301872360000032
Is a binary random sequence with length L3994.
3. The method of claim 1, wherein the length of each of the three sub-data blocks in (2) is L1＝Lcp-1、L2＝Ld-2Lcp+2、L3＝Lcp-1, wherein LcpIs the cyclic prefix length.
4. The method of claim 1, wherein the length L is added in (4) at two modulation signal headerscpThe cyclic prefix of (c) is implemented as follows:
modulating the tail length of the signal by the 1 st transmitting antenna to be LcpThe data is copied to the head of the modulation signal of the 1 st transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm1(t)：
Figure FDA0003301872360000033
Modulating the 2 nd transmitting antenna with the tail length of LcpThe data is copied to the head of the modulation signal of the 2 nd transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm2(t)：
Figure FDA0003301872360000034
Wherein L iso＝Ld+3 denotes the modulation signal length.
5. The method of claim 1, wherein the transmitted signal s on the 1 st antenna in (4)1(t) transmitting signal s on 2 nd antenna2(t) are respectively represented as follows:
s1(t)＝[sm1(t) sm2(t)]
Figure FDA0003301872360000035
6. the method of claim 1, wherein in (5) two training sequences p of transmitted signals1(t)、p2(t) all internal structures are [1, -1,1, -1,.. multidot.1, -1]Length L ofpL is more than or equal to 50pAn even number less than or equal to 1000.
7. The method of claim 1, wherein the transmitted signal s with the training sequence on the 1 st antenna in (5)p1(t) and the transmitted signal s with training sequence on the 2 nd antennap2(t) are respectively represented as follows:
sp1(t)＝[p1(t) s1(t)]
sp2(t)＝[p2(t) s2(t)]
wherein s is1(t) is the transmitted signal on the 1 st antenna, s2(t) for signals transmitted on the 2 nd antenna, p1(t)For training sequences on the 1 st antenna, p2And (t) is a training sequence on the 2 nd antenna.
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