CN112838657B - Control method and device of charging system and terminal equipment - Google Patents
Control method and device of charging system and terminal equipment Download PDFInfo
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- CN112838657B CN112838657B CN202110118295.2A CN202110118295A CN112838657B CN 112838657 B CN112838657 B CN 112838657B CN 202110118295 A CN202110118295 A CN 202110118295A CN 112838657 B CN112838657 B CN 112838657B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
- H02J7/04—Regulation of charging current or voltage
- H02J7/06—Regulation of charging current or voltage using discharge tubes or semiconductor devices
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- B—PERFORMING OPERATIONS; TRANSPORTING
- B60—VEHICLES IN GENERAL
- B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
- B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
- B60L53/60—Monitoring or controlling charging stations
- B60L53/62—Monitoring or controlling charging stations in response to charging parameters, e.g. current, voltage or electrical charge
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/70—Energy storage systems for electromobility, e.g. batteries
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T10/00—Road transport of goods or passengers
- Y02T10/60—Other road transportation technologies with climate change mitigation effect
- Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
- Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
- Y02T90/10—Technologies relating to charging of electric vehicles
- Y02T90/12—Electric charging stations
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Transportation (AREA)
- Mechanical Engineering (AREA)
- Charge And Discharge Circuits For Batteries Or The Like (AREA)
Abstract
The application is applicable to the technical field of power systems, and provides a control method, a device and terminal equipment of a charging system, wherein the control method of the charging system comprises the following steps: acquiring a target value of a preset parameter of a pulse width modulation control circuit in a charging system at a target moment; determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation; and adjusting the DC bus voltage ripple small signal feedback coefficient of the pulse width modulation control circuit to be a target DC bus voltage ripple small signal feedback coefficient. The application can improve the stability of the charging system.
Description
Technical Field
The application belongs to the technical field of power systems, and particularly relates to a control method, a device and terminal equipment of a charging system.
Background
With the popularization of electric vehicles and the increase of endurance mileage, the demand of people for high-power rapid charging is becoming stronger. In order to meet the requirement of high-power rapid charging, the charging system needs to be ensured to be capable of running stably under different loads or when different loads are switched.
The charging system is a typical cascade system, which generally consists of a pulse width modulation (Pulse Width Modulation, PWM) rectifier and a DC/DC converter. As in the cascade system shown in fig. 1, the PWM rectifier can be considered as the source converter in fig. 1 and the DC/DC converter can be considered as the load converter in fig. 1, where Z o Representing the output impedance of the source converter, Z in Representing the input impedance of the load converter. Currently, the stability of a cascade system is generally analyzed by using the impedance characteristics of the module ports, and if the output impedance of the source converter is smaller than the input impedance of the load converter in the entire frequency range in which the system operates, the system can stably operate. Taking a charging system adopting an LCL type PWM rectifier as an example, the output impedance of the LCL type PWM rectifier can be reduced by introducing virtual impedance, so that the stability of the charging system is improved.
However, the existing manner of introducing virtual impedance to reduce output impedance still does not improve the stability of the charging system well.
Disclosure of Invention
In view of the above, the embodiments of the present application provide a control method, apparatus and terminal device for a charging system, so as to solve the problem in the prior art that the charging system is poor in stability.
A first aspect of an embodiment of the present application provides a method for controlling a charging system, including:
acquiring a target value of a preset parameter of a pulse width modulation control circuit in a charging system at a target moment;
determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation;
and adjusting the DC bus voltage ripple small signal feedback coefficient of the pulse width modulation control circuit to be a target DC bus voltage ripple small signal feedback coefficient.
Optionally, the preset parameter is a difference between a given value of the dc bus voltage and a measured value of the dc bus voltage.
Optionally, the preset parameter is a difference between a given value of the dc bus voltage ripple small signal and a measured value of the dc bus voltage ripple small signal.
Optionally, the preset corresponding relation includes a first constant and a second constant, and the first constant is greater than the second constant;
correspondingly, according to the target value and the preset corresponding relation, determining the feedback coefficient of the ripple small signal of the target direct current bus voltage corresponding to the target value comprises the following steps:
under the condition that the target value is greater than or equal to a preset threshold value, determining a first constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus;
and under the condition that the target value is smaller than a preset threshold value, determining the second constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus.
Optionally, the preset corresponding relation includes a plurality of constants, and each constant corresponds to a threshold interval;
correspondingly, according to the target value and the preset corresponding relation, determining the feedback coefficient of the ripple small signal of the target direct current bus voltage corresponding to the target value comprises the following steps:
determining a threshold interval to which the target value belongs;
and determining a constant corresponding to a threshold interval to which the target value belongs as a feedback coefficient of the ripple small signal of the target direct current bus voltage.
Optionally, the preset corresponding relation includes a first coefficient and a second coefficient;
correspondingly, before determining the feedback coefficient of the ripple small signal of the target direct current bus voltage corresponding to the target numerical value according to the target numerical value and the preset corresponding relation, the control method of the charging system further comprises the following steps:
acquiring a first numerical value of a preset parameter of a pulse width modulation control circuit at a first moment; the first moment is the moment before the target moment, and the absolute value of the difference value between the target value and the first value is obtained;
correspondingly, according to the target value and the preset corresponding relation, determining the feedback coefficient of the ripple small signal of the target direct current bus voltage corresponding to the target value comprises the following steps:
acquiring a first multiplication value and a second multiplication value; the first multiplication is the multiplication of the first coefficient and the target value, and the second multiplication is the multiplication of the second coefficient and the absolute value;
and determining the sum of the first multiplication value and the second multiplication value as a target direct current bus voltage ripple small signal feedback coefficient.
A second aspect of an embodiment of the present application provides a control device for a charging system, including:
the acquisition module is used for acquiring a target value of a preset parameter of a pulse width modulation control circuit in the charging system at a target moment;
the determining module is used for determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation;
and the control module is used for adjusting the feedback coefficient of the DC bus voltage ripple small signal of the pulse width modulation control circuit to be the feedback coefficient of the target DC bus voltage ripple small signal.
Optionally, the preset parameter is a difference between a given value of the dc bus voltage and a measured value of the dc bus voltage.
Optionally, the preset parameter is a difference between a given value of the dc bus voltage ripple small signal and a measured value of the dc bus voltage ripple small signal.
Optionally, the preset corresponding relation includes a first constant and a second constant, and the first constant is greater than the second constant;
correspondingly, the determining module is further configured to:
under the condition that the target value is greater than or equal to a preset threshold value, determining a first constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus;
and under the condition that the target value is smaller than a preset threshold value, determining the second constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus.
Optionally, the preset corresponding relation includes a plurality of constants, and each constant corresponds to a threshold interval;
correspondingly, the determining module is further configured to:
determining a threshold interval to which the target value belongs;
and determining a constant corresponding to a threshold interval to which the target value belongs as a feedback coefficient of the ripple small signal of the target direct current bus voltage.
Optionally, the preset corresponding relation includes a first coefficient and a second coefficient;
correspondingly, the acquisition module is further configured to:
acquiring a first numerical value of a preset parameter of a pulse width modulation control circuit at a first moment; the first moment is the moment before the target moment, and the absolute value of the difference value between the target value and the first value is obtained;
correspondingly, the determining module is further configured to:
acquiring a first multiplication value and a second multiplication value; the first multiplication is the multiplication of the first coefficient and the target value, and the second multiplication is the multiplication of the second coefficient and the absolute value;
and determining the sum of the first multiplication value and the second multiplication value as a target direct current bus voltage ripple small signal feedback coefficient.
A third aspect of an embodiment of the present application provides a terminal device comprising a memory, a processor and a computer program stored in the memory and executable on the processor, the processor implementing the steps of the method according to the first aspect when executing the computer program.
Compared with the prior art, the embodiment of the application has the beneficial effects that:
according to the embodiment of the application, the target value of the preset parameter of the pulse width modulation control circuit in the charging system at the target moment can be obtained, then the target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value is determined according to the target value and the preset corresponding relation, and finally the direct current bus voltage ripple small signal feedback coefficient of the pulse width modulation control circuit can be adjusted to be the target direct current bus voltage ripple small signal feedback coefficient. Therefore, the voltage ripple small signal feedback coefficient k of the direct current bus can be automatically adjusted based on the fluctuation condition of the voltage of the direct current bus, the problems that the grid side harmonic current is increased and the system stability is deteriorated due to the fact that the voltage ripple small signal feedback coefficient of the direct current bus is too large are solved, and the stability of a charging system is better improved. In addition, the stability of the system direct current bus is enhanced when the high-power electric automobile power battery is charged and discharged, meanwhile, the current harmonic wave at the power grid side can be reduced, and the network access current quality is improved.
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present application, the drawings that are needed in the embodiments or the description of the prior art will be briefly described below, it being obvious that the drawings in the following description are only some embodiments of the present application, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a schematic diagram of a cascade system according to an embodiment of the present application;
fig. 2 is a topology diagram of a three-phase LCL-type PWM rectifier according to an embodiment of the present application;
fig. 3 is a block diagram of a control system of an LCL PWM rectifier according to an embodiment of the present application;
FIG. 4 is a closed-loop control block diagram of a reduced order small signal model according to an embodiment of the present application;
FIG. 5 is a closed-loop control block diagram of a reduced-order small signal model after virtual impedance is introduced according to an embodiment of the present application;
fig. 6 is a flowchart of steps of a control method of a charging system according to an embodiment of the present application;
FIG. 7 is a control block diagram according to an embodiment of the present application;
FIG. 8 is a program control block diagram of a first implementation provided by an embodiment of the present application;
FIG. 9 is a program control block diagram of a second implementation provided by an embodiment of the present application;
fig. 10 is a schematic diagram of a control device of a charging system according to an embodiment of the present application;
fig. 11 is a schematic diagram of a terminal device according to an embodiment of the present application.
Detailed Description
In the following description, for purposes of explanation and not limitation, specific details are set forth such as the particular system architecture, techniques, etc., in order to provide a thorough understanding of the embodiments of the present application. It will be apparent, however, to one skilled in the art that the present application may be practiced in other embodiments that depart from these specific details. In other instances, detailed descriptions of well-known systems, devices, circuits, and methods are omitted so as not to obscure the description of the present application with unnecessary detail.
In order to illustrate the technical scheme of the application, the following description is made by specific examples.
First, an existing way of introducing virtual impedance to reduce output impedance will be described.
Currently, the impedance characteristics of the module ports are typically used to analyze the stability of the cascade system based on Middlebrook criteria. Referring to fig. 2 and 3, fig. 2 shows a three-phase LCL type PWM rectifier topology,FIG. 3 shows a block diagram of an LCL PWM rectifier control system, where L s1 Is a network side inductance, the internal resistance is R L1 ；L s2 Is a rectifier side inductance with an internal resistance of R L2 ；C 1 The capacitor is a network side filter capacitor, and C is a direct current side bus capacitor; i.e sd 、i sq For the dq transformed net side current, i d 、i q For the rectifier side current after dq conversion, v Cd 、v Cq Is the voltage of the filter capacitor terminal after dq conversion, v sd 、v sq For the network side voltage after dq conversion, v d 、v q The midpoint voltage of the bridge arm after dq conversion; current source i for DC/DC charging system o Indicating that the DC bus voltage is v dc ；v dcref Is the reference value of the voltage of the direct current bus, i abc Is three-phase current at the inverter side.
According to kirchhoff voltage and current law, an average model of the three-phase LCL type PWM rectifier under the dq coordinate system can be established as follows:
from the above-mentioned average model, it is known that there is an influence of mutual coupling between d-axis and q-axis variables, and decoupling control can be adopted for dq-axis in order to simplify analysis. And because the LCL type filter has resonance peak, the stability of the system is affected, and the current oscillation can be restrained by adopting an active damping control method of capacitive current feedback, so that the method can be used for obtaining:
the duty cycle is divided into three parts in the above formula, wherein d d1 And d q1 Is a current-receiving inner loop regulator G for controlling the duty ratio of the output of the system ci Is a function of (1); d, d d2 And d q2 The duty cycle of the generated coupling current; d, d d3 And d q3 The duty ratio of the active damping is increased by adopting capacitive current feedback, and the active damping coefficient is K.
The average model under the dq axis of the decoupled LCL type PWM rectifier is as follows:
is arranged at a direct current working point, and the D-axis duty ratio is D d1 The q-axis duty ratio is D q1 The d-axis current is I d Q-axis current is I q The load current source is I o The DC side voltage is V dc Capacitor voltage V dc . Consider that when the PWM rectifier is operating at a steady state operating point, there is I sd 、I d 、I sq 、I q V (V) dc 、V Cd 、V Cq The variation of (2) is 0. And the PWM rectifier is operated in the rectifying mode, requiring control of I sq ＝0、I q =0, so that V sq ＝0、V q =0, the dc stable operating point can be further found as:
consider i q ＝0、v q =0 and dq are decoupled from each other, analysis shows that v dc The method is only related to the d-axis component, so that the influence of the q-axis component can be ignored in analysis, and the average model of the PWM rectifier after the reduction is obtained as follows:
small signal disturbance is carried out near a steady-state working point, a quadratic term in the small signal disturbance is ignored, and a small signal model after the PWM rectifier is reduced is obtained as follows:
in the above formula, the variable symbol band "≡" represents a corresponding small signal, and correspondingly, the output equation corresponding to the above formula is:
and carrying out Laplace transformation and matrix operation on the small signal model subjected to the order reduction of the PWM rectifier and a corresponding output equation to obtain the PWM rectifier:
wherein, the liquid crystal display device comprises a liquid crystal display device,
according to the definition of the output impedance and the above formula obtained by Law transformation and matrix operation, the open loop output impedance of the three-phase LCL type PWM rectifier can be obtained as follows:
according to the above equation obtained by the Laplace transformation and the matrix operation, a reduced order small signal model closed-loop control block diagram is obtained by adopting a control structure of a voltage outer loop and a current inner loop, as shown in figure 4, wherein,g is the small signal reference value of the voltage of the direct current bus cv G is the transfer function of the voltage outer loop PI controller ci The transfer function of the current inner loop PI controller is expressed as follows:
wherein KP1 and KP2 are proportional coefficients of the PI controller; KI1 and KI2 are integral coefficients of the PI controller.
From the closed-loop control block diagram shown in fig. 4, the closed-loop output impedance can be obtained according to the meisen gain equation as:
under the condition that an additional circuit of the system is not added, a ripple small signal of the DC bus voltage is used as a negative feedback signal to be added to a given end of an outer ring of the DC bus voltage, the output impedance can be optimized by introducing virtual impedance, the stability of the cascade system is improved, a control block diagram is shown in fig. 5, and k is a feedback coefficient of the ripple small signal of the DC bus voltage in fig. 5. The method for improving the stability of the PWM rectifier and the DC/DC cascade system is relatively more, easy to realize and relatively good in effect.
According to fig. 5, the output impedance after the feedback of the ripple small signal of the dc bus voltage is introduced can be obtained by the meisen gain formula:
the output impedance bode diagram can be obtained through the method, and the extremum of the output impedance is found from the output impedance bode diagram to be reduced along with the increase of the ripple small signal feedback coefficient k of the DC bus voltage; the larger the feedback coefficient k is, the smaller the amplitude of the output impedance is, the stronger the system stability is, and the smaller the fluctuation amplitude of the DC bus voltage is during sudden loading.
However, a too large feedback coefficient k reduces the output impedance, which will lead to a decrease in the stability of the PWM rectifier system, resulting in a poor sine of the grid-side current waveform at steady state and an increase in the grid-side harmonic current. Therefore, as described in the background art, the existing manner of introducing a virtual impedance to reduce the output impedance still cannot better improve the stability of the charging system.
In order to solve the problems in the prior art, the embodiment of the application provides a control method, a device and terminal equipment of a charging system. The following first describes a control method of the charging system provided by the embodiment of the present application.
The execution body of the control method of the charging system may be a control device of the charging system, and the control device of the charging system may be a terminal device with data processing capability, for example, a programmable controller, a singlechip, a personal computer, or the like, and the embodiment of the application is not particularly limited.
As shown in fig. 6, the control method of the charging system provided by the embodiment of the application includes the following steps:
step S610, obtaining a target value of a preset parameter of a pwm control circuit in the charging system at a target time.
In some embodiments, the preset parameter may be a difference between a given value of the dc bus voltage and a measured value of the dc bus voltage.
In some embodiments, the preset parameter may be a difference between a given value of the dc bus voltage ripple small signal and a measured value of the dc bus voltage ripple small signal.
In some embodiments, the target time may be any one time.
In this way, in the running process of the charging system, the target value of the preset parameter of the pulse width modulation control circuit in the charging system at the target moment can be obtained.
And S620, determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation.
In some embodiments, the preset correspondence may include a plurality of relationships.
For example, the preset correspondence may include a first constant and a second constant, wherein the first constant is greater than the second constant. Accordingly, the specific process of step S620 may be as follows: under the condition that the target value is greater than or equal to a preset threshold value, determining a first constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus; and under the condition that the target value is smaller than a preset threshold value, determining the second constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus.
For another example, the preset correspondence may include a plurality of constants, each constant corresponding to a threshold interval. Accordingly, the specific process of step S620 may be as follows: determining a threshold interval to which the target value belongs; and determining a constant corresponding to a threshold interval to which the target value belongs as a feedback coefficient of the ripple small signal of the target direct current bus voltage.
For another example, the preset correspondence may include a first coefficient and a second coefficient. Accordingly, the following process may be performed before step S620: acquiring a first numerical value of a preset parameter of a pulse width modulation control circuit at a first moment; the first time is a time preceding the target time, and an absolute value of a difference between the target value and the first value is obtained. Thus, the specific process of step S620 may be as follows: acquiring a first multiplication value and a second multiplication value; the first multiplication is the multiplication of the first coefficient and the target value, and the second multiplication is the multiplication of the second coefficient and the absolute value; and determining the sum of the first multiplication value and the second multiplication value as a target direct current bus voltage ripple small signal feedback coefficient.
Step S630, the feedback coefficient of the dc bus voltage ripple small signal of the pwm control circuit is adjusted to the feedback coefficient of the target dc bus voltage ripple small signal.
In some embodiments, the dc bus voltage ripple small signal feedback coefficient of the pwm control circuit may be adjusted to the target dc bus voltage ripple small signal feedback coefficient after determining the target dc bus voltage ripple small signal feedback coefficient corresponding to the target value. Therefore, the voltage ripple small signal feedback coefficient k of the direct current bus can be automatically adjusted based on the fluctuation condition of the voltage of the direct current bus, the problems that the grid side harmonic current is increased and the system stability is deteriorated due to the fact that the voltage ripple small signal feedback coefficient of the direct current bus is too large are solved, and the stability of a charging system is better improved. In addition, the stability of the system direct current bus is enhanced when the high-power electric automobile power battery is charged and discharged, meanwhile, the current harmonic wave at the power grid side can be reduced, and the network access current quality is improved.
In order to better understand the control method of the charging system provided by the application, a scheme one when the preset parameter is a difference value between a given value of the dc bus voltage and a measured value of the dc bus voltage and a scheme two when the preset parameter is a difference value between a given value of the dc bus voltage ripple small signal and a measured value of the dc bus voltage ripple small signal are provided below, specifically as follows:
scheme one: the magnitude of the DC bus voltage ripple small signal feedback coefficient k is automatically changed according to a certain requirement and rule along with the magnitude e of the deviation value of the DC bus voltage given value and the actual DC bus voltage, or is automatically changed according to a certain requirement and rule along with the magnitude e of the deviation value and the change rate deltae of the magnitude of the deviation value.
Scheme II: the magnitude of the feedback coefficient k of the ripple small signal of the DC bus voltage is enabled to follow the ripple small signalThe magnitude of the value is automatically changed according to certain requirements and rules or is changed along with a ripple small signal +.>Magnitude of the value and ripple small signal +.>Rate of change of value size ∈>Automatically changes according to certain requirements and rules.
In this way, the DC bus voltage v dc Is a ripple small signal of (1)As a negative feedback signal to be superimposed on the outer ring of the DC bus voltage, the output impedance optimization of the PWM rectifier can be realized by introducing virtual impedance, the system stability is improved, the control block diagram is shown in figure 7, G is a low-pass filter for acquiring the DC bus voltage ripple small signal, k is the DC bus voltage ripple small signal feedback control coefficient, e is the deviation between the given value of the DC bus voltage and the actual DC bus voltage, G is the feedback control coefficient of the DC bus voltage ripple small signal cv Is a voltage outer loop PI controller G ci The current loop PI controller is characterized in that the current loop PI controller is a current loop PI controller, and the other parts are traditional PWM rectifier control system structures.
It can be found that the feedback control of the ripple small signal of the DC bus voltage can be added on the basis of the DC bus voltage control of the conventional PWM rectifier, as shown in FIG. 7, on the one hand, the DC bus voltage reference value v dcref With actual DC bus voltage v dc Comparing to obtain a deviation e of the two; on the other hand, the DC bus voltage v dc Obtaining DC bus voltage ripple small signal through low pass filter GDC bus voltage ripple small signal +.>Multiplying the small signal feedback coefficient k of the DC bus voltage ripple with the reference value v of the DC bus voltage dcref With actual DC bus voltage v dc The deviation e of the two is subtracted by comparison and is used as a voltage outer loop PI controller G cv Is input in common with the input of the input module.
The following describes a specific implementation manner of the control method of the charging system provided by the embodiment of the present application by taking the "scheme one" as an example, and the implementation manner of the "scheme two" is similar.
Three implementations of scheme one are presented below.
(1) The implementation mode is as follows: the ripple small signal feedback coefficient k is 0 or some constant.
When the deviation value |e| is larger, a ripple small signal feedback coefficient is introduced, and the ripple small signal feedback coefficient k is a certain constant, for example, k=6, so that the system stability is improved; when the deviation value |e| is reduced and the system tends to be stable, the ripple small signal feedback coefficient k=0 is caused, and the network side current waveform is improved. The specific implementation steps are as follows:
1) Setting a proper threshold epsilon according to the actual condition of the system, for example, taking 0.2V-0.5V;
2) When |e| is not less than epsilon, introducing busbar voltage small signal feedback control, wherein k is a certain constant, for example, k=6, so that the output impedance of the PWM rectifier is reduced, and the system stability is improved;
3) When |e| < epsilon, the busbar voltage small signal feedback control is removed, so that k=0, and the network side current waveform when the system is stable is improved.
A program control block diagram of the first embodiment is shown in fig. 8, V dcref_n N-time sampling value V which is the reference value of DC bus voltage dc_n E is the actual sampling value of the direct current bus voltage at the moment n n Is the deviation sampling value of the direct current bus voltage n moment.
(2) The implementation mode II is as follows: the ripple small signal feedback coefficient k varies with the magnitude of the offset value e (look-up table).
And establishing a table corresponding to the feedback coefficient k of the ripple small signal according to the magnitude of the deviation value |e|, and automatically selecting the feedback coefficient k according to the magnitude of the actual deviation value |e| when the device operates. The specific implementation steps are as follows:
1) According to the actual condition of the system, a proper threshold epsilon and grading are set as shown in the following table one:
list one
| e | k |
| |e|<0.1 | 0 |
| 0.1≤|e|<0.2 | 2 |
| 0.2≤|e|<0.3 | 4 |
| 0.3≤|e|<0.5 | 5 |
| |e|>0.6 | 6 |
2) According to the magnitude of the deviation value |e| the magnitude of a corresponding small signal feedback coefficient k is obtained by looking up a table;
a program control block diagram of implementation two is shown in fig. 9.
(3) And the implementation mode is three: the feedback coefficient k of the ripple small signal changes along with the magnitude and change rate deltae of the offset value e
Set V dcref_n N-time sampling value V which is the reference value of DC bus voltage dc_n E is the actual sampling value of the direct current bus voltage at the moment n n For the deviation sampling value of the direct current bus voltage n moment, the following steps are:
e n ＝V dcref_n -V dc_n ；
Δe n ＝e n -e n-1 ；
correspondingly, the feedback coefficient k of the ripple small signal at the moment n is:
k n ＝P|e n |+D|Δe n |
Kn＝P|en|+D|Δen|
in the above formula, P is a proportionality coefficient of the deviation value e, and D is a proportionality coefficient of the deviation value change rate Δe. kn requires setting of upper and lower limits, which may be set to 0, and upper limits and scaling factors P and D may be set by experimental tests.
Through the above processing, it can be found that the "implementation one" is the simplest to implement; the second implementation mode is more refined in adjustment and better in effect; the implementation mode III considers the control deviation change rate delta e and plays an important role in inhibiting the direct current bus from greatly fluctuating.
It is worth mentioning that, introduce the adaptive control strategy of variable parameter in the little signal feedback control method based on direct current busbar voltage, can reduce the output impedance of PWM rectifier when high-power electric automobile power battery charges, discharges, strengthen cascade system stability, can effectively reduce the network access current distortion when electric automobile power battery charges, discharges again, improve the electric current quality of electric wire netting side, have important meaning to improving the power supply of electric wire netting, electricity quality.
In the embodiment of the application, the target value of the preset parameter of the pulse width modulation control circuit in the charging system at the target moment can be obtained, then the target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value is determined according to the target value and the preset corresponding relation, and finally the direct current bus voltage ripple small signal feedback coefficient of the pulse width modulation control circuit can be adjusted to the target direct current bus voltage ripple small signal feedback coefficient. Therefore, the voltage ripple small signal feedback coefficient k of the direct current bus can be automatically adjusted based on the fluctuation condition of the voltage of the direct current bus, the problems that the grid side harmonic current is increased and the system stability is deteriorated due to the fact that the voltage ripple small signal feedback coefficient of the direct current bus is too large are solved, and the stability of a charging system is better improved. In addition, the stability of the system direct current bus is enhanced when the high-power electric automobile power battery is charged and discharged, meanwhile, the current harmonic wave at the power grid side can be reduced, and the network access current quality is improved.
Based on the control method of the charging system provided by the embodiment, correspondingly, the application further provides a specific implementation mode of the control device of the charging system, which is applied to the control method of the charging system. Please refer to the following examples.
As shown in fig. 10, there is provided a control device of a charging system, the device including:
an obtaining module 1010, configured to obtain a target value of a preset parameter of a pwm control circuit in a charging system at a target time;
the determining module 1020 is configured to determine a target dc bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset correspondence;
the control module 1030 is configured to adjust the dc bus voltage ripple small signal feedback coefficient of the pwm control circuit to a target dc bus voltage ripple small signal feedback coefficient.
Optionally, the preset parameter is a difference between a given value of the dc bus voltage and a measured value of the dc bus voltage.
Optionally, the preset parameter is a difference between a given value of the dc bus voltage ripple small signal and a measured value of the dc bus voltage ripple small signal.
Optionally, the preset corresponding relation includes a first constant and a second constant, and the first constant is greater than the second constant;
correspondingly, the determining module is further configured to:
under the condition that the target value is greater than or equal to a preset threshold value, determining a first constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus;
and under the condition that the target value is smaller than a preset threshold value, determining the second constant as a small signal feedback coefficient of the voltage ripple of the target direct current bus.
Optionally, the preset corresponding relation includes a plurality of constants, and each constant corresponds to a threshold interval;
correspondingly, the determining module is further configured to:
determining a threshold interval to which the target value belongs;
and determining a constant corresponding to a threshold interval to which the target value belongs as a feedback coefficient of the ripple small signal of the target direct current bus voltage.
Optionally, the preset corresponding relation includes a first coefficient and a second coefficient;
correspondingly, the acquisition module is further configured to:
acquiring a first numerical value of a preset parameter of a pulse width modulation control circuit at a first moment; the first moment is the moment before the target moment, and the absolute value of the difference value between the target value and the first value is obtained;
correspondingly, the determining module is further configured to:
acquiring a first multiplication value and a second multiplication value; the first multiplication is the multiplication of the first coefficient and the target value, and the second multiplication is the multiplication of the second coefficient and the absolute value;
and determining the sum of the first multiplication value and the second multiplication value as a target direct current bus voltage ripple small signal feedback coefficient.
In the embodiment of the application, the target value of the preset parameter of the pulse width modulation control circuit in the charging system at the target moment can be obtained, then the target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value is determined according to the target value and the preset corresponding relation, and finally the direct current bus voltage ripple small signal feedback coefficient of the pulse width modulation control circuit can be adjusted to the target direct current bus voltage ripple small signal feedback coefficient. Therefore, the voltage ripple small signal feedback coefficient k of the direct current bus can be automatically adjusted based on the fluctuation condition of the voltage of the direct current bus, the problems that the grid side harmonic current is increased and the system stability is deteriorated due to the fact that the voltage ripple small signal feedback coefficient of the direct current bus is too large are solved, and the stability of a charging system is better improved. In addition, the stability of the system direct current bus is enhanced when the high-power electric automobile power battery is charged and discharged, meanwhile, the current harmonic wave at the power grid side can be reduced, and the network access current quality is improved.
Fig. 11 is a schematic diagram of a terminal device according to an embodiment of the present application. As shown in fig. 11, the terminal device 11 of this embodiment includes: a processor 110, a memory 111 and a computer program 112 stored in said memory 111 and executable on said processor 110. The processor 110, when executing the computer program 112, implements the steps of the control method embodiments of the respective charging systems described above. Alternatively, the processor 110, when executing the computer program 112, performs the functions of the modules/units of the apparatus embodiments described above.
Illustratively, the computer program 112 may be partitioned into one or more modules/units that are stored in the memory 111 and executed by the processor 110 to complete the present application. The one or more modules/units may be a series of computer program instruction segments capable of performing specific functions for describing the execution of the computer program 112 in the terminal device 11. For example, the computer program 112 may be divided into an acquisition module, a determination module, and an adjustment module, where each module specifically functions as follows:
the acquisition module is used for acquiring a target value of a preset parameter of a pulse width modulation control circuit in the charging system at a target moment;
the determining module is used for determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation;
and the control module is used for adjusting the feedback coefficient of the DC bus voltage ripple small signal of the pulse width modulation control circuit to be the feedback coefficient of the target DC bus voltage ripple small signal.
The terminal device 11 may be a computing device such as a desktop computer, a notebook computer, a palm computer, a cloud server, etc. The terminal device may include, but is not limited to, a processor 110, a memory 111. It will be appreciated by those skilled in the art that fig. 11 is merely an example of a terminal device 11 and does not constitute a limitation of the terminal device 11, and may include more or less components than illustrated, or may combine certain components, or different components, e.g., the terminal device may further include an input-output device, a network access device, a bus, etc.
The processor 110 may be a central processing unit (Central Processing Unit, CPU), but may also be other general purpose processors, digital signal processors (Digital Signal Processor, DSP), application specific integrated circuits (Application Specific Integrated Circuit, ASIC), field programmable gate arrays (Field-Programmable Gate Array, FPGA) or other programmable logic devices, discrete gate or transistor logic devices, discrete hardware components, or the like. A general purpose processor may be a microprocessor or the processor may be any conventional processor or the like.
The memory 111 may be an internal storage unit of the terminal device 11, such as a hard disk or a memory of the terminal device 11. The memory 111 may be an external storage device of the terminal device 11, such as a plug-in hard disk, a Smart Media Card (SMC), a Secure Digital (SD) Card, a Flash memory Card (Flash Card) or the like, which are provided on the terminal device 11. Further, the memory 111 may also include both an internal storage unit and an external storage device of the terminal device 11. The memory 111 is used for storing the computer program and other programs and data required by the terminal device. The memory 111 may also be used to temporarily store data that has been output or is to be output.
It will be apparent to those skilled in the art that, for convenience and brevity of description, only the above-described division of the functional units and modules is illustrated, and in practical application, the above-described functional distribution may be performed by different functional units and modules according to needs, i.e. the internal structure of the apparatus is divided into different functional units or modules to perform all or part of the above-described functions. The functional units and modules in the embodiment may be integrated in one processing unit, or each unit may exist alone physically, or two or more units may be integrated in one unit, where the integrated units may be implemented in a form of hardware or a form of a software functional unit. In addition, the specific names of the functional units and modules are only for distinguishing from each other, and are not used for limiting the protection scope of the present application. The specific working process of the units and modules in the above system may refer to the corresponding process in the foregoing method embodiment, which is not described herein again.
In the foregoing embodiments, the descriptions of the embodiments are emphasized, and in part, not described or illustrated in any particular embodiment, reference is made to the related descriptions of other embodiments.
Those of ordinary skill in the art will appreciate that the various illustrative elements and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware, or combinations of computer software and electronic hardware. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the solution. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present application.
In the embodiments provided in the present application, it should be understood that the disclosed apparatus/terminal device and method may be implemented in other manners. For example, the apparatus/terminal device embodiments described above are merely illustrative, e.g., the division of the modules or units is merely a logical function division, and there may be additional divisions in actual implementation, e.g., multiple units or components may be combined or integrated into another system, or some features may be omitted or not performed. Alternatively, the coupling or direct coupling or communication connection shown or discussed may be an indirect coupling or communication connection via interfaces, devices or units, which may be in electrical, mechanical or other forms.
The units described as separate units may or may not be physically separate, and units shown as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the units may be selected according to actual needs to achieve the purpose of the solution of this embodiment.
In addition, each functional unit in the embodiments of the present application may be integrated in one processing unit, or each unit may exist alone physically, or two or more units may be integrated in one unit. The integrated units may be implemented in hardware or in software functional units.
The integrated modules/units, if implemented in the form of software functional units and sold or used as stand-alone products, may be stored in a computer readable storage medium. Based on such understanding, the present application may implement all or part of the flow of the method of the above embodiment, or may be implemented by a computer program to instruct related hardware, where the computer program may be stored in a computer readable storage medium, and when the computer program is executed by a processor, the computer program may implement the steps of each of the method embodiments described above. Wherein the computer program comprises computer program code which may be in source code form, object code form, executable file or some intermediate form etc. The computer readable medium may include: any entity or device capable of carrying the computer program code, a recording medium, a U disk, a removable hard disk, a magnetic disk, an optical disk, a computer Memory, a Read-Only Memory (ROM), a random access Memory (RAM, random Access Memory), an electrical carrier signal, a telecommunications signal, a software distribution medium, and so forth. It should be noted that the computer readable medium contains content that can be appropriately scaled according to the requirements of jurisdictions in which such content is subject to legislation and patent practice, such as in certain jurisdictions in which such content is subject to legislation and patent practice, the computer readable medium does not include electrical carrier signals and telecommunication signals.
The above embodiments are only for illustrating the technical solution of the present application, and not for limiting the same; although the application has been described in detail with reference to the foregoing embodiments, it will be understood by those of ordinary skill in the art that: the technical scheme described in the foregoing embodiments can be modified or some technical features thereof can be replaced by equivalents; such modifications and substitutions do not depart from the spirit and scope of the technical solutions of the embodiments of the present application, and are intended to be included in the scope of the present application.
Claims (6)
1. A control method of a charging system, characterized by being applied to a charging system employing an LCL type PWM rectifier, comprising:
acquiring a target value of a preset parameter of a pulse width modulation control circuit in the charging system at a target moment; the preset parameter is a difference value between a given value of the DC bus voltage and a measured value of the DC bus voltage, or a difference value between a given value of the DC bus voltage ripple small signal and a measured value of the DC bus voltage ripple small signal;
determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation;
and adjusting the feedback coefficient of the DC bus voltage ripple small signal of the pulse width modulation control circuit to be the feedback coefficient of the target DC bus voltage ripple small signal.
2. The control method of a charging system according to claim 1, wherein the preset correspondence relationship includes a first constant and a second constant, the first constant being larger than the second constant;
the determining, according to the target value and a preset correspondence, a target dc bus voltage ripple small signal feedback coefficient corresponding to the target value includes:
under the condition that the target value is greater than or equal to a preset threshold value, determining the first constant as the feedback coefficient of the ripple small signal of the target direct current bus voltage;
and under the condition that the target numerical value is smaller than the preset threshold value, determining the second constant as the feedback coefficient of the ripple small signal of the target direct current bus voltage.
3. The control method of a charging system according to claim 1, wherein the preset correspondence relationship includes a plurality of constants, each constant corresponding to a threshold interval;
the determining, according to the target value and a preset correspondence, a target dc bus voltage ripple small signal feedback coefficient corresponding to the target value includes:
determining a threshold interval to which the target value belongs;
and determining a constant corresponding to a threshold interval to which the target value belongs as the feedback coefficient of the ripple small signal of the target direct current bus voltage.
4. The control method of a charging system according to claim 1, wherein the preset correspondence relationship includes a first coefficient and a second coefficient;
before determining the target direct current bus voltage ripple small signal feedback coefficient corresponding to the target value according to the target value and a preset corresponding relation, the method further comprises:
acquiring a first numerical value of a preset parameter of the pulse width modulation control circuit at a first moment; the first moment is the moment before the target moment, and the absolute value of the difference value between the target value and the first value is obtained;
the determining, according to the target value and a preset correspondence, a target dc bus voltage ripple small signal feedback coefficient corresponding to the target value includes:
acquiring a first multiplication value and a second multiplication value; the first multiplier is a multiplier of the first coefficient and the target value, and the second multiplier is a multiplier of the second coefficient and the absolute value;
and determining the sum value of the first multiplication value and the second multiplication value as the target direct current bus voltage ripple small signal feedback coefficient.
5. A control device of a charging system, characterized by being applied to a charging system employing an LCL type PWM rectifier, comprising:
the acquisition module is used for acquiring a target value of a preset parameter of a pulse width modulation control circuit in the charging system at a target moment; the preset parameter is a difference value between a given value of the DC bus voltage and a measured value of the DC bus voltage, or a difference value between a given value of the DC bus voltage ripple small signal and a measured value of the DC bus voltage ripple small signal;
the determining module is used for determining a target direct current bus voltage ripple small signal feedback coefficient corresponding to the target numerical value according to the target numerical value and a preset corresponding relation;
and the control module is used for adjusting the feedback coefficient of the DC bus voltage ripple small signal of the pulse width modulation control circuit to the feedback coefficient of the target DC bus voltage ripple small signal.
6. A terminal device comprising a memory, a processor and a computer program stored in the memory and executable on the processor, characterized in that the processor implements the steps of the method according to any of claims 1 to 4 when the computer program is executed.
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Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103227469A (en) * | 2012-11-28 | 2013-07-31 | 东方日立(成都)电控设备有限公司 | Secondary ripple wave suppression method for bus voltage of photovoltaic grid-connected inverter |
| CN106160433A (en) * | 2015-03-25 | 2016-11-23 | 神华集团有限责任公司 | A kind of feedback system for controlling current transformer and energy-storage system |
| CN108123463A (en) * | 2016-11-29 | 2018-06-05 | 赵志刚 | A kind of energy accumulation current converter based on multiplex DC/DC converters |
| CN108832804A (en) * | 2018-06-08 | 2018-11-16 | 哈尔滨工程大学 | It is a kind of improve two stage power converter intermediate-bus voltage dynamic property compensation method and device |
| CN109039184A (en) * | 2018-09-03 | 2018-12-18 | 中国商用飞机有限责任公司北京民用飞机技术研究中心 | A kind of device and method based on virtual resistance compensating direct current power supply system stability |
| CN109039038A (en) * | 2018-07-04 | 2018-12-18 | 天津大学 | Capacitor energy storage type single-phase rectifier secondary ripple wave suppressing method based on virtual impedance |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP3393034A1 (en) * | 2017-04-21 | 2018-10-24 | GE Energy Power Conversion Technology Limited | Controlling a back-to-back three-level converter with midpoint voltage ripple compensation |
-
2021
- 2021-01-28 CN CN202110118295.2A patent/CN112838657B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103227469A (en) * | 2012-11-28 | 2013-07-31 | 东方日立(成都)电控设备有限公司 | Secondary ripple wave suppression method for bus voltage of photovoltaic grid-connected inverter |
| CN106160433A (en) * | 2015-03-25 | 2016-11-23 | 神华集团有限责任公司 | A kind of feedback system for controlling current transformer and energy-storage system |
| CN108123463A (en) * | 2016-11-29 | 2018-06-05 | 赵志刚 | A kind of energy accumulation current converter based on multiplex DC/DC converters |
| CN108832804A (en) * | 2018-06-08 | 2018-11-16 | 哈尔滨工程大学 | It is a kind of improve two stage power converter intermediate-bus voltage dynamic property compensation method and device |
| CN109039038A (en) * | 2018-07-04 | 2018-12-18 | 天津大学 | Capacitor energy storage type single-phase rectifier secondary ripple wave suppressing method based on virtual impedance |
| CN109039184A (en) * | 2018-09-03 | 2018-12-18 | 中国商用飞机有限责任公司北京民用飞机技术研究中心 | A kind of device and method based on virtual resistance compensating direct current power supply system stability |
Non-Patent Citations (4)
| Title |
|---|
| EMI Reduction and Output Ripple Improvement of Switching DC-DC Converters with Linear Swept Frequency Modulation;Minh Tri Tran等;《2018 14th IEEE International Conference on Solid-State and Integrated Circuit Technology (ICSICT)》;全文 * |
| Online_Inductance_Identification_of_PWM_Rectifier_under_Unbalanced_and_Distorted_Network;Yongchang Zhang等;《2019 22nd International Conference on Electrical Machines and Systems (ICEMS)》;全文 * |
| 三相电压型PWM整流器建模、控制及稳定性分析;贺诗明;熊健;代大一;王泽;吕知彼;;电网技术(第06期);全文 * |
| 采用变参数 PI 调节器的三相电压型 PWM 整流器的研究;李新杰等;《变流技术》;全文 * |
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