CN112583081B - Quick wireless charging circuit of battery - Google Patents
Quick wireless charging circuit of battery Download PDFInfo
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- CN112583081B CN112583081B CN202011530450.3A CN202011530450A CN112583081B CN 112583081 B CN112583081 B CN 112583081B CN 202011530450 A CN202011530450 A CN 202011530450A CN 112583081 B CN112583081 B CN 112583081B
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- 238000007600 charging Methods 0.000 title claims abstract description 56
- 230000005540 biological transmission Effects 0.000 claims abstract description 16
- 238000006243 chemical reaction Methods 0.000 claims abstract description 14
- 238000010280 constant potential charging Methods 0.000 claims abstract description 13
- 238000005070 sampling Methods 0.000 claims description 34
- 239000003990 capacitor Substances 0.000 claims description 25
- WHXSMMKQMYFTQS-UHFFFAOYSA-N Lithium Chemical compound [Li] WHXSMMKQMYFTQS-UHFFFAOYSA-N 0.000 claims description 20
- 229910052744 lithium Inorganic materials 0.000 claims description 20
- 230000001105 regulatory effect Effects 0.000 claims description 15
- 238000000034 method Methods 0.000 claims description 14
- 229920000134 Metallised film Polymers 0.000 claims description 9
- 239000000969 carrier Substances 0.000 claims description 6
- 230000008859 change Effects 0.000 claims description 6
- 230000008569 process Effects 0.000 claims description 6
- 230000006872 improvement Effects 0.000 claims description 5
- 230000000087 stabilizing effect Effects 0.000 claims description 3
- 238000012360 testing method Methods 0.000 claims description 3
- 238000004891 communication Methods 0.000 description 6
- 238000010586 diagram Methods 0.000 description 5
- 238000012546 transfer Methods 0.000 description 4
- 230000008901 benefit Effects 0.000 description 3
- 230000007423 decrease Effects 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 230000004075 alteration Effects 0.000 description 1
- 230000033228 biological regulation Effects 0.000 description 1
- 238000011217 control strategy Methods 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 239000000428 dust Substances 0.000 description 1
- 230000005672 electromagnetic field Effects 0.000 description 1
Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/007—Regulation of charging or discharging current or voltage
- H02J7/00712—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters
- H02J7/007182—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters in response to battery voltage
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J2207/20—Charging or discharging characterised by the power electronics converter
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Computer Networks & Wireless Communication (AREA)
- Dc-Dc Converters (AREA)
- Charge And Discharge Circuits For Batteries Or The Like (AREA)
- Secondary Cells (AREA)
Abstract
The embodiment of the invention provides a storage battery rapid wireless charging circuit which is characterized by being applied to a magnetic resonance wireless energy transmission system and comprising a power conversion circuit and a control circuit, wherein the power conversion circuit is connected between a full-bridge rectifying circuit and a battery load of a receiving end circuit in the magnetic resonance wireless energy transmission system and is used for adjusting output voltage and power to meet the charging requirement of a storage battery; the control circuit is used for realizing two stages of maximum efficiency charging and constant voltage charging of the storage battery.
Description
Technical Field
The invention belongs to the technical field of wireless power transmission power management, and relates to a power conversion circuit for rapid wireless charging of a storage battery.
Background
Compared with the traditional wired power supply mode through the plug-in mode, the wireless energy transmission technology is more suitable for the environment with dust and outer space, and avoids the problems that a socket is easy to age, easy to pollute, instant plug-in discharge exists in wired plug-in charging, so that the technology is more and more important in the aerospace field.
The magnetic resonance wireless energy transmission system can thoroughly and physically isolate the circuits at the transmitting end and the receiving end, can realize wireless power supply for external equipment and a detector, prolongs the service life of the external equipment and the detector, and does not need to be retransmitted frequently so as to reduce the cost. But the transmitting end and the receiving end are completely physically isolated, and the circuit information of the other end cannot be directly obtained by the two ends, so that the high-efficiency and high-power lithium battery charging is realized, and higher requirements are put on the wireless energy transmission circuit topology structure and the control strategy thereof.
The magnetic resonance wireless energy transmission system can generate an alternating electromagnetic field to transmit energy, and meanwhile, under the aerospace environment, the communication control is not very reliable, so that a standby control scheme without communication needs to be researched, the communication wireless energy transmission system can still work normally under the condition of communication failure, and the complexity of a communication circuit and control is reduced.
The traditional series-series resonant network has the advantages of being capable of realizing the input of zero impedance angle and soft switching due to few passive devices, simple in design and good in constant current output characteristic, and is a good choice for wireless charging of lithium batteries. However, the existing wireless charging system adopts the traditional constant voltage and constant current mode for control, the efficiency is not high, and meanwhile, the complexity of a control circuit is improved due to the requirement of communication.
Disclosure of Invention
The invention aims to provide a storage battery rapid wireless charging circuit which is characterized by being applied to a magnetic resonance wireless energy transmission system and comprising a power conversion circuit and a control circuit, wherein the power conversion circuit is connected between a full-bridge rectifying circuit and a battery load of a receiving end circuit in the magnetic resonance wireless energy transmission system and is used for adjusting output voltage and power to meet the charging requirement of a storage battery; the control circuit is used for realizing two stages of maximum efficiency charging and constant voltage charging of the storage battery.
Preferably, the power conversion circuit comprises a shunt regulator and a Buck circuit, wherein the shunt regulator is composed of a switching tube Q1, a diode D1 and a voltage stabilizing filter capacitor C1, the switching tube Q2, the diode D2, a filter inductor L1 and the filter capacitor C2.
Preferably, the current output by the full-bridge rectifying circuit flows through the diode D1 to charge the capacitor C1, so that the output of the conventional S-S wireless energy transfer circuit is converted from a current source to a voltage source.
Preferably, by changing the duty ratio, the switching tube Q2 can be continuously turned on and off, when turned on, the current directly flows through the inductor to charge the capacitor and the battery, and when turned off, the inductor L1 freewheels to discharge the capacitor and the battery, and the diode D2 serves as a connector of the current loop; the duty cycle represents the different ratio between the output voltage, i.e. the voltage Uc across the capacitor C2, and the input voltage, i.e. the voltage Uo across the capacitor C1.
Preferably, the control circuit comprises a voltage sampling module, a PI controller, a big circuit, a comparator, a subtracter, a triangular carrier generating circuit and a driving circuit; the control circuit controls the switching tubes Q1 and Q2 in the same way; the voltage sampling module is used for collecting voltage Uc on C1 and voltage Uo on C2; when the control circuit controls the switching tube Q1, a sampling value and a given value Uref1 of the output voltage Uo are connected to two ends of the PI controller, a PI output signal of the PI controller is connected to one end of the comparator, the other end of the PI output signal is connected to the triangular carrier generating circuit, after the PI output signal passes through the comparator, when the positive end input is higher than the negative end input, the output is high, otherwise, the output is zero, a square wave control signal with a certain duty ratio is formed, and the on-off state of the switching tube Q1 is changed through the driving circuit.
Preferably, the control circuit further comprises a maximum efficiency point tracking MPET linear fitting circuit, the maximum efficiency point tracking MPET linear fitting circuit obtains that when the maximum efficiency is output, the front end voltage of the Buck circuit and the output voltage have a linear relation through analyzing the relation between the efficiency and the front end voltage of the Buck circuit and the output sampling voltage, and the maximum efficiency charging is achieved by using the circuit as a given PI controller.
Preferably, the comparator comprises a comparator 1 and a comparator 2, the switching tube has two working states, and only one switching tube in each working state needs a soft switching control method when PWM wave control is needed; under the split-domain control, the triangular carriers of the comparator 1 and the comparator 2 do not need to be identical, and may be different carriers.
Preferably, the Buck circuit of the power variation circuit has two operation modes, including a maximum efficiency charging mode and a constant voltage charging mode; the maximum efficiency charging mode is that a switching tube Q1 is in a normally-off state, and a switching tube Q2 is in a modulation state; the constant voltage charging mode is that the switching tube Q1 is in a modulation state, and the switching tube Q2 is in a normally-on state.
Preferably, when the lithium battery does not reach the charge threshold voltage, the changer operates in a maximum efficiency charge mode, and the specific steps are as follows:
Step 1: the input of the maximum efficiency tracking (MEPT) linear fitting circuit is a sampling value of output voltage, and the sampling ratio of the output voltage is consistent with that of the front end voltage; through actual test, the front-end voltage and the output voltage meet the linear relation in the state of the maximum efficiency working point; the output of the MEPT linear fitting circuit is used as the negative phase input Uref2 of the PI controller 2;
Step 2: the negative-phase input Uref1 of the PI controller 1 is equal to the threshold voltage multiplied by the sampling ratio k of the lithium battery, the positive-phase input of the PI controller 1 is an output voltage sampling value, and when the voltage of the lithium battery does not reach the threshold voltage, the output of the PI controller 1 is zero;
step 3: the negative phase input of the PI controller 2 is a given value from MPET algorithm, the positive phase input of the PI controller 2 is a sampling value of front-end voltage, and the front-end voltage of the Buck circuit is regulated through PI;
step 4: at this time, the output of the PI controller 1 is zero, and the PI controller 2 works normally, and the output is larger than zero, so that the output value of the large circuit is taken as the output of the PI controller 2; the output of the big circuit is the positive phase input of the comparator 2 and is also the positive phase input of the subtracter; the negative phase input Vref of the subtracter needs to be larger than the maximum value of the triangular carrier 2, so that the domains of the comparator 1 and the comparator 2 are completed;
Step 5: the value range of the triangular wave 1 at the negative end of the comparator 1 is [ V1, V2], the value range of the triangular wave 2 at the negative end of the comparator 2 is [ V3, V4], the output value of the large circuit is larger than V1 and smaller than V2 at the moment through self-adaptive adjustment of the PI controller, the comparator 2 outputs PWM waveforms, and the switching tube Q2 is adjusted to be in a modulation state through the Buck driving circuit; since Vref is greater than V2, the comparator 1 outputs a low level, and the switching tube Q1 is regulated to be in a normally-off state by the shift driving circuit.
Preferably, when the lithium battery reaches the charge threshold voltage, the converter operates in a constant voltage charge mode, comprising the following steps:
Step 1: when the sampling value of the input and output voltage at the positive end of the PI controller 1 reaches the vicinity of the given value of the negative end, the output of the PI controller 1 starts to rise continuously; when the output of the PI controller 1 is larger than that of the PI controller 2, the large output is taken as the output of the PI controller 1, so that the duty ratio of the Buck driving tube is continuously increased after the output of the PI controller 1 passes through the comparator 2 until the Buck tube is directly connected, and the output is in a flexible switching state;
Step 2: the negative phase input of the PI controller 2 is given that Uref2 is larger than the front end voltage sampling value of the positive phase input, so that the output of the PI controller 2 is zero; the positive and negative phase input of the PI controller 1 has small errors, is in a linear working area, and the PI output enters another block range;
step 3: the output of the PI controller 1 is passed through the big circuit, and is self-adaptively regulated by the subtracter and the PI controller at the moment, and the output value is larger than (V3+Vref) and smaller than (V4+Vref); the output value subtracts the negative phase input value Vref of the subtracter, the input value of the positive phase input end of the comparator 1 is greater than V3 and smaller than V4, so that the comparator 1 outputs PWM waves, and the switch tube driving circuit controls the switch tube Q1 to be in an adjusting state;
Step 4: taking a large output value larger than (V < 3+ > Vref), wherein Vref is larger than V < 2 >, so that the output of the comparator 2 is high level, and regulating the switching tube Q2 to be in a normally-on state through the Buck tube driving circuit;
Step 5: when the switching tube Q1 is switched on, the receiving end circuit is in a short circuit state, and the battery load is powered by the capacitor C2; when the receiving end is short-circuited, the power of the transmitting end is suddenly reduced, so that the power of the transmitting end is automatically adjusted along with the continuous improvement of the duty ratio of the shunt tube Q1, and when the charging is finished, the power of the transmitting end is reduced to be extremely low, and the transmitting end can be automatically cut off through a detecting circuit of the transmitting end, so that the whole charging process is finished.
The dual-mode charging control mode provided by the invention can automatically change along with the charging state, reduces the power input, and has the main protection effect of shunting without consuming a large amount of power on the shunt tube. The shunt tube acts to control output voltage, the duty ratio of the shunt tube changes to change input impedance, the power of the transmitting end gradually decreases along with the increase of the duty ratio, and finally, when the power reaches less than the lower power limit threshold value, the transmitting end is powered off to complete the charging process.
The invention provides an efficient communication-free wireless charging circuit and a control mode, and realizes dual-mode charging of a lithium battery by utilizing a hardware circuit mode.
Drawings
FIG. 1 is a block diagram of a magnetic resonance wireless energy transfer system;
FIG. 2 is a diagram of an improved power variation circuit in a block diagram of a magnetic resonance wireless energy transfer system;
FIG. 3 is a diagram of an improved control circuit in a block diagram of a magnetic resonance wireless energy transfer system.
Detailed Description
In order that the above-recited objects, features and advantages of the present invention will become more readily apparent, a more particular description of the invention will be rendered by reference to the appended drawings and appended detailed description.
In order to overcome the defect of low efficiency, a circuit topology is provided, namely a primary DC-DC converter is added at a receiving end, and direct current impedance matching is carried out on a battery. Based on the circuit topology, a corresponding control method and a corresponding control circuit are provided.
In order to meet the aim of quick charge of a storage battery, the invention provides a circuit topology which is added with a shunt pipe after using a traditional series-series resonance network and is cascaded with a back-stage Buck circuit, and has the capability of adapting to different battery loads and automatically adjusting primary side input power.
Based on the circuit topology, the invention provides a control method for realizing dual-mode charging of a lithium battery, and the two modes of maximum-efficiency charging and constant-voltage charging are flexibly switched by combining a Buck circuit and a shunt circuit. And the purpose of protecting the battery load is realized by utilizing the shunt tube, and the power-off operation of ending the charging is realized by means of impedance change.
The invention provides a maximum efficiency-constant voltage charging dual-mode control circuit and a method thereof, wherein: and when the output voltage is equal to the threshold voltage of the battery, the Buck converter firstly carries out constant voltage regulation, the duty ratio of a switching tube of the Buck converter is continuously regulated until the full-pass state, and the shunt tube acts, so that the flexible conversion process is realized.
The dual-mode charging control mode provided by the invention can automatically change along with the charging state, reduces the power input, and has the main protection effect of shunting without consuming a large amount of power on the shunt tube. The shunt tube acts to control output voltage, the duty ratio of the shunt tube changes to change input impedance, the power of the transmitting end gradually decreases along with the increase of the duty ratio, and finally, when the power reaches less than the lower power limit threshold value, the transmitting end is powered off to complete the charging process.
The invention provides an efficient communication-free wireless charging circuit and a control mode, and realizes dual-mode charging of a lithium battery by utilizing a hardware circuit mode.
In fig. 1, a magnetic resonance wireless energy transmission system in the prior art mainly comprises a direct current power supply, a high-frequency inverter, a primary side compensation network, a transmitting coil, a receiving coil, a secondary side compensation network, a rectifier, a power conversion circuit and a battery load. The power supply comprises a direct current power supply, a high-frequency inverter, a primary side compensation network, a transmitting coil, a receiving coil, a secondary side compensation network, a rectifier, a power conversion circuit and a battery load. When the lithium battery does not reach the charging threshold voltage, the maximum efficiency working point of the string resonance is utilized to carry out impedance matching and then charge with the maximum efficiency; and after the lithium battery reaches the charging threshold voltage, constant-voltage charging is performed until the lithium battery reaches a trickle charging state, and the power supply is cut off to finish charging. The present invention is primarily an improvement over the power conversion circuit and control circuit of fig. 1.
As shown in fig. 2, the improved power conversion circuit comprises a shunt regulator and a Buck circuit, wherein the shunt regulator is composed of a switching tube Q1, a diode D1 and a voltage stabilizing filter capacitor C1, the switching tube Q2, the diode D2, a filter inductor L1 and a filter capacitor C2. The power converter is connected after the rectifier, and the rectified current flows through the diode D1 to charge the capacitor C1, so that the output of the traditional S-S wireless energy transmission circuit can be converted into a voltage source from a current source. Under certain duty ratio control, the switching tube Q2 can be continuously turned on and off, current directly flows through the inductor during the turn-on, the capacitor and the battery are charged, the inductor L1 freewheels to discharge to the capacitor and the battery during the turn-off, and the diode D2 serves as a connector of a current loop. Wherein diode D3 is an important protection against short-circuit discharge between the capacitor and the battery. The different duty cycles represent different ratios between the output voltage (voltage Uc on capacitor C2) and the input voltage (voltage Uo on capacitor C1), so that the battery can still be supplied with electrical energy when it is boosted as the state of charge changes.
The added shunt regulating circuit is an important improvement, and the problem that the battery needs to be trickle charged can not be solved by only using the Buck circuit under the condition that the battery is charged for most of the time and is not fully loaded, the output characteristic of the common wireless energy transmission system is a constant current source, the battery can not be fully charged without the shunt regulating function, and the battery is extremely easy to be damaged by large current when the voltage threshold value of the battery is reached.
As shown in fig. 3, the improved control circuit comprises a voltage sampling module (voltage Uc on C1 and voltage Uo on C2), a PI controller, a sampling circuit, a comparator, an adder, a triangular carrier generating circuit and a driving circuit. The control circuit controls two switching transistors Q1, Q2, and one of them is taken as an example of the workflow. The general control signal flow is: the sampling value and the given value Uref1 of the output voltage Uo are connected to two ends of a PI controller, the PI output signal is connected to one end of a comparator, the other end of the PI output signal is connected to a triangular carrier wave, after the PI output signal passes through the comparator, when the positive end input is higher than the negative end input, the output is high, otherwise, the output is zero, a square wave control signal with a certain duty ratio is formed, and the on-off state of a switching tube can be changed through a driving circuit.
In addition, the maximum efficiency point tracking (MPET) linear fitting circuit is used for obtaining the linear relation between the front end voltage of the Buck and the output voltage when the maximum efficiency is output through analyzing the relation between the efficiency, the front end voltage of the Buck and the output sampling voltage, and the circuit is used as a given PI controller to realize the charging of the maximum efficiency.
The big circuit and the subtracter are core circuits for realizing domain control, which is a soft switching control method when only one switching tube needs PWM wave control in each working state. Under the split-domain control, the triangular carriers of the comparator 1 and the comparator 2 do not have to be identical, but can be different carriers, which is an important advantage.
Next, a control method of the circuit topology will be described.
In fig. 2, the Buck converter with shunt function has two modes of operation:
Maximum efficiency charging mode: the switching tube Q1 is in a normally-off state, and the switching tube Q2 is in a modulation state;
constant voltage charging mode: the switching tube Q1 is in a modulation state, and the switching tube Q2 is in a normally-on state.
Fig. 3 is a control circuit and method based on a Buck converter with a Shunt function, which comprises output voltage sampling, front-end voltage sampling, a maximum efficiency tracking (MPET) linear fitting circuit, a PI controller 1, a PI controller 2, a subtracter, a comparator 1, a comparator 2, a modulating wave circuit, a big circuit, a Buck driving circuit, a Shunt (Shunt) driving circuit and other modules.
When the lithium battery does not reach the charging threshold voltage, the changer works in a maximum efficiency charging mode, and the specific steps are as follows:
step 1: the input of the maximum efficiency tracking (MEPT) linear fitting circuit is a sampling value of the output voltage, and the sampling ratio of the output voltage is k consistent with that of the front end voltage. By utilizing the characteristic that the string resonance network has the maximum efficiency working point, and is influenced by the efficiency of the two-stage cascade connection of the Buck converter, the actual output still has the maximum efficiency output working point, but the maximum efficiency output working point is offset compared with the maximum efficiency working point of the string resonance network. According to practical tests, the front-end voltage and the output voltage in the maximum efficiency working point state meet the linear relation. The output of the linear fit circuit through MEPT is taken as the negative phase input Uref2 of PI controller 2.
Step 2: the negative-phase input Uref1 of the PI controller 1 is equal to the threshold voltage of the lithium battery multiplied by the sampling ratio k, the positive-phase input of the PI controller 1 is an output voltage sampling value, and when the voltage of the lithium battery does not reach the threshold voltage, the output of the PI controller 1 is zero.
Step 3: the negative phase input of the PI controller 2 is a given value from the MPET algorithm, the positive phase input of the PI controller 2 is a sampling value of the front-end voltage, and the front-end voltage of the Buck circuit is regulated by PI.
Step 4: at this time, the output of the PI controller 1 is zero, and the PI controller 2 works normally, and the output is greater than zero, so the output value of the large circuit is taken as the output of the PI controller 2. The output of the inverting circuit is the non-inverting input of the comparator 2 and is also the non-inverting input of the subtractor. The negative phase input Vref of the subtracter needs to be larger than the maximum value of the triangular carrier 2, so that the domains of the comparator 1 and the comparator 2 are completed.
Step 5: the value range of the triangular wave 1 at the negative end of the comparator 1 is [ V1, V2], the value range of the triangular wave 2 at the negative end of the comparator 2 is [ V3, V4], the output value of the large circuit is larger than V1 and smaller than V2 at the moment through self-adaptive adjustment of the PI controller, the comparator 2 outputs PWM waveforms, and the switching tube Q2 is adjusted to be in a modulation state through the Buck driving circuit; since Vref is greater than V2, the comparator 1 outputs a low level, and the switching tube Q1 is regulated to be in a normally-off state by the shift driving circuit.
When the lithium battery reaches the charging threshold voltage, the converter works in a constant voltage charging mode, and the specific steps are as follows:
step 1: when the positive input output voltage sampling value of the PI controller 1 reaches the vicinity of the negative end given value, the output of the PI controller 1 starts to rise continuously. When the output of the PI controller 1 is larger than that of the PI controller 2, the large output is taken as the output of the PI controller 1, so that the duty ratio of the Buck driving tube is continuously increased after the output of the PI controller 1 passes through the comparator 2 until the Buck tube is directly connected, and the output is in a flexible switching state.
Step 2: the negative phase input of the PI controller 2 gives Uref2 greater than the positive phase input front end voltage sample value, so the PI controller 2 output is zero. The positive and negative phase inputs of the PI controller 1 have small errors, are in a linear operating region, and the PI output enters another block range.
Step 3: the output of the PI controller 1 is passed through the big circuit, and is self-adaptively regulated by the subtracter and the PI controller, and the output value is larger than (V3+Vref) and smaller than (V4+Vref). The output value minus the minus phase input value Vref of the subtracter, the input value of the positive phase input end of the comparator 1 is greater than V3 and smaller than V4, so that the comparator 1 outputs PWM waves, and the switch tube driving circuit controls the switch tube Q1 to be in an adjusting state.
Step 4: the large output value is larger than (V < 3+ > Vref), and the Vref is larger than V <2 >, so that the output of the comparator 2 is high level, and the switching tube Q2 is regulated to be in a normally-on state through the Buck tube driving circuit.
Step 5: when the switching tube Q1 is switched on, the receiving end circuit is in a short circuit state, and the battery load is powered by the capacitor C2; when the receiving end is short-circuited, the power of the transmitting end is suddenly reduced, so that the power of the transmitting end is automatically adjusted along with the continuous improvement of the duty ratio of the shunt tube Q1, and when the charging is finished, the power of the transmitting end is reduced to be extremely low, and the transmitting end can be automatically cut off through a detecting circuit of the transmitting end, so that the whole charging process is finished.
It will be apparent to those skilled in the art that various modifications and variations can be made to the present invention without departing from the spirit or scope of the invention. Thus, it is intended that the present invention also include such modifications and alterations insofar as they come within the scope of the appended claims or the equivalents thereof.
Claims (6)
1. The quick wireless charging circuit for the storage battery is characterized by being applied to a magnetic resonance wireless energy transmission system and comprising a power conversion circuit and a control circuit, wherein the power conversion circuit is connected between a full-bridge rectifying circuit of a receiving end circuit in the magnetic resonance wireless energy transmission system and a battery load and is used for adjusting output voltage and power to meet the charging requirement of the storage battery; the control circuit is used for realizing two stages of maximum efficiency charging and constant voltage charging of the storage battery;
The power conversion circuit comprises a shunt regulator consisting of a switching tube Q1, a diode D1 and a voltage stabilizing filter capacitor C1, and a Buck circuit consisting of a switching tube Q2, a diode D2, a filter inductor L1 and a filter capacitor C2;
the current output by the full-bridge rectifying circuit flows through a diode D1 to charge a capacitor C1, so that the output of a traditional S-S wireless energy transmission circuit is converted into a voltage source from a current source;
By changing the duty ratio, the switching tube Q2 can be continuously turned on and off, current directly flows through the inductor during the turn-on, the capacitor and the battery are charged, the inductor L1 is continuously discharged to the capacitor and the battery during the turn-off, and the diode D2 serves as a connector of a current loop; the duty cycle represents the different ratio between the output voltage, i.e. the voltage Uc across the capacitor C2, and the input voltage, i.e. the voltage Uo across the capacitor C1;
The control circuit comprises a voltage sampling module, a PI controller, a big taking circuit, a comparator, a subtracter, a triangular carrier generating circuit and a driving circuit; the control circuit controls the switching tubes Q1 and Q2 in the same way; the voltage sampling module is used for collecting voltage Uc on C1 and voltage Uo on C2; when the control circuit controls the switching tube Q1, a sampling value and a given value Uref1 of the output voltage Uo are connected to two ends of the PI controller, a PI output signal of the PI controller is connected to one end of the comparator, the other end of the PI output signal is connected to the triangular carrier generating circuit, after the PI output signal passes through the comparator, when the positive end input is higher than the negative end input, the output is high, otherwise, the output is zero, a square wave control signal with a certain duty ratio is formed, and the on-off state of the switching tube Q1 is changed through the driving circuit.
2. The rapid wireless charging circuit of claim 1, wherein the control circuit further comprises a maximum efficiency point tracking MPET linear fitting circuit, the maximum efficiency point tracking MPET linear fitting circuit obtains that when the maximum efficiency is output, the front end voltage of the Buck circuit has a linear relation with the output voltage by analyzing the relation between the efficiency and the front end voltage of the Buck circuit and the output sampling voltage, and the maximum efficiency charging is realized by using the circuit as a given PI controller.
3. The rapid wireless charging circuit of claim 2, wherein the comparator comprises a comparator 1 and a comparator 2, the switching tube has two working states, and only one switching tube in each working state needs a soft switching control method when PWM wave control is needed; under the split-domain control, the triangular carriers of the comparator 1 and the comparator 2 do not need to be identical, and may be different carriers.
4. The battery quick wireless charging circuit of claim 3, wherein the Buck circuit of the power change circuit has two modes of operation, including a maximum efficiency charging mode and a constant voltage charging mode; the maximum efficiency charging mode is that a switching tube Q1 is in a normally-off state, and a switching tube Q2 is in a modulation state; the constant voltage charging mode is that the switching tube Q1 is in a modulation state, and the switching tube Q2 is in a normally-on state.
5. The battery quick wireless charging circuit of claim 4, wherein the variator operates in a maximum efficiency charging mode when the lithium battery does not reach a charge threshold voltage, comprising the steps of:
Step 1: the input of the maximum efficiency tracking (MEPT) linear fitting circuit is a sampling value of output voltage, and the sampling ratio of the output voltage is consistent with that of the front end voltage; through actual test, the front-end voltage and the output voltage meet the linear relation in the state of the maximum efficiency working point; the output of the MEPT linear fitting circuit is used as the negative phase input Uref2 of the PI controller 2;
Step 2: the negative-phase input Uref1 of the PI controller 1 is equal to the threshold voltage multiplied by the sampling ratio k of the lithium battery, the positive-phase input of the PI controller 1 is an output voltage sampling value, and when the voltage of the lithium battery does not reach the threshold voltage, the output of the PI controller 1 is zero;
step 3: the negative phase input of the PI controller 2 is a given value from MPET algorithm, the positive phase input of the PI controller 2 is a sampling value of front-end voltage, and the front-end voltage of the Buck circuit is regulated through PI;
step 4: at this time, the output of the PI controller 1 is zero, and the PI controller 2 works normally, and the output is larger than zero, so that the output value of the large circuit is taken as the output of the PI controller 2; the output of the big circuit is the positive phase input of the comparator 2 and is also the positive phase input of the subtracter; the negative phase input Vref of the subtracter needs to be larger than the maximum value of the triangular carrier 2, so that the domains of the comparator 1 and the comparator 2 are completed;
Step 5: the value range of the triangular wave 1 at the negative end of the comparator 1 is [ V1, V2], the value range of the triangular wave 2 at the negative end of the comparator 2 is [ V3, V4], the output value of the large circuit is larger than V1 and smaller than V2 at the moment through self-adaptive adjustment of the PI controller, the comparator 2 outputs PWM waveforms, and the switching tube Q2 is adjusted to be in a modulation state through the Buck driving circuit; since Vref is greater than V2, the comparator 1 outputs a low level, and the switching tube Q1 is regulated to be in a normally-off state by the shift driving circuit.
6. The battery quick wireless charging circuit of claim 4, wherein the converter operates in a constant voltage charging mode when the lithium battery reaches a charge threshold voltage, comprising the steps of:
Step 1: when the sampling value of the input and output voltage at the positive end of the PI controller 1 reaches the vicinity of the given value of the negative end, the output of the PI controller 1 starts to rise continuously; when the output of the PI controller 1 is larger than that of the PI controller 2, the large output is taken as the output of the PI controller 1, so that the duty ratio of the Buck driving tube is continuously increased after the output of the PI controller 1 passes through the comparator 2 until the Buck tube is directly connected, and the output is in a flexible switching state;
Step 2: the negative phase input of the PI controller 2 is given that Uref2 is larger than the front end voltage sampling value of the positive phase input, so that the output of the PI controller 2 is zero; the positive and negative phase input of the PI controller 1 has small errors, is in a linear working area, and the PI output enters another block range;
step 3: the output of the PI controller 1 is passed through the big circuit, and is self-adaptively regulated by the subtracter and the PI controller at the moment, and the output value is larger than (V3+Vref) and smaller than (V4+Vref); the output value subtracts the negative phase input value Vref of the subtracter, the input value of the positive phase input end of the comparator 1 is greater than V3 and smaller than V4, so that the comparator 1 outputs PWM waves, and the switch tube driving circuit controls the switch tube Q1 to be in an adjusting state;
Step 4: taking a large output value larger than (V < 3+ > Vref), wherein Vref is larger than V < 2 >, so that the output of the comparator 2 is high level, and regulating the switching tube Q2 to be in a normally-on state through the Buck tube driving circuit;
Step 5: when the switching tube Q1 is switched on, the receiving end circuit is in a short circuit state, and the battery load is powered by the capacitor C2; when the receiving end is short-circuited, the power of the transmitting end is suddenly reduced, so that the power of the transmitting end is automatically adjusted along with the continuous improvement of the duty ratio of the shunt tube Q1, and when the charging is finished, the power of the transmitting end is reduced to be extremely low, and the transmitting end can be automatically cut off through a detecting circuit of the transmitting end, so that the whole charging process is finished.
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