CN112436268A - Dual-beam frequency scanning leaky-wave antenna - Google Patents
Dual-beam frequency scanning leaky-wave antenna Download PDFInfo
- Publication number
- CN112436268A CN112436268A CN202011228493.6A CN202011228493A CN112436268A CN 112436268 A CN112436268 A CN 112436268A CN 202011228493 A CN202011228493 A CN 202011228493A CN 112436268 A CN112436268 A CN 112436268A
- Authority
- CN
- China
- Prior art keywords
- metal panel
- axis
- impedance modulation
- top metal
- dielectric substrate
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/08—Radiating ends of two-conductor microwave transmission lines, e.g. of coaxial lines, of microstrip lines
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/20—Non-resonant leaky-waveguide or transmission-line antennas; Equivalent structures causing radiation along the transmission path of a guided wave
Abstract
The invention discloses a dual-beam frequency scanning leaky-wave antenna, which consists of a dielectric substrate, a top metal panel, a bottom metal panel and a metal tube, wherein the dielectric substrate is a metal substrate; the invention adopts a half-mode substrate integrated waveguide structure, and is based on a periodic sinusoidal impedance modulation principle, a double-periodic sinusoidal impedance modulation groove is arranged on a top metal panel to be used as a radiation unit, and because the top metal panel is formed by superposing sinusoidal impedances of two single beams, beams in two radiation directions can be generated; the bottom metal panel is also provided with the periodically-changed groove as the radiation unit, so that the radiation efficiency of the antenna can be improved, the stop band effect of the periodic leaky-wave antenna can be inhibited, and compared with the traditional dual-beam frequency scanning antenna, the periodic leaky-wave antenna has the characteristics of simple structure, narrow bandwidth, large scanning angle and the like.
Description
Technical Field
The invention relates to the technical field of microwave, wireless communication and test simulation, in particular to a dual-beam frequency scanning leaky-wave antenna based on periodic sinusoidal impedance modulation.
Background
The leaky-wave antenna is a traveling-wave antenna, has simple structure, frequency scanning capability and excellent directivity, and is widely applied to the fields of radar, aerospace and the like. Since the invention of leaky-wave antenna, the technology has been mature so far, and can be divided into the following four categories: uniform, quasi-uniform, periodic, and left-right hand composite leaky-wave antenna. The periodic leaky-wave antenna is an antenna for exciting higher harmonics to radiate, and because the conventional periodic leaky-wave antenna has the problems of narrow scanning angle, large bandwidth, difficulty in realizing dual-beam scanning and the like, how to realize the dual-beam frequency scanning antenna with large range and narrow bandwidth becomes a key point for designing the leaky-wave antenna.
The most common method for increasing the scanning range is to increase the scanning frequency range, but this results in a relatively large bandwidth and occupies too much spectrum resources. In addition, in order to implement dual-beam radiation, the conventional method is to implement dual-beam by using-1 st and-2 nd harmonic radiation together, or to implement dual-beam by integrating two antennas with different radiation directions, but this causes problems of difficult design, complex structure, increased cost, etc. The design of the invention is to superpose two different sinusoidal periodic impedances together, so that the dual-beam radiation can be realized only by representing the height of a surface groove corresponding to the superposed impedance, and the antenna has the characteristics of simplified structure, narrow bandwidth and large scanning angle.
Disclosure of Invention
The invention aims at the defects of the prior art and provides a dual-beam frequency scanning leaky-wave antenna which is composed of a dielectric substrate, a top metal panel, a bottom metal panel and a metal tube; the invention adopts a half-mode substrate integrated waveguide structure, and is based on a periodic sinusoidal impedance modulation principle, a double-periodic sinusoidal impedance modulation groove is arranged on a top metal panel to be used as a radiation unit, and because the top metal panel is formed by superposing sinusoidal impedances of two single beams, beams in two radiation directions can be generated; the bottom metal panel is also provided with the periodically-changed groove as the radiation unit, so that the radiation efficiency of the antenna can be improved, the stop band effect of the periodic leaky-wave antenna can be inhibited, and compared with the traditional dual-beam frequency scanning antenna, the periodic leaky-wave antenna has the characteristics of simple structure, narrow bandwidth, large scanning angle and the like.
The specific technical scheme for realizing the purpose of the invention is as follows:
a dual-beam frequency scanning leaky-wave antenna is characterized by comprising a dielectric substrate, a top metal panel, a bottom metal panel and a metal tube;
the medium substrate, the top metal panel and the bottom metal panel are arranged in the same rectangular coordinate system.
The dielectric substrate is a rectangular Rogers RT5880, a rectangular coordinate system is arranged by taking the center of the plate surface as an original point, an X axis is arranged along the length direction of the plate surface, a Y axis is arranged along the width direction of the plate surface, and the plate surface is divided into four quadrants by the rectangular coordinate;
the top metal panel is rectangular, the length of the top metal panel is equal to that of the dielectric substrate, and the width of the top metal panel is one half of that of the dielectric substrate; the top metal panel is attached to the front surface of the medium substrate and is coincided with a first quadrant and a second quadrant of a rectangular coordinate system on the medium substrate, and the bottom edge of the top metal panel is coincided with the X axis of the medium substrate;
the bottom metal panel is rectangular, and the length and the width of the bottom metal panel are equal to those of the dielectric substrate; the bottom metal panel is attached to the back surface of the dielectric substrate and is coincided with four quadrants of a rectangular coordinate system on the dielectric substrate;
a row of round holes are respectively formed in the top edges of the medium substrate, the top metal panel and the bottom metal panel in parallel to the X axis; the three rows of round holes are in one-to-one correspondence;
the metal tubes are multiple, penetrate through the round holes of the medium substrate, and two ends of each metal tube are respectively connected with the round hole of the top metal panel and the round hole of the bottom metal panel.
Curves are arranged in the first quadrant and the second quadrant on the top metal panel, the curves and the Y axis are symmetrical to form a semi-cloud-shaped impedance modulation area, and rectangular microstrip feed lines and trapezoidal impedance matching microstrip lines are symmetrically cut out from two ends of the top metal panel along the X axis;
the top metal panel is provided with a plurality of elongated slots in a semi-cloud-shaped impedance modulation area along an X axis, the bottoms of the elongated slots are flush with the bottom edge of the top metal panel, and the tops of the elongated slots are tangent to the curve of the semi-cloud-shaped impedance modulation area;
the bottom metal panel is provided with a full-cloud-shaped impedance modulation area, and the full-cloud-shaped impedance modulation area is formed by two half-cloud-shaped impedance modulation areas which are symmetrical along an X axis;
the bottom metal panel is provided with a plurality of elongated slots in the full-cloud-shaped impedance modulation area along the X axis, the length of each elongated slot is twice that of the elongated slot in the half-cloud-shaped impedance modulation area, and the top and the bottom of each elongated slot are tangent to a curve forming the full-cloud-shaped impedance modulation area respectively.
The curve of the top metal panel in the first quadrant is composed of two parts along the X axis, the first part is a linear curve with gradually changed height, and the long groove arranged in the linear curve area is an impedance matching groove; the second part is a double-period sine curve, and the long grooves arranged in the area of the double-period sine curve are double-period sine impedance modulation grooves.
The dual-period sine impedance modulation slot is a dual-period sine impedance modulation result with the period of 40mm, which is obtained by respectively multiplying the sine impedance modulation results with the periods of 10mm and 8mm by the coefficient of 0.5 and then superposing the two results, and is positioned in the second part, wherein two period slots of the dual-period sine impedance modulation slot are positioned in the positive direction of the X axis, and the other two period slots are positioned in the negative direction of the X axis and are symmetrically arranged with the Y axis.
The impedance matching slots are positioned in the first part, and the height of the impedance matching slots is linearly gradually changed to 0.1 reference unit by taking the adjacent bicycle sinusoidal impedance modulation slots as 1 reference unit; nine long grooves of the impedance matching groove are located in the positive direction of the X axis, and the other nine long grooves are located in the negative direction of the X axis and are symmetrically arranged with the Y axis.
The invention has the beneficial effects that 2 types of elongated slots with periodically and sinusoidally changed impedance are etched and superposed on the metal panel to excite the dual-beam, the first sinusoidal impedance change can realize beam scanning from minus 60 degrees to 2 degrees in the range of 8.9GHz to 9.6GHz, the second sinusoidal impedance change can realize beam scanning from 0 degrees to plus 57 degrees, and the superposed structure can realize the scanning range of 117 degrees. In addition, long grooves with periodically changed etching are also etched on the bottom surface of the substrate and used as radiation units, so that the radiation efficiency can be improved, the forbidden band effect can be inhibited by staggering the bottom grooves and the top grooves for a certain distance in the horizontal position, and the characteristic of continuous scanning is realized. By the method, the dual-beam leaky-wave antenna with a simple structure, a narrow bandwidth and large-range scanning is realized.
Drawings
FIG. 1 is a schematic structural view of the present invention;
FIG. 2 is a schematic view of a top metal panel according to the present invention;
FIG. 3 is a schematic structural diagram of a dielectric substrate according to the present invention;
FIG. 4 is a schematic structural view of a bottom metal panel according to the present invention;
fig. 5 is a schematic diagram illustrating directions of dual beams radiated by the antenna according to the embodiment of the present invention.
Detailed Description
Referring to fig. 1, the present invention includes a dielectric substrate 1, a top metal panel 2, a bottom metal panel 3 and a metal tube 4;
the dielectric substrate 1, the top metal panel 2 and the bottom metal panel 3 are arranged in the same rectangular coordinate system.
Referring to fig. 1 and 3, the dielectric substrate 1 is a rectangular Rogers RT5880, a rectangular coordinate system is arranged at the center O of the plate surface, an X axis is arranged along the length direction of the plate surface, a Y axis is arranged along the width direction of the plate surface, and the plate surface is divided into four quadrants by the rectangular coordinate system.
Referring to fig. 1 and 2, the top metal panel 2 is rectangular, and has a length equal to that of the dielectric substrate 1 and a width half that of the dielectric substrate 1; the top metal panel 2 is attached to the front surface of the dielectric substrate 1 and coincides with the first quadrant and the second quadrant of the rectangular coordinate system on the dielectric substrate 1, and the bottom edge of the top metal panel 2 coincides with the X axis of the dielectric substrate 1.
Referring to fig. 1 and 4, the bottom metal panel 3 is rectangular, and has a length and a width equal to those of the dielectric substrate 1; the bottom metal panel 3 is attached to the back surface of the dielectric substrate 1 and coincides with four quadrants of a rectangular coordinate system on the dielectric substrate 1.
Referring to fig. 1 to 4, a row of circular holes is respectively formed on one side of the top edge of the dielectric substrate 1, the top metal panel 2 and the bottom metal panel 3 in parallel with the X axis; the three rows of round holes are in one-to-one correspondence;
the metal tubes 4 are multiple, the metal tubes 4 penetrate through the round holes of the medium substrate 1, and two ends of each metal tube 4 are respectively connected with the round hole of the top metal panel 2 and the round hole of the bottom metal panel 3.
Referring to fig. 1 and 2, curves are arranged in the first quadrant and the second quadrant of the top metal panel 2, the curves and the Y axis are symmetrical to form a semi-cloud-shaped impedance modulation region 23, and rectangular microstrip feed lines 21 and trapezoidal impedance matching microstrip lines 22 are symmetrically cut out from both ends of the top metal panel 2 along the X axis;
the top metal panel 2 is provided with a plurality of elongated slots arranged along an X axis in the semi-cloud-shaped impedance modulation region 23, the bottoms of the elongated slots are flush with the bottom edge of the top metal panel 2, and the tops of the elongated slots are tangent to the curve of the semi-cloud-shaped impedance modulation region 23.
Referring to fig. 1 and 4, a full-cloud-shaped impedance modulation region (31) is disposed on the bottom metal panel 3, and the full-cloud-shaped impedance modulation region 31 is formed by two half-cloud-shaped impedance modulation regions 23 symmetrically along the X axis;
the bottom metal panel 3 is provided with a plurality of elongated slots arranged along the X axis in the full-cloud-shaped impedance modulation region 31, the length of each elongated slot is twice that of the elongated slot in the half-cloud-shaped impedance modulation region 23, and the top and the bottom of each elongated slot are tangent to the curve forming the full-cloud-shaped impedance modulation region 31.
Referring to fig. 1 and 2, the curve of the top metal panel 2 in the first quadrant is formed by two parts along the X axis, the first part 24 is a linear curve with gradually changed height, and the long groove arranged in the linear curve area is an impedance matching groove; the second portion 25 is a bi-periodic sinusoidal curve with elongated slots in the area of the bi-periodic sinusoidal curve being bi-periodic sinusoidal impedance modulating slots.
Referring to fig. 1 and 2, the dual-period sinusoidal impedance modulation slot is a dual-period sinusoidal impedance modulation slot with a period of 40mm obtained by multiplying the sinusoidal impedance modulation results with periods P of 10mm and P of 8mm by a factor of 0.5, respectively, and is located in the second portion 25, wherein two periodic slots are located in the positive direction of the X axis, and the other two periodic slots are located in the negative direction of the X axis and are symmetrical to the Y axis.
Referring to fig. 1 and 2, the impedance matching slot is located in the first portion 24, and the height of the impedance matching slot is linearly gradually changed to 0.1 reference unit by using 1 reference unit of the adjacent double-period sinusoidal impedance modulation slot; the nine linear gradually-changed long grooves are positioned in the positive direction of the X axis, and the other nine linear gradually-changed long grooves are positioned in the negative direction of the X axis and are symmetrical to the Y axis.
Examples
In order to explain technical contents, achieved objects, and effects of the present invention in detail, the following description is made with reference to the accompanying drawings in combination with the embodiments.
Referring to fig. 1, the embodiment of the present invention is provided with a dielectric substrate 1, wherein metal panels are respectively covered on the top and the bottom of the dielectric substrate 1, and a top metal panel 2 and a bottom metal panel 3 are both printed on the dielectric substrate 1 by using a PCB process.
Referring to fig. 1 and 2, a microstrip feeder line 21 with rectangular two ends of the top metal panel 2 is connected to a trapezoidal impedance matching microstrip line 22, a semi-cloud-shaped impedance modulation region 23 disposed on the top metal panel 2 is divided into two parts, a second part 25 is located in the middle, and an elongated slot thereon is a dual-period sinusoidal impedance modulation slot with periodically-changing etching height; the first portion 24 is located at two ends, and the long groove thereon is an impedance matching groove with the etching height linearly changing.
Referring to fig. 1 and 3, the dielectric substrate 1 is rectangular, made of Rogers RT5880, having a dielectric constant of 2.2, a loss tangent of 0.009, and preferably 1.5mm thick and having dimensions 213mm × 30 mm; the top and bottom metal thicknesses of the dielectric substrate 1 were each set to 0.035mm using copper as the working material.
Referring to fig. 1 and 4, the size of the bottom metal panel 3 is completely the same as that of the dielectric substrate 1, a full-cloud-shaped impedance modulation region 31 is disposed on the bottom metal panel 3, and the full-cloud-shaped impedance modulation region 31 is formed by two half-cloud-shaped impedance modulation regions 23 symmetrically along the X axis; the length of the long groove etched on the full-cloud-shaped impedance modulation region 31 is twice as long as that of the long groove of the half-cloud-shaped impedance modulation region 23 in sequence.
Referring to fig. 1, a row of circular holes is respectively formed on one side of the top edge of the dielectric substrate 1, the top metal panel 2 and the bottom metal panel 3 in parallel to the X axis; the three rows of round holes are in one-to-one correspondence;
referring to fig. 1 to 4, the metal tubes 4 are several, the metal tubes 4 penetrate through the circular holes of the dielectric substrate 1, and two ends of the metal tubes 4 are respectively connected with the circular holes of the top metal panel 2 and the bottom metal panel 3.
Referring to fig. 1-4, in use, to verify the performance of the antenna, three-dimensional full-wave electromagnetic simulation software is used to simulate the performance of the antenna. Wherein a microstrip feed line on the left side of the antenna is connected to a wave port as a feed terminal and on the right side to another wave port as a load absorption terminal, electromagnetic waves are fed into the antenna from the feed terminal, and energy is radiated while propagating in the antenna, a beam directed to a certain direction is generated, and finally, the surplus energy is absorbed at the load absorption terminal.
Referring to fig. 5, a schematic view of the direction of the dual beams radiated by the antenna can be observed by setting a field monitor in the electromagnetic simulation software. The dual-beam leaky-wave antenna based on frequency scanning deflects the beam direction along with the change of the feeding frequency, and radiation patterns of the antenna at the three frequency points are obtained through far-field monitors arranged at 8.9GHz, 9.2GHz and 9.6 GHz. When the feed frequency is 8.9GHz, the antenna can radiate dual beams, the direction of the beam 1 is-60 degrees, and the direction of the beam 2 is 0 degree; when the frequency is increased to 9.2GHz, the beam 1 is steered to-31 ° and the beam 2 is steered to 19 °; as the frequency continues to increase to 9.6GHz, beam 1 is deflected to 2 deg., and beam 2 is deflected to 57 deg., so that the antenna achieves a total of 117 deg. beam sweep in the 8.9 GHz-9.6 GHz band.
Zs(x)＝jXs[1+a1Mf1(x)+a2Mf2(x)] ①
Description of the drawings:
the above two formulas are a double-period sine impedance modulation formula, wherein Z issIs the impedance value at surface coordinate X, j representing the surface impedance with only imaginary part, XsIs a mean surface impedance selected, a1And a2Is the coefficient of two sinusoidal periods, and M is the modulation factor of the sinusoidal modulation function. The formula II is a specific expression of the function in the formula I, and represents a modulation function of two periodic impedances, P1，P2Two different modulation periods. In addition, dispersion curves corresponding to the grooves with different heights are obtained through an eigenmode solver of CST electromagnetic simulation software, and impedance curves corresponding to the heights of the surface grooves are obtained through conversion.
Due to the common stopband effect in the periodic leaky-wave antenna, namely, the antenna generates great reflection in the direction of radiating 0 degrees at the side, and energy cannot be radiated out. The bottom groove is translated by 2.9mm in the positive direction of the X axis relative to the top groove, and the translation is translated by 1.5mm in the positive direction of the Y axis, so that the stop band effect is inhibited.
The metal pipes adopted by the invention are communicated with the upper metal panel and the lower metal panel, so that the row of metal pipes can be equivalent to narrow edges in the rectangular waveguide, and the structure has the capability of conducting electromagnetic waves. The half-mode substrate integrated waveguide structure is obtained by cutting the substrate integrated waveguide into a half along a longitudinal central plane (X axis), and when the substrate integrated waveguide works in a main mode, the longitudinal central plane is equivalent to a magnetic wall, so that the half-mode structure hardly influences the working state of the main mode.
Claims (4)
1. A dual-beam frequency scanning leaky-wave antenna is characterized by comprising a dielectric substrate (1), a top metal panel (2), a bottom metal panel (3) and a metal tube (4);
the medium substrate (1), the top metal panel (2) and the bottom metal panel (3) are arranged in the same rectangular coordinate system;
the medium substrate (1) is a rectangular Rogers plate, a rectangular coordinate system is arranged by taking the center of the plate surface as an original point, an X axis is arranged along the length direction of the plate surface, a Y axis is arranged along the width direction of the plate surface, and the medium substrate is divided into four quadrants;
the top metal panel (2) is rectangular, the length of the top metal panel is equal to that of the dielectric substrate (1), and the width of the top metal panel is one half of that of the dielectric substrate (1); the top metal panel (2) is attached to the front surface of the dielectric substrate (1) and is coincided with a first quadrant and a second quadrant of a rectangular coordinate system on the dielectric substrate (1), and the bottom edge of the top metal panel (2) is coincided with the X axis of the dielectric substrate (1);
the bottom metal panel (3) is rectangular, and the length and the width of the bottom metal panel are equal to those of the dielectric substrate (1); the bottom metal panel (3) is attached to the back surface of the dielectric substrate (1) and is coincided with four quadrants of a rectangular coordinate system on the dielectric substrate (1);
a row of round holes are respectively formed in the top edges of the medium substrate (1), the top metal panel (2) and the bottom metal panel (3) in parallel to the X axis; all rows of round holes are in one-to-one correspondence;
the metal tubes (4) are multiple, the metal tubes (4) penetrate through the round holes of the medium substrate (1), and two ends of each metal tube (4) are respectively connected with the round hole of the top metal panel (2) and the round hole of the bottom metal panel (3);
curves are arranged in the first quadrant and the second quadrant on the top metal panel (2), the curves are symmetrical to the Y axis to form a semi-cloud-shaped impedance modulation area (23), and rectangular microstrip feed lines (21) and trapezoidal impedance matching microstrip lines (22) are symmetrically cut out from the two ends of the top metal panel (2) along the X axis;
the top metal panel (2) is provided with a plurality of elongated slots in the semi-cloud-shaped impedance modulation area (23) along the X axis, the bottoms of the elongated slots are flush with the bottom edge of the top metal panel (2), and the tops of the elongated slots are tangent to the curve of the semi-cloud-shaped impedance modulation area (23);
the bottom metal panel (3) is provided with a full-cloud-shaped impedance modulation region (31), and the full-cloud-shaped impedance modulation region (31) is formed by two half-cloud-shaped impedance modulation regions (23) symmetrically along an X axis;
and a plurality of elongated slots are arranged in the full-cloud-shaped impedance modulation area (31) of the bottom metal panel (3) along the X axis, the length of each elongated slot is twice that of each elongated slot in the half-cloud-shaped impedance modulation area (23), and the top and the bottom of each elongated slot are tangent to the curve forming the full-cloud-shaped impedance modulation area (31) respectively.
2. A dual-beam frequency-scanning leaky-wave antenna as claimed in claim 1, wherein the curve in the first quadrant on said top metal panel (2) is formed by two parts along the X-axis, the first part (24) being a highly graduated linear curve, the elongated slot provided in the area of the linear curve being an impedance matching slot; the second part (25) is a double-period sinusoidal curve, and the long grooves arranged in the area of the double-period sinusoidal curve are double-period sinusoidal impedance modulation grooves.
3. The dual-beam frequency-scanning leaky-wave antenna as claimed in claim 2, wherein said bi-periodic sinusoidal impedance modulation slots are formed by superimposing sinusoidal impedance modulation results having a period P of 10mm and a period P of 8mm by a factor of 0.5, respectively, to obtain a bi-periodic sinusoidal impedance modulation result having a period of 40mm, said bi-periodic sinusoidal impedance modulation slots being located in the second portion (25), wherein two periodic slots of the bi-periodic sinusoidal impedance modulation slots are located in a positive direction of the X-axis, and the other two periodic slots are located in a negative direction of the X-axis and are symmetrically arranged with respect to the Y-axis.
4. A dual-beam frequency-scanning leaky-wave antenna as claimed in claim 2, wherein said impedance-matching slot is located in the first section (24) with a height linearly tapered to 0.1 reference units for 1 reference unit of adjacent bi-periodic sinusoidal impedance-modulating slots; the impedance matching groove is provided with nine linear gradually-changed long grooves in the positive direction of the X axis, and the other nine linear gradually-changed long grooves are in the negative direction of the X axis and are symmetrically arranged with the Y axis.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011228493.6A CN112436268B (en) | 2020-11-06 | 2020-11-06 | Dual-beam frequency scanning leaky-wave antenna |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011228493.6A CN112436268B (en) | 2020-11-06 | 2020-11-06 | Dual-beam frequency scanning leaky-wave antenna |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN112436268A true CN112436268A (en) | 2021-03-02 |
| CN112436268B CN112436268B (en) | 2022-07-29 |
Family
ID=74695531
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202011228493.6A Active CN112436268B (en) | 2020-11-06 | 2020-11-06 | Dual-beam frequency scanning leaky-wave antenna |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN112436268B (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113224541A (en) * | 2021-04-25 | 2021-08-06 | 华东师范大学 | Frequency scanning leaky-wave antenna based on composite left-right-hand metamaterial structure |
| CN113745814A (en) * | 2021-08-26 | 2021-12-03 | 中山大学 | Reconfigurable dual-beam periodic leaky-wave antenna |
| CN113851850A (en) * | 2021-10-28 | 2021-12-28 | 中国舰船研究设计中心 | Zero-crossing scanning leaky-wave antenna |
| CN114725686A (en) * | 2022-05-17 | 2022-07-08 | 安徽大学 | Log-periodic antenna based on half-mode rectangular metal waveguide excitation |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN201732867U (en) * | 2010-07-27 | 2011-02-02 | 东南大学 | Periodic leaky-wave antenna of substrate integrated waveguide (SIW) based on half module |
| US20110248898A1 (en) * | 2010-04-09 | 2011-10-13 | Board Of Trustees Of Michigan State University | Reconfigurable leaky wave antenna |
| CN105006632A (en) * | 2015-07-24 | 2015-10-28 | 哈尔滨工业大学 | Liquid crystal electric control zero crossing scanning leaky-wave antenna based on half-mode pectinate line waveguide |
| CN107425275A (en) * | 2017-07-20 | 2017-12-01 | 东南大学 | A kind of transmission line and leaky-wave antenna multiplexing device and its beam sweeping method |
| CN107425282A (en) * | 2017-07-20 | 2017-12-01 | 东南大学 | It is a kind of to determine frequency beam scanning leaky-wave antenna and its beam sweeping method |
| CN108718001A (en) * | 2018-04-25 | 2018-10-30 | 电子科技大学 | A kind of wave beam based on liquid crystal material is adjustable leaky-wave antenna |
| CN109004341A (en) * | 2018-09-02 | 2018-12-14 | 西南电子技术研究所（中国电子科技集团公司第十研究所） | Substrate integration wave-guide Sine Modulated leaky-wave antenna |
-
2020
- 2020-11-06 CN CN202011228493.6A patent/CN112436268B/en active Active
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20110248898A1 (en) * | 2010-04-09 | 2011-10-13 | Board Of Trustees Of Michigan State University | Reconfigurable leaky wave antenna |
| CN201732867U (en) * | 2010-07-27 | 2011-02-02 | 东南大学 | Periodic leaky-wave antenna of substrate integrated waveguide (SIW) based on half module |
| CN105006632A (en) * | 2015-07-24 | 2015-10-28 | 哈尔滨工业大学 | Liquid crystal electric control zero crossing scanning leaky-wave antenna based on half-mode pectinate line waveguide |
| CN107425275A (en) * | 2017-07-20 | 2017-12-01 | 东南大学 | A kind of transmission line and leaky-wave antenna multiplexing device and its beam sweeping method |
| CN107425282A (en) * | 2017-07-20 | 2017-12-01 | 东南大学 | It is a kind of to determine frequency beam scanning leaky-wave antenna and its beam sweeping method |
| CN108718001A (en) * | 2018-04-25 | 2018-10-30 | 电子科技大学 | A kind of wave beam based on liquid crystal material is adjustable leaky-wave antenna |
| CN109004341A (en) * | 2018-09-02 | 2018-12-14 | 西南电子技术研究所（中国电子科技集团公司第十研究所） | Substrate integration wave-guide Sine Modulated leaky-wave antenna |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN113224541A (en) * | 2021-04-25 | 2021-08-06 | 华东师范大学 | Frequency scanning leaky-wave antenna based on composite left-right-hand metamaterial structure |
| CN113745814A (en) * | 2021-08-26 | 2021-12-03 | 中山大学 | Reconfigurable dual-beam periodic leaky-wave antenna |
| CN113851850A (en) * | 2021-10-28 | 2021-12-28 | 中国舰船研究设计中心 | Zero-crossing scanning leaky-wave antenna |
| CN114725686A (en) * | 2022-05-17 | 2022-07-08 | 安徽大学 | Log-periodic antenna based on half-mode rectangular metal waveguide excitation |
| CN114725686B (en) * | 2022-05-17 | 2024-03-12 | 安徽大学 | Logarithmic periodic antenna based on half-module rectangular metal waveguide excitation |
Also Published As
| Publication number | Publication date |
|---|---|
| CN112436268B (en) | 2022-07-29 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN112436268B (en) | Dual-beam frequency scanning leaky-wave antenna | |
| CN106887716B (en) | A kind of CTS flat plate array antenna | |
| CN109004341B (en) | Substrate integrated waveguide sine modulation leaky-wave antenna | |
| CN208062245U (en) | A kind of automobile collision avoidance radar antenna | |
| CN108598691B (en) | Broadband wide-angle scanning phased-array antenna based on flat-plate long-slot antenna | |
| CN209913026U (en) | High-gain double-frequency circularly polarized antenna based on super surface | |
| CN102800956A (en) | Wideband dual-polarized antenna for integrated balun feed | |
| CN203596414U (en) | Tapered slot antenna and phased array antenna thereof | |
| CN112201933B (en) | Array antenna of compact lightweight multi-scanning system | |
| CN103500883B (en) | Broadband substrate integrated waveguide circularly polarized antenna | |
| CN113206377A (en) | Four-trapped-wave flexible wearable ultra-wideband antenna fed by coplanar waveguide | |
| CN113328242B (en) | High-preparation-property eight-diagram-type element metamaterial cladding microstrip antenna and design method thereof | |
| CN113206392B (en) | Microstrip array antenna with reduced scattering cross section of in-band radar | |
| CN113224541B (en) | Frequency scanning leaky-wave antenna based on composite left-right-hand metamaterial structure | |
| CN113644425A (en) | Wide-bandwidth beam antenna for short-distance vehicle-mounted radar | |
| CN111355027B (en) | Self-decoupling antenna array | |
| CN112164874A (en) | Low RCS broadband printed slot antenna based on digital electromagnetic super surface | |
| CN215266654U (en) | Waveguide antenna unit and waveguide array antenna | |
| CN109904617A (en) | Based on the frequency scanning leaky-wave antenna for loading high guarantor's transmission line that parasitic branch is formed | |
| Liu et al. | A new kind of circularly polarized leaky-wave antenna based on corrugated substrate integrated waveguide | |
| CN212571346U (en) | Patch antenna asymmetrically cut along E-plane | |
| CN114725691A (en) | Dielectric-buried broadband high-power microwave space beam swept reflective array antenna | |
| CN108376841A (en) | Compare broadband dual polarized antenna before and after a kind of height with abutment wall structure | |
| CN113270723A (en) | Metamaterial structure antenna with quasi-rectangular cavity feed | |
| CN113506989A (en) | 5G millimeter wave dielectric resonator antenna and array thereof |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |