CN112130139A - Distributed full-coherent sparse linear array radar system optimization array arrangement method - Google Patents
Distributed full-coherent sparse linear array radar system optimization array arrangement method Download PDFInfo
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Abstract
The invention relates to an optimization array arrangement method for a distributed type fully coherent sparse linear array radar system, and aims to solve the problem that the performance of an antenna directional diagram is deteriorated due to the fact that the existing sparse array arrangement optimization method cannot meet the requirement of distributed type fully coherent sparse array radar array arrangement optimization. The method calculates the maximum array arrangement aperture, the unit radar array element number requirement and the directional diagram optimization angle of the distributed full-coherent sparse linear array radar system on the basis of considering the design and signal processing requirements of the distributed full-coherent radar system; then, carrying out sparse array arrangement optimization aiming at a specific optimization angle domain; and then, screening discrete interference angles aiming at a non-optimized angle area, forming nulls at interference positions by utilizing self-adaptive beam forming to inhibit interference, and finally outputting an optimized array layout directional diagram of the distributed full-coherent sparse linear array radar system.
Description
Technical Field
The invention belongs to the technical field of communication, and further relates to an optimization and arrangement method of a distributed type full-coherent sparse linear array radar system in the technical field of distributed type motion platform radars. The method can be used for the array layout design of the distributed sparse array full-coherent radar system to realize better moving target detection capability.
Background
The full-coherent distributed array radar enables the power gain of a target to be detected to reach the power of 3 times of the number of channels through antenna transmission coherent, and the detection performance of the radar on a moving target with a low signal-to-noise ratio is remarkably improved.
The spacing between unit radars of the distributed full-coherent distributed array radar can reach hundreds of meters (far more than the wavelength), the distributed full-coherent distributed array radar is represented as a sparsely distributed array, and the problems of grating lobes and high side lobes of an antenna emission directional diagram can occur, so that the detection performance of the radar on a moving target is deteriorated. Therefore, there is a need to optimally design sparse array manifold for distributed fully coherent array radar to obtain better transmit pattern. At present, sparse array optimization methods are mainly classified into two types: the first method mainly optimizes the arrangement position of the sparse array, and considers that the full-coherent distributed sparse array radar realizes transmission coherent and limits the array arrangement aperture, so that the method is difficult to obtain the array manifold with better transmission direction diagram performance; the second method combines array position optimization and amplitude phase optimization of array transmission signals to obtain a transmission directional diagram meeting requirements, but this method is not suitable for a full-coherent distributed sparse array radar, because the full-coherent distributed sparse array radar needs to control the phase of the array transmission signals to realize transmission coherence and control the amplitude of the transmission signals to ensure good performance of a radar system, and thus the array position optimization and the amplitude phase optimization of the transmission signals cannot be combined to improve the performance of the directional diagram.
Disclosure of Invention
The technical problem solved by the invention is as follows: the method for optimizing the array layout of the distributed type full-coherent sparse linear array radar system overcomes the defects of the prior art, optimizes the performance of an antenna directional diagram at a local space angle by utilizing the freedom degree of the array position, and simultaneously forms a null at a grating lobe interference position in a non-optimized area by combining airspace self-adaptive beam forming, so that the performance of a receiving and transmitting antenna directional diagram is comprehensively improved, and the problem that the performance of the antenna directional diagram is deteriorated because the existing sparse array layout optimization method cannot meet the requirement of the distributed type full-coherent sparse array radar array layout optimization is solved.
The technical scheme of the invention is as follows: a distributed full-coherent sparse linear array radar system optimization array arrangement method is provided, the distributed full-coherent radar system is a linear array, the array element configuration of each radar unit is the same, the method comprises the following steps:
(1) calculating the maximum array aperture D of the distributed type full-coherent radar system according to the maximum characteristic size of the interested moving targetmax；
(2) Calculating the array element number M of unit radars of the distributed full-coherent radar system under the condition that the unit radars of the distributed full-coherent radar system are uniformly distributed along a straight line according to the integral sidelobe ratio requirement of a directional diagram, thereby obtaining the initial sparse array manifold of the distributed full-coherent radar system;
(3) calculating a space angular domain needing to be optimized by a directional diagram of the distributed type fully coherent radar system according to the initial sparse array manifold of the distributed type fully coherent radar system;
(4) optimizing the distribution position of unit radars in the distributed full-coherent radar system according to the minimum criterion of integral sidelobe ratio in a spatial angular domain to be optimized of a directional diagram of the distributed full-coherent radar system to obtain an optimized sparse array manifold of the distributed full-coherent radar system;
(5) obtaining an optimized transmitting antenna directional diagram of the distributed full-coherent radar system according to the optimized distributed sparse array manifold of the distributed full-coherent radar system;
(6) screening out an angle set of interference of transmitting antenna power in an unoptimized spatial angular domain to a receiving antenna according to the optimized transmitting antenna directional diagram of the distributed full-coherent radar system;
(7) taking the angle set of the interference caused by the transmitting antenna power in the unoptimized space angular domain obtained in the step (6) to the receiving antenna as input, constructing an interference and noise covariance matrix, and calculating a self-adaptive beam forming weight vector of the receiving antenna of the radar system to obtain a self-adaptive beam forming directional diagram of a receiving end of the radar system;
(8) and (4) multiplying the transmitting antenna directional diagram obtained in the step (5) with the corresponding element of the self-adaptive beam forming directional diagram obtained in the step (7) to obtain the optimized array arrangement directional diagram of the distributed full-coherent sparse linear array radar system.
The maximum array-arranging aperture D of the distributed full-coherent radar systemmaxCalculated according to the following formula:
wherein D ismaxDenotes the maximum array aperture, RtRepresents the slant range of the moving target of interest, lambda represents the radar operating wavelength, LtRepresenting the maximum feature size of the moving object of interest.
The array element number M of the unit radar under the condition of uniform distribution is obtained by solving the following equation:
f (theta, M) represents an antenna emission directional diagram when the number of array elements of the unit radar is M under the condition that the unit radars are uniformly distributed, theta represents a space angle, and theta represents0The positive angle corresponding to the first zero point of the antenna emission directional diagram when the array element number of the unit radar is M under the condition of uniform distribution of the unit radar is represented, | | represents the complex modulus operation, and ηIIndicating a pattern integration sidelobe ratio threshold.
The step (3) is realized by the following steps:
(3a) according to the spatial angle theta of the moving object of interesttDividing the interval b with a preset space angle to obtain a discretized space angle thetakThe kth discretized space angle θkComprises the following steps:
θk＝θt+k×b
wherein k represents the space angle ordinal number and the value range is
Represents a round-down operation;
(3b) adopt the bestAn optimization solving method, wherein the optimal discretization space angle is screened out from the discretization space angles to be used as a space boundary angle thetaoptSo that the spatial boundary angle thetaoptThe following conditions are satisfied:
min(θopt-θt)2
wherein, w (θ)k) Representing discrete spatial angles thetakThe optimal beamforming weight vector at which the null is formed, H denotes the conjugate transpose operation, a (θ)k) Representing discrete spatial angles thetakCorresponding space domain steering vector, a (theta)t) Representing the spatial steering vector, η, corresponding to the moving targetJRepresents an interference rejection notch threshold;
(3c) according to the spatial boundary angle thetaoptAngle of space theta with moving object of interesttAnd obtaining a space angular domain theta [ -beta + theta ] of the distributed full-coherent radar directional diagram needing to be optimized by the difference betat,β+θt]。
The discrete spatial angle θkOptimal beamforming weight vector w (θ) of the null formingk) Calculated using the following formula:
w(θk)＝μ(R(θk))-1a(θt)
wherein μ represents a normalization coefficient, ()-1Representing the inverse operation of the matrix sphere, R (θ)k) Representing a spatial angle of thetakInterference-plus-noise covariance matrix of, a (theta)t) Representing the space domain guide vector corresponding to the moving target,
norm () represents a two-extensive operation of a vector. .
Optimizing the unit radar distribution position according to the minimum criterion of the integral sidelobe ratio, and optimizing according to the following formula:
wherein, N represents the number of unit radars, N represents the ordinal number of the unit radars, N has the value range of {1,2, …, N-1}, and dnDenotes the distance of the nth element radar from the reference position, F (theta )t,d1,d2,…,dN) Indicating radar position configuration d for a given unit1,d2,…,dNThe spatial angle of the moving object of interest is thetatCorresponding direction diagram, theta0Indicating radar position configuration d for a given unit1,d2,…,dNThe spatial angle of the moving object of interest is thetatAngle of first zero position of corresponding directional diagram, DmaxDenotes the maximum array aperture, SminRepresenting the minimum spacing between adjacent element radars.
The step (6) is realized by the following steps:
(6.1) according to the preset angle discrete interval, carrying out non-optimization on the spatial angular domain
Discretizing the inner space angle to obtain a set of discretized space angles;
(6.2) screening the set of discretized spatial angles for discretized angles that satisfy the following conditions
Wherein the content of the first and second substances,
represents the optimized sparse array manifold of the distributed full coherent radar system,
representing the optimized antenna emission pattern, ηSRepresents an interference decision threshold;
the number of the discrete angles meeting the conditions is counted as Q, in the Q discrete angles, the discrete angles are arranged from large to small according to the size of the corresponding directional diagram, the smaller value of (MN-1) in the P expression and Q is taken out, and the previous P discrete angles are taken out as an angle set for causing interference to a receiving antenna by the power of the transmitting antenna in an unoptimized space angular domain. The step (7) is realized by the following steps:
(7a) constructing a non-optimal region interference plus noise covariance matrix according to the following formula
Wherein R isJRepresenting the non-optimal region interference plus noise covariance matrix, σJThe power of the interference is represented by,
representing the space domain steering vector, sigma, corresponding to the interference space angle alpha under the optimized distributed sparse array manifoldnRepresenting the noise power, INMA diagonal identity matrix representing NM × 1 dimensions;
(7b) the adaptive beam forming weight vector of the radar receiving antenna is
Wherein, mu1Which represents the normalized coefficient of the coefficient,
representing a target space domain guide vector under the optimized distributed sparse array manifold;
(7c) the self-adaptive beam forming directional diagram of the radar receiving end is as follows:
wherein the content of the first and second substances,
represents the corresponding self-adaptive beam forming directional diagram when the space angle of the radar receiving end is theta,
and representing a corresponding space domain steering vector when the space angle under the optimized distributed sparse array manifold is theta.
Compared with the prior art, the invention has the beneficial effects that:
(1) the invention considers the requirements of the coherent transmitting and receiving signals on the base line, the minimum distance limit of the unit radar, the number requirement of the unit radar array elements and the like, so that the invention can better meet the full coherent processing requirement in engineering practice.
(2) The invention optimizes the directional diagram in the selected area not by optimizing the performance of the full airspace directional diagram, but by concentrating the degree of freedom of sparse array arrangement, the performance of the directional diagram in the area can be obviously improved, and a better integral side lobe ratio can be obtained.
(3) Aiming at a non-optimized area, the invention utilizes the processing freedom degree of the receiving end to adaptively form the null trap suppression high side lobe and grating lobe interference, so that the invention fully utilizes the array distribution freedom degree and the processing freedom degree of the system receiving end to improve the performance of a transmitting-receiving directional diagram under the condition of ensuring the requirement of a full coherent working system, and can obtain a better moving target detection result.
Drawings
Fig. 1 is a flow of a full-coherent sparse distributed array optimization arraying method for joint adaptive beamforming according to an embodiment of the present invention.
FIG. 2 is an un-optimized transmission pattern according to an embodiment of the present invention;
FIG. 3 is a diagram of an emission pattern using the optimized design method according to an embodiment of the present invention;
FIG. 4 is a receiver diagram of adaptive null beamforming in accordance with an embodiment of the present invention;
fig. 5 is a diagram of a transmitting-receiving two-way antenna pattern designed by the present invention according to an embodiment of the present invention.
Detailed Description
The invention is further illustrated by the following examples.
The use scene of the invention is as follows: the distributed full-coherent radar array distribution method can be applied to a distributed radar sparse array full-coherent radar array distribution method to achieve better moving target detection capability, the distributed full-coherent radar is a linear array, and the array elements of each radar unit are configured identically. The method optimizes the performance of an antenna directional pattern of a local space angle by utilizing the freedom degree of an array position, and simultaneously forms a null at a grating lobe interference position in a non-optimized area by combining the self-adaptive beam forming of a space domain, so that the performance of a receiving and transmitting antenna directional pattern is comprehensively improved, and the problem that the performance of the antenna directional pattern is deteriorated because the existing sparse array deployment optimization method cannot meet the deployment optimization requirement of a distributed full-coherent sparse array radar is solved, and the method is specifically realized by the following steps:
(1) calculating the maximum array aperture D of the distributed type full-coherent radar system according to the maximum characteristic size of the interested moving targetmax；
Maximum array-laying aperture D of distributed full-coherent radar systemmaxCalculated according to the following formula:
wherein D ismaxDenotes the maximum array aperture, RtRepresents the slant range of the moving target of interest, lambda represents the radar operating wavelength, LtRepresenting the maximum characteristic dimension of the moving object of interest, e.g. when the moving object is an airplane, the maximum characteristic dimension is taken as the length of the airplane
(2) Calculating the array element number M of unit radars of the distributed full-coherent radar system under the condition that the unit radars of the distributed full-coherent radar system are uniformly distributed along a straight line according to the integral sidelobe ratio requirement of a directional diagram, thereby obtaining the initial sparse array manifold of the distributed full-coherent radar system;
the array element number M of the unit radar under the condition of uniform distribution is obtained by solving the following equation:
f (theta, M) represents an antenna emission directional diagram when the number of array elements of the unit radar is M under the condition that the unit radars are uniformly distributed, theta represents a space angle, and theta represents0The positive angle corresponding to the first zero point of the antenna emission directional diagram when the array element number of the unit radar is M under the condition of uniform distribution of the unit radar is represented, | | represents the complex modulus operation, and ηIRepresents the pattern integral sidelobe ratio threshold, namely: and the maximum value threshold of the side lobe ratio meeting the requirement of the directional diagram integral side lobe ratio is met.
(3) Calculating a space angular domain needing to be optimized by a directional diagram of the distributed type fully coherent radar system according to the initial sparse array manifold of the distributed type fully coherent radar system;
the concrete implementation is as follows:
(3a) according to the spatial angle theta of the moving object of interesttDividing the interval b with a preset space angle to obtain a discretized space angle thetakThe kth discretized space angle θkComprises the following steps:
θk＝θt+k×b
wherein k represents the space angle ordinal number and the value range is
Represents a round-down operation;
(3b) screening out the optimal discretization space angle from the discretization space angles by adopting an optimization solving method as a space boundary angle thetaoptSo that the spatial boundary angle thetaoptThe following conditions are satisfied:
min(θopt-θt)2
wherein, w (θ)k) Representing discrete spatial angles thetakThe optimal beamforming weight vector at which the null is formed,Hdenotes a conjugate transpose operation, a (θ)k) Representing discrete spatial angles thetakCorresponding space domain steering vector, a (theta)t) Representing the spatial steering vector, η, corresponding to the moving targetJRepresenting the interference rejection notch threshold.
Discrete spatial angle thetakOptimal beamforming weight vector w (θ) of the null formingk) Calculated using the following formula:
w(θk)＝μ(R(θk))-1a(θt)
wherein μ represents a normalization coefficient, ()-1Representing the inverse operation of the matrix sphere, R (θ)k) Representing a spatial angle of thetakInterference-plus-noise covariance matrix of, a (theta)t) Representing the space domain guide vector corresponding to the moving target,
norm () represents a two-extensive operation of a vector. .
(3c) According to the spatial boundary angle thetaoptAngle of space theta with moving object of interesttAnd obtaining a space angular domain theta [ -beta + theta ] of the distributed full-coherent radar directional diagram needing to be optimized by the difference betat,β+θt]。
(4) Optimizing the distribution position of unit radars in the distributed full-coherent radar according to the minimum criterion of integral sidelobe ratio in a spatial angular domain to be optimized of a directional diagram of the distributed full-coherent radar system to obtain an optimized sparse array manifold of the distributed full-coherent radar system;
optimizing the unit radar distribution position according to the minimum criterion of the integral sidelobe ratio, and optimizing according to the following formula:
wherein, N represents the number of unit radars, N represents the ordinal number of the unit radars, N has the value range of {1,2, …, N-1}, and dnDenotes the distance of the nth element radar from the reference position, F (theta )t,d1,d2,…,dN) Indicating radar position configuration d for a given unit1,d2,…,dNThe spatial angle of the moving object of interest is thetatCorresponding direction diagram, theta0Indicating radar position configuration d for a given unit1,d2,…,dNThe spatial angle of the moving object of interest is thetatAngle of first zero position of corresponding directional diagram, DmaxDenotes the maximum array aperture, SminRepresenting the minimum spacing between adjacent element radars.
(5) Obtaining an optimized transmitting antenna directional diagram of the distributed full-coherent radar system according to the optimized distributed sparse array manifold of the distributed full-coherent radar system
(6) Screening out an angle set of interference of transmitting antenna power in an unoptimized spatial angular domain to a receiving antenna according to the optimized transmitting antenna directional diagram of the distributed full-coherent radar system; the concrete implementation is as follows:
(6.1) according to the preset angle discrete interval, carrying out non-optimization on the spatial angular domain
Discretizing the inner space angle to obtain a set of discretized space angles;
(6.2) screening the set of discretized spatial angles for discretized angles that satisfy the following conditions
Wherein the content of the first and second substances,
represents the optimized sparse array manifold of the distributed full coherent radar system,
representing the optimized antenna emission pattern, ηSRepresents an interference decision threshold;
the number of the discrete angles meeting the conditions is counted as Q, in the Q discrete angles, the discrete angles are arranged from large to small according to the size of the corresponding directional diagram, the smaller value of (MN-1) in the P expression and Q is taken out, and the previous P discrete angles are taken out as an angle set for causing interference to a receiving antenna by the power of the transmitting antenna in an unoptimized space angular domain.
(7) Taking the angle set of the interference caused by the transmitting antenna power in the unoptimized space angular domain obtained in the step (6) to the receiving antenna as input, constructing an interference and noise covariance matrix, and calculating a self-adaptive beam forming weight vector of the receiving antenna of the radar system to obtain a self-adaptive beam forming directional diagram of a receiving end of the radar system;
(7a) according to the discrete interference angle set, constructing a non-optimal region interference and noise covariance matrix according to the following formula
Wherein R isJRepresenting the non-optimal region interference plus noise covariance matrix, σJThe power of the interference is represented by,
representing the space domain steering vector, sigma, corresponding to the interference space angle alpha under the optimized distributed sparse array manifoldnRepresenting the noise power, INMRepresents a diagonal identity matrix of NM × 1 dimension.
(7b) The radar receiving end adaptive beam forming weight vector is
Wherein, mu1Which represents the normalized coefficient of the coefficient,
and representing the target space domain guide vector under the optimized distributed sparse array manifold.
(7c) The adaptive beam forming directional diagram at the receiving end of the radar system is
Wherein the content of the first and second substances,
represents the corresponding self-adaptive beam forming directional diagram when the space angle at the receiving end of the radar system is theta,
and representing a corresponding space domain steering vector when the space angle under the optimized distributed sparse array manifold is theta.
(8) And (4) multiplying the transmitting antenna directional diagram obtained in the step (5) with the corresponding element of the self-adaptive beam forming directional diagram obtained in the step (7) to obtain the optimized array arrangement directional diagram of the distributed full-coherent sparse linear array radar system.
The optimization array arrangement method of the distributed type holohedral sparse linear array radar system provided by the invention optimizes the performance of an antenna directional diagram of a local space angle by utilizing the freedom degree of an array position, and simultaneously forms a null at a grating lobe interference position of a non-optimized area by combining with the self-adaptive wave beam of an airspace, so as to solve the problem that the performance of the antenna directional diagram is deteriorated because the prior sparse array arrangement optimization method can not meet the optimization requirement of the distributed type holohedral sparse array radar,
the effect of the present invention is further explained by simulation experiments as follows:
the simulation parameters are set as follows: in order to verify the effectiveness of the algorithm, the working wavelength of the radar in simulation is 0.15 m, the number of unit radars is 4, the interested moving target is a cruise ship, the length of the ship is 200 m, the azimuth angle is 0 degrees, the observation distance is 2000 kilometers, and the maximum array aperture is 1500 m calculated according to the step 1. The integral sidelobe ratio threshold of the directional diagram is-9 dB, the number of array elements of the unit radar obtained through calculation according to the step 2 is 400, the interference suppression notch threshold is-20 dB, the optimized angular domain theta of the directional diagram obtained through calculation according to the step 3 is [ -5 degrees, 5 degrees ], the interference judgment threshold is-40 dB, and the interference-to-noise power ratio is 50 dB.
Fig. 2 is a transmission pattern of an unoptimized design (regular 4-unit radar uniform arrangement (200 array elements/unit)). Fig. 3 is a transmission pattern using the optimized design method of the present invention. Fig. 4 is a reception pattern of adaptive null beamforming. Fig. 5 is a diagram of a transmit-receive dual-pass antenna pattern designed using the present invention.
And (4) simulation conclusion: simulation results show that after the optimization arrangement is carried out by adopting the optimization design method provided by the invention, the transmitting antenna directional diagram, the receiving directional diagram and the receiving and transmitting double-pass antenna directional diagram have better performance, the design requirements are met, and the effectiveness of the algorithm is verified by the simulation results.
Although the present invention has been described with reference to the preferred embodiments, it is not intended to limit the present invention, and those skilled in the art can make variations and modifications of the present invention without departing from the spirit and scope of the present invention by using the methods and technical contents disclosed above.
Claims (8)
1. A distributed full-coherent sparse linear array radar system optimization array arrangement method is characterized by comprising the following steps of:
(1) calculating the maximum array aperture D of the distributed type full-coherent radar system according to the maximum characteristic size of the interested moving targetmax；
(2) Calculating the array element number M of unit radars of the distributed full-coherent radar system under the condition that the unit radars of the distributed full-coherent radar system are uniformly distributed along a straight line according to the integral sidelobe ratio requirement of a directional diagram, thereby obtaining the initial sparse array manifold of the distributed full-coherent radar system;
(3) calculating a space angular domain needing to be optimized by a directional diagram of the distributed type fully coherent radar system according to the initial sparse array manifold of the distributed type fully coherent radar system;
(4) optimizing the distribution position of unit radars in the distributed full-coherent radar system according to the minimum criterion of integral sidelobe ratio in a spatial angular domain to be optimized of a directional diagram of the distributed full-coherent radar system to obtain a sparse array manifold after the distributed full-coherent radar is optimized;
(5) obtaining an optimized transmitting antenna directional diagram of the distributed full-coherent radar system according to the optimized distributed sparse array manifold of the distributed full-coherent radar system;
(6) screening out an angle set of interference of transmitting antenna power in an unoptimized spatial angular domain to a receiving antenna according to the optimized transmitting antenna directional diagram of the distributed full-coherent radar system;
(7) taking the angle set of the interference caused by the transmitting antenna power in the unoptimized space angular domain obtained in the step (6) to the receiving antenna as input, constructing an interference and noise covariance matrix, and calculating a self-adaptive beam forming weight vector of the receiving antenna of the radar system to obtain a self-adaptive beam forming directional diagram of a receiving end of the radar system;
(8) and (4) multiplying the transmitting antenna directional diagram obtained in the step (5) with the corresponding element of the self-adaptive beam forming directional diagram obtained in the step (7) to obtain the optimized array arrangement directional diagram of the distributed full-coherent sparse linear array radar system.
2. The optimized arraying method for the distributed full-coherent sparse linear array radar system according to claim 1, wherein the maximum arraying aperture D of the distributed full-coherent radar systemmaxCalculated according to the following formula:
wherein D ismaxDenotes the maximum array aperture, RtRepresents the slant range of the moving target of interest, lambda represents the radar operating wavelength, LtRepresenting the maximum feature size of the moving object of interest.
3. The optimized array arrangement method of the distributed full-coherent sparse linear array radar system as claimed in claim 1, wherein the number M of array elements of the unit radar under the condition of uniform distribution is obtained by solving the following equation:
f (theta, M) represents an antenna emission directional diagram when the number of array elements of the unit radar is M under the condition that the unit radars are uniformly distributed, theta represents a space angle, and theta represents0The positive angle corresponding to the first zero point of the antenna emission directional diagram when the array element number of the unit radar is M under the condition of uniform distribution of the unit radar is represented, | | represents the complex modulus operation, and ηIIndicating a pattern integration sidelobe ratio threshold.
4. The optimized arraying method for the distributed full-coherent sparse linear array radar system according to claim 1, wherein the step (3) is implemented by:
(3a) according to the spatial angle theta of the moving object of interesttDividing the interval b with a preset space angle to obtain a discretized space angle thetakThe kth discretized space angle θkComprises the following steps:
θk＝θt+k×b
wherein k represents the space angle ordinal number and the value range is
Represents a round-down operation;
(3b) screening out the optimal discretization space angle from the discretization space angles by adopting an optimization solving method as a space boundary angle thetaoptSo that the spatial boundary angle thetaoptThe following conditions are satisfied:
min(θopt-θt)2
wherein, w (θ)k) Representing discrete spatial angles thetakThe optimal beamforming weight vector at which the null is formed, H denotes the conjugate transpose operation, a (θ)k) Representing discrete spatial angles thetakCorresponding space domain steering vector, a (theta)t) Representing the spatial steering vector, η, corresponding to the moving targetJRepresents an interference rejection notch threshold;
(3c) according to the spatial boundary angle thetaoptAngle of space theta with moving object of interesttAnd obtaining a space angular domain needing to be optimized for a directional diagram of the distributed full-coherent radar system by the difference beta, wherein theta is [ -beta + thetat,β+θt]。
5. The optimized arraying method for the distributed full-coherent sparse linear array radar system according to claim 4, wherein the discrete spatial angle θ iskOptimal beamforming weight vector w (θ) of the null formingk) Calculated using the following formula:
w(θk)＝μ(R(θk))-1a(θt)
wherein μ represents a normalization coefficient, ()-1Representing the inverse operation of the matrix sphere, R (θ)k) Representing a spatial angle of thetakInterference-plus-noise covariance matrix of, a (theta)t) Representing the space domain guide vector corresponding to the moving target,
norm () represents a two-extensive operation of a vector. .
6. The distributed full-coherent sparse linear array radar system optimizing arraying method according to claim 1, wherein unit radar distribution positions are optimized according to an integration sidelobe ratio minimum criterion and optimized according to the following formula:
wherein, N represents the number of unit radars, N represents the ordinal number of the unit radars, N has the value range of {1,2, …, N-1}, and dnDenotes the distance of the nth element radar from the reference position, F (theta )t,d1,d2,…,dN) Indicating radar position configuration d for a given unit1,d2,…,dNThe spatial angle of the moving object of interest is thetatCorresponding direction diagram, theta0Indicating radar position configuration d for a given unit1,d2,…,dNThe spatial angle of the moving object of interest is thetatAngle of first zero position of corresponding directional diagram, DmaxDenotes the maximum array aperture, SminRepresenting the minimum spacing between adjacent element radars.
7. The optimized arraying method for the distributed full-coherent sparse linear array radar system according to claim 1, wherein the step (6) is implemented by:
(6.1) according to the preset angle discrete interval, carrying out non-optimization on the spatial angular domain
Discretizing the inner space angle to obtain a discretized space angleA set of (a);
(6.2) screening the set of discretized spatial angles for discretized angles that satisfy the following conditions
Wherein the content of the first and second substances,
represents the optimized sparse array manifold of the distributed full coherent radar system,
representing the optimized antenna emission pattern, ηSRepresents an interference decision threshold;
the number of the discrete angles meeting the conditions is counted as Q, in the Q discrete angles, the discrete angles are arranged from large to small according to the size of the corresponding directional diagram, the smaller value of (MN-1) in the P expression and Q is taken out, and the previous P discrete angles are taken out as an angle set for causing interference to a receiving antenna by the power of the transmitting antenna in an unoptimized space angular domain.
8. The optimized arraying method for the distributed full-coherent sparse linear array radar system according to claim 1, wherein the optimized arraying method is characterized in that
(7a) Constructing a non-optimal region interference plus noise covariance matrix according to the following formula
Wherein R isJRepresenting the non-optimal region interference plus noise covariance matrix, σJThe power of the interference is represented by,
representing the space domain steering vector, sigma, corresponding to the interference space angle alpha under the optimized distributed sparse array manifoldnRepresenting the noise power, INMA diagonal identity matrix representing NM × 1 dimensions;
(7b) the adaptive beam forming weight vector of the radar receiving antenna is
Wherein, mu1Which represents the normalized coefficient of the coefficient,
representing a target space domain guide vector under the optimized distributed sparse array manifold;
(7c) the self-adaptive beam forming directional diagram of the radar receiving end is as follows:
wherein the content of the first and second substances,
represents the corresponding self-adaptive beam forming directional diagram when the space angle of the radar receiving end is theta,
and representing a corresponding space domain steering vector when the space angle under the optimized distributed sparse array manifold is theta.
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