CN111934576A - Auxiliary resonance converter pole inverter with phase-correlated magnetizing current symmetric reset - Google Patents
Auxiliary resonance converter pole inverter with phase-correlated magnetizing current symmetric reset Download PDFInfo
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- CN111934576A CN111934576A CN202010301490.4A CN202010301490A CN111934576A CN 111934576 A CN111934576 A CN 111934576A CN 202010301490 A CN202010301490 A CN 202010301490A CN 111934576 A CN111934576 A CN 111934576A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses an auxiliary resonance converter pole inverter with symmetrically reset phase-correlated magnetizing current, the circuit of the invention keeps the prior art by utilizing a phase correlation method, realizes the advantage of zero-voltage switching-on of a main switch tube, reduces the switching loss of a main switch, and in addition, an auxiliary switch in an auxiliary loop also realizes the zero-voltage switching-on through energy storage in an excitation inductor and has a voltage withstanding value far smaller than that of the main switch; the magnetizing current reset is reliably realized in each switching period, and the volume of the transformer is effectively reduced; the secondary winding of the transformer is coupled to solve the problem of an auxiliary converter diode DN1And DN2The problem of overpressure.
Description
Technical Field
The invention relates to the technical field of power electronic conversion, in particular to an auxiliary resonance converter pole inverter with symmetrically reset phase-correlated magnetizing current.
Background
Voltage Source Inverter (VSI), which is essentially a synchronous rectification buck-boost converter formed by a fully-controlled switching half-bridge, is widely used in various power class applications, such as: motor drives, active power filters, Uninterruptible Power Supplies (UPS), photovoltaic power systems, fuel cell power systems, distributed power grids, and the like. The research core is to improve the efficiency and the power density.
Under hard switching conditions, power density is typically increased by reducing the size and weight of passive components (e.g., filter inductors and capacitors) by increasing the switching frequency, but increasing the switching frequency results in increased switching losses and high frequency electromagnetic interference (EMI), which in turn reduces the efficiency of the inverter. In VSI, the circuit is an inverter half-bridge and an inductor connected to the midpoint of the half-bridge; during hard switching, after the freewheeling mode, the energy Qrr, Qoss stored in the antiparallel diode and the output capacitor at the switching-on instant of the switching-on switching tube to be switched on is released into the channel of the switching tube, so that peak current, switching-on loss and high-frequency electromagnetic interference (EMI) are generated. One way to overcome the above problems (switching losses and EMI) is to advance the switching device technology and another is to soft switch topology technology.
Wide bandgap semiconductors such as SiC and GaN have faster turn-on and turn-off times, lower turn-off losses and lower parasitic capacitance than conventional Si power semiconductors; but faster switching times result in greater high frequency electromagnetic interference (EMI). In addition, SiC has the problems of harsh grid opening and closing conditions, high cost and the like.
Soft switching topologies can reduce switching losses and EMI at high switching frequencies. Soft switching topologies are methods to reduce switching losses by adding auxiliary circuits to decouple the transition edges of the current and voltage of the switching tubes. Among many soft switching inverter topologies, the auxiliary resonant very soft switching inverter is generally accepted because the voltage and current stresses of the switching tubes in the main circuit are not additionally increased, and the auxiliary circuit only works when the switching tubes are commutated without affecting the normal operation of the main circuit.
In the prior art, see the article "An Improved Zero-Voltage Switching Inverter Using Two Coupled Magnetics in One resistor pol" published in the 25 th volume of 2010 of IEEE Transactions on Power Electronics journal, the double-Coupled inductor (ZVT-2CI) circuit can realize Zero-Voltage Switching of a main switch and Zero-current Switching of An auxiliary switch and solve the problem that An excitation current cannot be reset. The converter diode has no clamping measure, and after the resonant current is reduced to 0, the two ends of the converter diode can bear direct-current bus voltage which is about 2 times of the voltage, and potential oscillation of the undamped end of the diode can be caused; in the prior art, the New polarity of the line phase soft switching using a dual magnetizing circuit of IEEE 201315 th European Conference on Power Electronics and Applications (EPE) can realize that the main switch zero voltage is switched on and the auxiliary switch zero current switch resets the magnetizing current by disconnecting the free flow path of the exciting current. But the diodes connected in series on the high current loop will add extra losses. In the two methods, one coupling inductor can only realize zero voltage switching-on of one main switching tube, so that two coupling inductors are required to be used in one auxiliary circuit, and the size, the cost and the leakage inductance loss of the transformer are increased.
Disclosure of Invention
In order to solve the defects of the prior art, the auxiliary resonance converter pole inverter with the phase-associated magnetizing current symmetrically reset is provided, and zero voltage switching-on of a main switch and an auxiliary switch is realized; the efficiency and the power density are effectively improved, and the cost and the EMI are reduced.
The invention provides an auxiliary resonant inverter pole inverter with symmetrically reset phase-correlated magnetizing current, which comprises a first main switch tube (S1), a second main switch tube (S2), a first converter diode (Dc1), a second converter diode (Dc2), a first freewheeling diode (Dx1), a second freewheeling diode (Dx2), a direct current power supply (VDC), an auxiliary power supply (VAUX) Load (Load), a first voltage-dividing capacitor (Cd1), a second voltage-dividing capacitor (Cd2), a resonant inductor (Lr1), an auxiliary converter transformer primary winding (T1), an auxiliary converter transformer secondary side first winding (T2), a first auxiliary switch tube (Sa1), a second auxiliary switch tube (Sa2), a third auxiliary switch tube (Sa3), a fourth auxiliary switch tube (Sa 9638), a second auxiliary switch tube (Sa2), a third auxiliary switch tube (Sa3), a fourth auxiliary switch tube (Sa4), a leading-AC Lead inductor (LmLead) and a magnetic field inductor (Sa-LmLg), the source electrode of the first main switching tube (S1) and the drain electrode of the second main switching tube (S2) are connected to a point O, and the two switching tubes form a main switching bridge arm; the drain electrode of the first main switching tube (S1), the cathode of the first commutation diode (Dc1) and the cathode of the second freewheeling diode (Dx2) are connected with the anode of a direct-current power supply (VDC); the negative pole of the direct current power supply (VDC), the source electrode of the second main switch tube (S2), the positive pole of the second commutation diode (Dc2) and the first follow currentThe anode of the pole tube (Dx1) is connected; one end of a Load (Load) is connected with a point O of the middle point of the bridge arm of the main switch, and the other end of the Load (Load) is connected with the middle points of a first voltage-dividing capacitor (Cd1) and a second voltage-dividing capacitor (Cd 2); one end of a resonant inductor (Lr1) is connected with the point O of the midpoint of the main switch bridge arm, and the other end of the resonant inductor is connected with the synonym end of the auxiliary side first winding (T2) of the auxiliary converter transformer; the dotted terminal of the auxiliary side first winding (T2) of the auxiliary converter transformer is connected with the anode of the first converter diode (Dc1) and the cathode of the first freewheeling diode (Dx 1); one end of the resonant inductor (Lr2) is connected with the point O of the midpoint of the main switch bridge arm, and the other end of the resonant inductor is connected with the synonym end of the secondary side second winding (T3) of the auxiliary converter transformer; the dotted terminal of the secondary side second winding (T3) of the auxiliary converter transformer is connected with the cathode of the second converter diode (Dc2) and the anode of the second freewheeling diode (Dx 2); the source electrode of the first auxiliary switching tube (Sa1) and the drain electrode of the second auxiliary switching tube (Sa2) are connected to a point Q, and the two switching tubes form a leading bridge arm (AC-Lang) of the commutation auxiliary circuit; the source electrode of the third auxiliary switching tube (Sa3) and the drain electrode of the fourth auxiliary switching tube (Sa4) are connected to the R point, and the two switching tubes form a hysteresis bridge arm (AC-Lead) of the commutation auxiliary circuit; the drain electrode of the first auxiliary switch tube (Sa1) and the drain electrode of the third auxiliary switch tube (Sa3) are connected with the positive electrode of the auxiliary power supply (VAUX), the negative electrode of the auxiliary power supply (VAUX) is connected with the source electrode of the second auxiliary switch tube (Sa2), and the source electrode of the fourth auxiliary switch tube (Sa 4); the dotted end of the primary winding (T1) of the auxiliary converter transformer is connected with the midpoint Q point of the leading auxiliary switch bridge arm, and the unlike end is connected with the midpoint R point of the lagging auxiliary switch bridge arm; the exciting inductance Lm is connected in parallel with two ends of a primary winding (T1) of the auxiliary converter transformer; the number of turns of a first winding (T2) and a second winding (T3) on the secondary side of the auxiliary converter transformer is the same, the number of turns of a primary winding (T1) of the auxiliary converter transformer and the turn ratio of T2 (or T3) are 1/n, and the first freewheeling diode (D)x1) And a second freewheeling diode (D)x2) Is applied to the first commutation diode (D)c1) And a second commutation diode (D)c2) Providing follow current paths for reverse current in reverse recovery process, wherein the follow current paths are respectively T2->Lr1->S2->DX1->T2And T3->DX2->S1->Lr2->T3。
As a further improvement of the above scheme, when the load current is positive, the operation mode and the switching time interval are as follows:
the circuit is in a steady state, S2、Sa1、Sa3In the on state, S1、Sa2、Sa4In an off state; current conversion diode DN1、DN2Freewheel diode Dx1、Dx2A voltage stabilizing diode Dz1、Dz2And the anti-parallel diode of the switching tube is in a turn-off state;
t0at time, turn off Sa3;
Sa3Delay DP1 after turn-off, turn on Sa4;
Sa4Delay DP2 after switching on, turn off S2;
S2Delay DP3 after shutdown, turn off Sa1;
Sa1Delay DP4 after turn-off, turn on Sa2;
Sa2Delay DP5 after conduction, turn on S1;
S1Delay after conduction TonTurn off S1;
S1Delay DP6 after turn-off, turn on S2;
At t0Time of day, Sa3Delay after shutdown TSW/2, turn off Sa4;
Sa4Delay DP7 after turn-off, turn on Sa3;
Sa3Delay DP8 after switching on, turn off Sa2;
Off Sa2Delay DP9, turn on Sa1;
The working mode and the switching time interval when the load current is negative are:
the circuit is in a steady state, S1、Sa1、Sa3In the on state, S2、Sa2、Sa4In an off state; current conversion diode DN1、DN2Freewheel diode Dx1、Dx2A voltage stabilizing diode Dz1、Dz2And the anti-parallel diode of the switching tube is in a turn-off state;
t0at time, turn off Sa3;
Sa3The delay DN1 after the shutdown is reached,conducting Sa4;
Sa4DN2 is delayed after conduction and S is turned off1;
S1Delay DP3 after shutdown, turn off Sa1;
Sa1Delay DP4 after turn-off, turn on Sa2;
Sa2Delay DP5 after conduction, turn on S2;
S2Delay after conduction TonTurn off S2;
S2Delay DP6 after turn-off, turn on S1;
At t0Time of day, Sa3Delay after shutdown TSW/2, turn off Sa4;
Sa4DN7 is delayed after the switch-off, and S is conducteda3;
Sa3DN8 is delayed after conduction and S is turned offa2;
Turning off Sa2, delaying DN9, and turning on Sa 1;
wherein the following parameters are input quantities: vDCIs a dc bus voltage; vAUXIs the auxiliary supply voltage; t is1A_minThe shortest ZVS on-time for Sa 4; t is3BShortest on time of S1 (S2); i isrThe part of the commutation current peak value exceeding the load current; cm_ossIs a main switch tube S1-S2Parallel absorption capacitance: cm_oss=C1=C2;Ca_ossFor auxiliary switching of the tube Sa1-Sa4Parallel absorption capacitor Ca_oss=Ca1=Ca2=Ca3=Ca4(ii) a The following parameters can be expressed in terms of input quantity constraints; vA'UXIs the secondary side voltage of the transformer; l isrIs a commutation inductance; l ismIs an excitation inductor;the exciting current value before the current conversion of the auxiliary switch is in positive correlation with the load current value in each switching period;
wherein T is13_minTo ignore the current change before charging the commutation current, iLoadT obtained by adding 01-t3The time interval of (c); t is1A_minWhen the load current is 0, Sa4ZVS on time T1AThe value of (c).
As a further improvement of the above scheme, the specific description of each mode and the calculation process of the interval time when the output current is positive are as follows:
mode 1 (t)<t0): the circuit is in a steady state, S2In a conducting state; load current ILoadBy S2Afterflow; sa1、Sa3Conducting, exciting current iLmBy Sa1、Sa3Free flow of value of
Mode 2 (t)0-t1):t0At time, turn off Sa3(ii) a Commutation inductor LrThrough a transformer and an excitation inductor LmAfter being connected in parallel with an auxiliary capacitor Ca3、Ca4Resonance occurs, the potential of the point R drops, and an equivalent circuit diagram is shown in FIG. 6; current converting inductive currentIncrease from zero; excitation currentChanging to the positive direction;
exciting the inductive current according to the relation between the instantaneous value of the inductive current and the integral of the terminal voltage and the initial value of the currentAnd the current of the current converter
Wherein ω isaFor resonant angular frequency:
at t1Time of day, Sa3Voltage resonance at both ends to VAUXThe time according to the present resonance mode is:
mode 3 (t)1-t2):t1At that time, the potential at the point R is reduced to 0, Da4Natural conduction, Sa4Reaching ZVS commutation conditions, fig. 7 is an equivalent circuit diagram of this mode; the voltage at two ends of the exciting inductor is opposite to the current direction, and the magnitude of the exciting current is linearly reduced; the current of the commutation inductor is linearly increased; t is tAAt that moment, the primary winding current is reduced to zero, Sa4May be in the time period t1-tAThe ZVS conduction is controlled between the two switches;
the primary winding current in the mode is as follows:
auxiliary pipe Sa4The soft on-time of (d) is:
Sa3turn off to Sa4The on-time interval DP1 is:
charging mode (t)1-t2) The current conversion inductance current is:
wherein: v'AUXIs the secondary side voltage of the transformer;
iLr(t2)=Ir+iLoad\ formula (33)
Simultaneous, charging mode (T)1-2) The duration of (c) is:
Sa4is conducted to S2The off-time interval DP2 is:
mode 4 (t)2-t3):t2At the moment, the main switch S2Off, fig. 8 is an equivalent circuit diagram of this mode; current-converting inductive current iLrPart I of the medium excess load currentrTo the capacitor C1Discharge C2Charging, and enabling the potential of the point O to start resonant rising;
potential v at point OOAnd a current of commutation iLrThe expression is as follows:
wherein:
t3at that time, the potential at the point O rises to VDC-VA'UX(ii) a The mode duration is:
wherein:
S1is conducted to Sa1The off-time interval DP3 is:
DP3=T2-3formula (46)
Mode 5 (t)3-t5):t3At that time, the potential at the point O rises to VDC-VA'UXTurn off Sa1Excitation current iLmIs increased toExcitation currentTo Ca1Charging Ca2Discharging, and enabling the potential of the point Q to start to approximately linearly decrease; t is t4At that time, the potential at the point Q is lowered to 0, Da2Conducting naturally;
t3-t4the duration is:
Sa1turn off to Sa2The on-time interval DP4 is:
DP4=T3-4formula (42)
Mode 6 (t)5-t6) At t5Time of day, D1Natural conduction, S1The ZVS commutation condition is met; current-converting inductive current iLrLinear decrease, tBAt the moment, the current changes the inductive current iLrDown to the load current iLoad(ii) a Main switch tube S1May be in the time period t5-tBThe ZVS conduction is realized by controlling the conduction;
t5at that time, the potential at the point O rises to VDC;S1The commutation time is as follows:
thus, obtaining: s1ZVS on mode duration is:
Sa2is conducted to S1The on-time interval DP5 is:
mode 7 (t)6-t8):tB-t6Determined by PWM control requirement, t6At time, turn off S1Load current iLoadTo C1Charging, C2Discharging, and linearly reducing the potential of the O point; t is t7At that time, the potential at the point O is reduced to 0, and the diode D2Conducting naturally; s2Can be at t7Then controlling the conduction;
t6-t7the duration is:
S1turn off to S2The on-time interval DP6 is:
DP6=T6-7\ formula (48)
Mode 8 (t)8-t9):t8At time, turn off Sa4FIG. 9 shows an equivalent circuit diagram of this mode, in which an excitation current is appliedTo Ca4Charging Ca3Discharging, and the potential of the R point begins to rise;
wherein:
at t9At the moment, the potential at the point R resonates to VAUXThe pattern duration is:
mode 9 (t)9-t10):t9At that time, the potential at the point R rises to VAUX,Da3Natural conduction, Sa3Reach ZVS commutation condition, tCAt the moment, the excitation current is reduced to zero; sa3May be in the time period T9CControl conduction between the two;
the excitation current in the mode is as follows:
Sa3the soft on-time of (d) is:
Sa4turn off to Sa3The on-time interval DP7 is:
Sa3is conducted to Sa2The off-time interval DP8 is:
mode 10 (t)10-t11):t10At time, turn off Sa2(ii) a Auxiliary converter transformer excitation currentTo Ca2Charging Ca1Discharging, and enabling the potential of the point Q to rise approximately linearly; t is t11At that time, the potential at the point P rises to VAUX,Da1Conducting naturally; controlling conduction S before the next switching cyclea1;
The mode duration is:
Sa2turn off to Sa1The on-time interval DP9 is:
DP9=T10-11formula (59)
The specific description of each mode and the calculation process of the interval time when the output current is negative are as follows:
mode 1 (t)<t0): the circuit is in a steady state, S1In a conducting state; load current ILoadBy S1Follow current, Sa1、Sa3Conducting, exciting current iLmBy Sa1、Sa3Free flow of value of
Mode 2 (t)0-t1):t0At time, turn off Sa3(ii) a Commutation inductor LrThrough a transformer and an excitation inductor LmAfter being connected in parallel with an auxiliary capacitor Ca3、Ca4Resonance occurs, the potential of the point R drops, and an equivalent circuit diagram is shown in FIG. 6; current converting inductive currentIncrease from zero; excitation currentChanging to the positive direction;
exciting the inductive current according to the relation between the instantaneous value of the inductive current and the integral of the terminal voltage and the initial value of the currentAnd the current of the current converter
Wherein ω isaFor resonant angular frequency:
at t1Time of day, Sa3Voltage resonance at both ends to VAUXThe time according to the present resonance mode is:
mode 3 (t)1-t2):t1At that time, the potential at the point R is reduced to 0, Da4Natural conduction, Sa4Reaching ZVS commutation condition, FIG. 7 is the equivalent circuit diagram of this mode; the voltage at two ends of the exciting inductor is opposite to the current direction, and the magnitude of the exciting current is linearly reduced; the current of the commutation inductor is linearly increased; t is tAAt that moment, the primary winding current is reduced to zero, Sa4May be in the time period t1-tAThe ZVS conduction is controlled between the two switches;
the primary winding current in the mode is as follows:
auxiliary pipe Sa4The soft on-time of (d) is:
Sa3turn off to Sa4The on-time interval DN1 is: (ii) a
Charging mode (t)1-t2) The current conversion inductance current is:
wherein: v'AUXIs the secondary side voltage of the transformer;
iLr(t2)=Ir+iLoad\ formula (33)
Simultaneous, charging mode (T)1-2) The duration of (c) is:
Sa4is conducted to S1The off-time interval DN2 is:
mode 4 (t)2-t3):t2At the moment, the main switch S1Off, fig. 8 is an equivalent circuit diagram of this mode;current-converting inductive current iLrPart I of the medium excess load currentrTo the capacitor C2Discharge C1Charging, and the potential of the point O starts to decrease in resonance;
potential v at point OOAnd a current of commutation iLrThe expression is as follows:
wherein:
t3at that time, the potential at point O is lowered to V'AUX(ii) a The mode duration is:
wherein:
S1is conducted to Sa1The off-time interval DN3 is:
DN3=T2-3formula (46)
Mode 5 (t)3-t5):t3At that time, the potential at point O is lowered to V'AUXTurn off Sa1Excitation current iLmIs increased toExcitation currentTo Ca1Charging Ca2Discharging, and enabling the potential of the point Q to start to approximately linearly decrease; t is t4At that time, the potential at the point Q is lowered to 0, Da2Conducting naturally;
t3-t4the duration is:
Sa1turn off to Sa2The on-time interval DN4 is:
DN4=T3-4formula (42)
Mode 6 (t)5-t6) At t5Time of day, D2Natural conduction, S2The ZVS commutation condition is met; current-converting inductive current iLrLinear decrease, tBAt the moment, the current changes the inductive current iLrDown to the load current iLoad(ii) a Main switch tube S2May be in the time period t5-tBThe ZVS conduction is realized by controlling the conduction;
t5at that time, the potential at the point O rises to VDC;S2The commutation time is as follows:
thus, obtaining: s2ZVS on mode duration is:
Sa2is conducted to S1The on-time interval DN5 is:
mode 7 (t)6-t8):tB-t6Determined by PWM control requirement, t6At time, turn off S2Load current iLoadTo C2Charging, C1Discharging, and linearly increasing the potential of the O point; t is t7At that time, the potential at the point O rises to VDCDiode D1Conducting naturally; s1Can be at t7Then controlling the conduction;
t6-t7the duration is:
S1turn off to S2The on-time interval DN6 is:
DN6=T6-7\ formula (48)
Mode 8 (t)8-t9):t8At time, turn off Sa4FIG. 9 shows an equivalent circuit diagram of this mode, in which an excitation current is appliedTo Ca4Charging Ca3Discharging, and the potential of the R point begins to rise;
wherein:
at t9At the moment, the potential at the point R resonates to VAUXWhen this mode continuesThe method comprises the following steps:
mode 9 (t)9-t10):t9At that time, the potential at the point R rises to VAUXDa3Natural conduction, Sa3Reach ZVS commutation condition, tCAt the moment, the excitation current is reduced to zero; sa3May be in the time period T9CControl conduction between the two;
the excitation current in the mode is as follows:
Sa3the soft on-time of (d) is:
Sa4turn off to Sa3The on-time interval DN7 is:
Sa3is conducted to Sa2The off-time interval DN8 is:
mode 10 (t)10-t11):t10At time, turn off Sa2(ii) a Auxiliary converter transformer excitation currentTo Ca2Charging Ca1Discharging, and enabling the potential of the point Q to rise approximately linearly; t is t11At that time, the potential at the point P rises to VAUX,Da1Conducting naturally; controlling conduction S before the next switching cyclea1;
The mode duration is:
Sa2turn off to Sa1The on-time interval DN9 is:
DN9=T10-11formula (59).
As a further improvement of the above scheme, it can be known from the analysis of the above circuit structure and working principle that the main switch needs to design a commutation inductor, a transformer turn ratio and a switch parallel absorption capacitor to complete zero-voltage commutation; the auxiliary switch needs to design an excitation inductor to complete zero voltage commutation;
the above design of each element parameter will be completed as follows (analysis with output current as positive):
when V'AUXLess than VDCWhen/2, the S is cut off under the condition that the commutation current is larger than the load current by a certain value2Ensuring that the switching tube reliably completes current conversion; and the turn-off loss of the main switch is proportional to the square of the channel current at the turn-off instant [8,13 ]]Thus S2The turn-off loss of the main switch is approximately negligible (turn-off loss is less than 1/10) when the formula is satisfied:
wherein ILoad_rmsIs the effective value of the load current;
during actual circuit operation, load current detection has errors, resulting in IrError of (2), influence commutation time T2-5And ZVT on-time T5BAfter summation of the formula IrDerivation is carried out asrThe dead time of the main switch when the formula is met can be a fixed value;
simultaneous:
thus, obtaining:
wherein the value range of beta obtained by the solution of the sum is as follows:
to ensure reliable commutation of the lagging arm and Sa4Sufficient ZVS on-time, taken together, to obtain:
to ensure magnetizing current in commutation inductor LrAfter the linear discharge phase (t ═ t)4) And a resonant inductor LrBefore the linear charging phase (t ═ t)1) Equal in magnitude and opposite in direction (neglecting the change of magnetizing current in the resonant commutation stage of the hysteresis arm at the primary side):
wherein T is13T is obtained by summing up different time patterns of load1-t3Of each switching cycle, therebyDifferent; it can be seen from the sum that when the load current is 0,and T1AMinimum value, L calculated under this conditionmAccording to the condition that S is greater than 0 when any load current isa4There is a requirement for enough ZVS on-time;
will iLoadT is the sum of 01-t3The time interval of (c):
T13=T13_minformula (104)
Simultaneous:
wherein T is1A_minWhen the load current is 0, Sa4ZVS on time T1AThe value of (c).
The invention has the beneficial effects that:
compared with the prior art, the circuit of the invention utilizes the phase correlation method to keep the prior art, realizes the advantage of zero voltage switching-on of the main switch tube, reduces the switching loss of the main switch, and in addition, the auxiliary switch in the auxiliary loop also realizes the zero voltage switching-on through the energy storage in the excitation inductor and the voltage withstanding value of the auxiliary switch is far smaller than that of the main switch; the magnetizing current reset is reliably realized in each switching period, and the volume of the transformer is effectively reduced; the secondary winding of the transformer is coupled to solve the problem of an auxiliary converter diode DN1And DN2The problem of overpressure.
Drawings
The following detailed description of embodiments of the invention is provided in conjunction with the appended drawings, in which:
FIG. 1 is a prior art [12] soft switching inverter circuit with an auxiliary loop using two transformers;
FIG. 2 is a prior art [11] soft switching inverter circuit with two transformers for the auxiliary loop;
FIG. 3 is an auxiliary resonant commutating pole inverter circuit with bi-directional reset of the phase-correlated magnetizing current of the present invention;
FIG. 4 is a first commutating diode (D)C1) A freewheeling path for reverse recovery current;
FIG. 5 is a second commutating diode (D)C2) A freewheeling path for reverse recovery current;
FIG. 6 is a state diagram of the circuit of the present invention for each mode of a PWM switching cycle when the output current is positive;
FIG. 7 is a state diagram of the circuit of the present invention in each mode during a PWM switching cycle when the output current is negative;
FIG. 8 is a schematic diagram of the equivalent circuit of mode 2 in one PWM switching cycle in accordance with the present invention;
FIG. 9 is a schematic diagram of the equivalent circuit of mode 3 in one PWM switching cycle according to the present invention;
FIG. 10 is a schematic diagram of the equivalent circuit of mode 4 in one PWM switching cycle according to the present invention;
FIG. 11 is a schematic diagram of the equivalent circuit of mode 8 in one PWM switching cycle according to the present invention;
FIG. 12 is a waveform diagram of the driving pulse signal and the main node voltage and the branch current of each switching tube in a PWM switching period when the output current is positive in the circuit of the present invention;
FIG. 13 is a waveform diagram of the driving pulse signal and the primary node voltage and current of each switching tube in a PWM switching period when the output current is negative.
Detailed Description
As shown in fig. 1-13, the auxiliary resonant inverter with symmetrically reset phase-related magnetizing currents provided by the present invention includes a first main switch transistor S1A second main switching tube S2, a first converter diode Dc1, a second converter diode Dc2, a first freewheeling diode Dx1, a second freewheeling diode Dx2, a direct-current power supply VDC, an auxiliary power supply VAUX, a Load first voltage-dividing capacitor Cd1, a second voltage-dividing capacitor Cd2, a resonant inductor Lr1, a resonant inductor Lr2, an auxiliary converter transformer primary winding T1, an auxiliary converter transformer secondary winding T2, an auxiliary converter transformer secondary winding T3, a first auxiliary switching tube Sa1, a second auxiliary switching tube Sa2, a third auxiliary switching tube Sa3, a fourth auxiliary switching tube Sa4, an AC-Lag lagging bridge arm AC-Lead exciting inductor Lm, wherein 1. the source electrode of the first main switching tube S1 and the drain electrode of the second main switching tube S2 are at an O point, and the two switching tubes are connected to form a main switching arm; the drain electrode of the first main switching tube S1, the cathode of the first commutation diode Dc1 and the cathode of the second freewheeling diode Dx2 are connected with the anode of the direct-current power supply VDC; the negative electrode of the direct-current power supply VDC is connected with the source electrode of the second main switching tube S2, the positive electrode of the second commutation diode Dc2 and the positive electrode of the first freewheeling diode Dx 1; one end of the Load is connected with the point O of the middle point of the bridge arm of the main switch, and the other end of the Load is connected with the middle points of the first voltage-dividing capacitor Cd1 and the second voltage-dividing capacitor Cd 2; one end of the resonant inductor Lr1 is connected with the point O of the midpoint of the main switch bridge arm, and the other end of the resonant inductor Lr1 is connected with the synonym end of the auxiliary side first winding T2 of the auxiliary converter transformer; the dotted terminal of the auxiliary side first winding T2 of the auxiliary converter transformer is connected with the anode of the first converter diode Dc1 and the cathode of the first freewheeling diode Dx 1; one end of the resonant inductor Lr2 is connected with the point O of the midpoint of the main switch bridge arm, and the other end of the resonant inductor Lr2 is connected with the synonym end of the secondary side second winding T3 of the auxiliary converter transformer; the dotted terminal of the secondary side second winding T3 of the auxiliary converter transformer is connected with the cathode of the second converter diode Dc2 and the anode of the second freewheeling diode Dx 2; the source electrode of the first auxiliary switching tube Sa1 and the drain electrode of the second auxiliary switching tube Sa2 are connected to a point Q, and the two switching tubes form an advance bridge arm AC-Lang of the commutation auxiliary circuit; the source electrode of the third auxiliary switching tube Sa3 and the drain electrode of the fourth auxiliary switching tube Sa4 are connected to a point R, and the two switching tubes form a hysteresis bridge arm AC-Lead of the commutation auxiliary circuit; the drain of the first auxiliary switch tube Sa1 and the drain of the third auxiliary switch tube Sa3 are connected to the positive electrode of the auxiliary power supply VAUX, the negative electrode of the auxiliary power supply VAUX is connected to the source electrode of the second auxiliary switch tube Sa2,the source electrode of the fourth auxiliary switching tube Sa4 is connected; the dotted end of the primary winding T1 of the auxiliary converter transformer is connected with the midpoint Q point of the leading auxiliary switch bridge arm, and the unlike end is connected with the midpoint R point of the lagging auxiliary switch bridge arm; the exciting inductance Lm is connected in parallel with two ends of a primary winding T1 of the auxiliary converter transformer; the number of turns of the first winding T2 and the second winding T3 on the secondary side of the auxiliary converter transformer is the same, the number of turns of the primary winding T1 of the auxiliary converter transformer and the turn ratio of T2 or T3 are 1/n, and the first freewheeling diode Dx1And a second freewheeling diode Dx2Has the effect of being at the first commutation diode Dc1And a second commutation diode Dc2Providing follow current paths for reverse current in reverse recovery process, wherein the follow current paths are respectively T2->Lr1->S2->DX1->T2And T3->DX2->S1->Lr2->T3。
As a further improvement of the above scheme, when the load current is positive, the operation mode and the switching time interval are as follows:
the circuit is in a steady state, S2、Sa1、Sa3In the on state, S1、Sa2、Sa4In an off state; current conversion diode DN1、DN2Freewheel diode Dx1、Dx2A voltage stabilizing diode Dz1、Dz2And the anti-parallel diode of the switching tube is in a turn-off state;
t0at time, turn off Sa3;
Sa3Delay DP1 after turn-off, turn on Sa4;
Sa4Delay DP2 after switching on, turn off S2;
S2Delay DP3 after shutdown, turn off Sa1;
Sa1Delay DP4 after turn-off, turn on Sa2;
Sa2Delay DP5 after conduction, turn on S1;
S1Delay after conduction TonTurn off S1;
S1Delay DP6 after turn-off, turn on S2;
At t0Time of day, Sa3Delay after shutdown TSW/2, turn off Sa4;
Sa4Delay DP7 after turn-off, turn on Sa3;
Sa3Delay DP8 after switching on, turn off Sa2;
Off Sa2Delay DP9, turn on Sa1;
The working mode and the switching time interval when the load current is negative are:
the circuit is in a steady state, S1、Sa1、Sa3In the on state, S2、Sa2、Sa4In an off state; current conversion diode DN1、DN2Freewheel diode Dx1、Dx2A voltage stabilizing diode Dz1、Dz2And the anti-parallel diode of the switching tube is in a turn-off state;
t0at time, turn off Sa3;
Sa3DN1 is delayed after the switch-off, and S is conducteda4;
Sa4DN2 is delayed after conduction and S is turned off1;
S1Delay DP3 after shutdown, turn off Sa1;
Sa1Delay DP4 after turn-off, turn on Sa2;
Sa2Delay DP5 after conduction, turn on S2;
S2Delay after conduction TonTurn off S2;
S2Delay DP6 after turn-off, turn on S1;
At t0Time of day, Sa3Delay after shutdown TSW/2, turn off Sa4;
Sa4DN7 is delayed after the switch-off, and S is conducteda3;
Sa3DN8 is delayed after conduction and S is turned offa2;
Turning off Sa2, delaying DN9, and turning on Sa 1;
wherein the following parameters are input quantities: vDCIs a dc bus voltage; vAUXIs the auxiliary supply voltage; t is1A_minThe shortest ZVS on-time for Sa 4; t is3BShortest on time of S1 (S2); i isrThe part of the commutation current peak value exceeding the load current; cm_ossIs a main switch tube S1-S2Parallel absorption capacitance: cm_oss=C1=C2;Ca_ossFor auxiliary switching of the tube Sa1-Sa4Parallel absorption capacitor Ca_oss=Ca1=Ca2=Ca3=Ca4(ii) a The following parameters can be expressed in terms of input quantity constraints; vA'UXIs the secondary side voltage of the transformer; l isrIs a commutation inductance; l ismIs an excitation inductor;the exciting current value before the current conversion of the auxiliary switch is in positive correlation with the load current value in each switching period;
wherein T is13_minTo ignore the current change before charging the commutation current, iLoadT obtained by adding 01-t3The time interval of (c); t is1A_minWhen the load current is 0, Sa4ZVS on time T1AThe value of (c).
As a further improvement of the above scheme, the specific description of each mode and the calculation process of the interval time when the output current is positive are as follows:
mode 1 (t)<t0): the circuit is in a steady state, S2In a conducting state; load current ILoadBy S2Afterflow; sa1、Sa3Conducting, exciting current iLmBy Sa1、Sa3Free flow of value of
Mode 2 (t)0-t1):t0At time, turn off Sa3(ii) a Commutation inductor LrThrough a transformer and an excitation inductor LmAfter being connected in parallel with an auxiliary capacitor Ca3、Ca4Resonance occurs, the potential of the point R drops, and an equivalent circuit diagram is shown in FIG. 6; current converting inductive currentIncrease from zero; excitation currentChanging to the positive direction;
exciting the inductive current according to the relation between the instantaneous value of the inductive current and the integral of the terminal voltage and the initial value of the currentAnd the current of the current converter
Wherein ω isaFor resonant angular frequency:
at t1Time of day, Sa3Voltage resonance at both ends to VAUXThe time according to the present resonance mode is:
mode 3 (t)1-t2):t1At that time, the potential at the point R is reduced to 0, Da4Natural conduction, Sa4Reaching ZVS commutation conditions, fig. 7 is an equivalent circuit diagram of this mode; the voltage at two ends of the exciting inductor is opposite to the current direction, and the magnitude of the exciting current is linearly reduced; the current of the commutation inductor is linearly increased; t is tAAt that moment, the primary winding current is reduced to zero, Sa4May be in the time period t1-tAThe ZVS conduction is controlled between the two switches;
the primary winding current in the mode is as follows:
auxiliary pipe Sa4The soft on-time of (d) is:
Sa3turn off to Sa4The on-time interval DP1 is:
charging mode (t)1-t2) The current conversion inductance current is:
wherein: v'AUXIs the secondary side voltage of the transformer;
iLr(t2)=Ir+iLoad\ formula (33)
Simultaneous, charging mode (T)1-2) The duration of (c) is:
Sa4is conducted to S2The off-time interval DP2 is:
mode 4 (t)2-t3):t2At the moment, the main switch S2Off, fig. 8 is an equivalent circuit diagram of this mode; current-converting inductive current iLrPart I of the medium excess load currentrTo the capacitor C1Discharge C2Charging, and enabling the potential of the point O to start resonant rising;
potential v at point OOAnd a current of commutation iLrThe expression is as follows:
wherein:
t3at that time, the potential at the point O rises to VDC-V'AUX(ii) a The mode duration is:
wherein:
S1is conducted to Sa1The off-time interval DP3 is:
DP3=T2-3formula (46)
Mode 5 (t)3-t5):t3At that time, the potential at the point O rises to VDC-V'AUXTurn off Sa1Excitation current iLmIs increased toExcitation currentTo Ca1Charging Ca2Discharging, and enabling the potential of the point Q to start to approximately linearly decrease; t is t4At that time, the potential at the point Q is lowered to 0, Da2Conducting naturally;
t3-t4the duration is:
Sa1turn off to Sa2The on-time interval DP4 is:
DP4=T3-4formula (42)
Mode 6 (t)5-t6) At t5Time of day, D1Natural conduction, S1The ZVS commutation condition is met; current-converting inductive current iLrLinear decrease, tBAt the moment, the current changes the inductive current iLrDown to the load current iLoad(ii) a Main switch tube S1May be in the time period t5-tBThe ZVS conduction is realized by controlling the conduction;
t5at that time, the potential at the point O rises to VDC;S1The commutation time is as follows:
thus, obtaining: s1ZVS on mode duration is:
Sa2is conducted to S1The on-time interval DP5 is:
mode 7 (t)6-t8):tB-t6Determined by PWM control requirement, t6At time, turn off S1Load current iLoadTo C1Charging, C2Discharging, and linearly reducing the potential of the O point; t is t7At that time, the potential at the point O is reduced to 0, and the diode D2Conducting naturally; s2Can be at t7Then controlling the conduction;
t6-t7the duration is:
S1turn off to S2The on-time interval DP6 is:
DP6=T6-7\ formula (48)
Mode 8 (t)8-t9):t8At time, turn off Sa4FIG. 9 shows an equivalent circuit diagram of this mode, in which an excitation current is appliedTo Ca4Charging Ca3Discharging, and the potential of the R point begins to rise;
wherein:
at t9At the moment, the potential at the point R resonates to VAUXThe pattern duration is:
mode 9 (t)9-t10):t9At that time, the potential at the point R rises to VAUX,Da3Natural conduction, Sa3To reach ZVS commutation condition, tCAt the moment, the excitation current is reduced to zero; sa3May be in the time period T9CControl conduction between the two;
the excitation current in the mode is as follows:
Sa3the soft on-time of (d) is:
Sa4turn off to Sa3The on-time interval DP7 is:
Sa3is conducted to Sa2The off-time interval DP8 is:
mode 10 (t)10-t11):t10At time, turn off Sa2(ii) a Auxiliary converter transformer excitation currentTo Ca2Charging Ca1Discharging, and enabling the potential of the point Q to rise approximately linearly; t is t11At that time, the potential at the point P rises to VAUX,Da1Conducting naturally; controlling conduction S before the next switching cyclea1;
The mode duration is:
Sa2turn off to Sa1The on-time interval DP9 is:
DP9=T10-11formula (59)
The specific description of each mode and the calculation process of the interval time when the output current is negative are as follows:
mode 1 (t)<t0): the circuit is in a steady state, S1In a conducting state; load current ILoadBy S1Follow current, Sa1、Sa3Conducting, exciting current iLmBy Sa1、Sa3Free flow of value of
Mode 2 (t)0-t1):t0At time, turn off Sa3(ii) a Commutation inductor LrThrough a transformer and an excitation inductor LmAfter being connected in parallel with an auxiliary capacitor Ca3、Ca4Resonance occurs, the potential of the point R drops, and an equivalent circuit diagram is shown in FIG. 6; current converting inductive currentIncrease from zero; excitation currentChanging to the positive direction;
exciting the inductive current according to the relation between the instantaneous value of the inductive current and the integral of the terminal voltage and the initial value of the currentAnd the current of the current converter
Wherein ω isaFor resonant angular frequency:
at t1Time of day, Sa3Voltage resonance at both ends to VAUXThe time according to the present resonance mode is:
mode 3 (t)1-t2):t1At that time, the potential at the point R is reduced to 0, Da4Natural conduction, Sa4To achieveZVS commutation condition, FIG. 7 is the equivalent circuit diagram of this mode; the voltage at two ends of the exciting inductor is opposite to the current direction, and the magnitude of the exciting current is linearly reduced; the current of the commutation inductor is linearly increased; t is tAAt that moment, the primary winding current is reduced to zero, Sa4May be in the time period t1-tAThe ZVS conduction is controlled between the two switches;
the primary winding current in the mode is as follows:
auxiliary pipe Sa4The soft on-time of (d) is:
Sa3turn off to Sa4The on-time interval DN1 is: (ii) a
Charging mode (t)1-t2) The current conversion inductance current is:
wherein: v'AUXIs the secondary side voltage of the transformer;
iLr(t2)=Ir+iLoad\ formula (33)
Simultaneous, charging mode (T)1-2) The duration of (c) is:
Sa4is conducted to S1The off-time interval DN2 is:
mode 4 (t)2-t3):t2At the moment, the main switch S1Off, fig. 8 is an equivalent circuit diagram of this mode; current-converting inductive current iLrPart I of the medium excess load currentrTo the capacitor C2Discharge C1Charging, and the potential of the point O starts to decrease in resonance;
potential v at point OOAnd a current of commutation iLrThe expression is as follows:
wherein:
t3at that time, the potential at point O is lowered to V'AUX(ii) a The mode duration is:
wherein:
S1is conducted to Sa1The off-time interval DN3 is:
DN3=T2-3formula (46)
Mode 5 (t)3-t5):t3At that time, the potential at point O is lowered to V'AUXTurn off Sa1Excitation current iLmIs increased toExcitation currentTo Ca1Charging Ca2Discharging, and enabling the potential of the point Q to start to approximately linearly decrease; t is t4At that time, the potential at the point Q is lowered to 0, Da2Conducting naturally;
t3-t4the duration is:
Sa1turn off to Sa2The on-time interval DN4 is:
DN4=T3-4formula (42)
Mode 6 (t)5-t6) At t5Time of day, D2Natural conduction, S2The ZVS commutation condition is met; current-converting inductive current iLrLinear decrease, tBAt the moment, the current changes the inductive current iLrDown to the load current iLoad(ii) a Main switch tube S2May be in the time period t5-tBThe ZVS conduction is realized by controlling the conduction;
t5at that time, the potential at the point O rises to VDC;S2The commutation time is as follows:
thus, obtaining: s2ZVS on mode duration is:
Sa2is conducted to S1The on-time interval DN5 is:
mode 7 (t)6-t8):tB-t6Determined by PWM control requirement, t6At time, turn off S2Load current iLoadTo C2Charging, C1Discharging, and linearly increasing the potential of the O point; t is t7At that time, the potential at the point O rises to VDCDiode D1Conducting naturally; s1Can be at t7Then controlling the conduction;
t6-t7the duration is:
S1turn off to S2The on-time interval DN6 is:
DN6=T6-7\ formula (48)
Mode 8 (t)8-t9):t8At time, turn off Sa4FIG. 9 shows an equivalent circuit diagram of this mode, in which an excitation current is appliedTo Ca4Charging Ca3Discharging, and the potential of the R point begins to rise;
wherein:
at t9At the moment, the potential at the point R resonates to VAUXThe pattern duration is:
mode 9 (t)9-t10):t9At that time, the potential at the point R rises to VAUXDa3Natural conduction, Sa3Reach ZVS commutation condition, tCAt the moment, the excitation current is reduced to zero; sa3May be in the time period T9CControl conduction between the two;
the excitation current in the mode is as follows:
Sa3the soft on-time of (d) is:
Sa4turn off to Sa3The on-time interval DN7 is:
Sa3is conducted to Sa2The off-time interval DN8 is:
mode 10 (t)10-t11):t10At time, turn off Sa2(ii) a Auxiliary converter transformer excitation currentTo Ca2Charging Ca1Discharging, and enabling the potential of the point Q to rise approximately linearly; t is t11At that time, the potential at the point P rises to VAUX,Da1Conducting naturally; controlling conduction S before the next switching cyclea1;
The mode duration is:
Sa2turn off to Sa1The on-time interval DN9 is:
DN9=T10-11formula (59).
As a further improvement of the above scheme, it can be known from the analysis of the above circuit structure and working principle that the main switch needs to design a commutation inductor, a transformer turn ratio and a switch parallel absorption capacitor to complete zero-voltage commutation; the auxiliary switch needs to design an excitation inductor to complete zero voltage commutation;
the above design of each element parameter will be completed as follows (analysis with output current as positive):
when V'AUXLess than VDCWhen/2, the S is cut off under the condition that the commutation current is larger than the load current by a certain value2Ensuring that the switching tube reliably completes current conversion; and the turn-off loss of the main switch is proportional to the square of the channel current at the turn-off instant [8,13 ]]Thus S2The turn-off loss of the main switch is approximately negligible (turn-off loss is less than 1/10) when the formula is satisfied:
wherein ILoad_rmsIs the effective value of the load current;
during actual circuit operation, load current detection has errors, resulting in IrError of (2), influence commutation time T2-5And ZVT on-time T5BAfter summation of the formula IrDerivation is carried out asrThe dead time of the main switch when the formula is met can be a fixed value;
simultaneous:
thus, obtaining:
wherein the value range of beta obtained by the solution of the sum is as follows:
to ensure reliable commutation of the lagging arm and Sa4Sufficient ZVS on-time, taken together, to obtain:
to ensure magnetizing current in commutation inductor LrAfter the linear discharge phase (t ═ t)4) And a resonant inductor LrBefore the linear charging phase (t ═ t)1) Equal in magnitude and opposite in direction (neglecting the change of magnetizing current in the resonant commutation stage of the hysteresis arm at the primary side):
wherein T is13T is obtained by summing up different time patterns of load1-t3Of each switching cycle, therebyDifferent; it can be seen from the sum that when the load current is 0,and T1AMinimum value, L calculated under this conditionmAccording to the condition that S is greater than 0 when any load current isa4There is a requirement for enough ZVS on-time;
will iLoadT is the sum of 01-t3The time interval of (c):
T13=T13_minformula (104)
Simultaneous:
wherein T is1A_minWhen the load current is 0, Sa4ZVS on time T1AThe value of (c).
Auxiliary converter transformer TXBy a primary winding T1(number of winding turns N1), two secondary windings T2、T3Ideal transformer (N-2/N-1/N-3/N-1) and field inductance L (N-2, N-3 winding turns)mComposition is carried out;
when the output current is positive, the state diagram of the circuit of each mode in one PWM switching period is shown in FIG. 4, and the waveforms of the driving pulse signal of each switching tube, the main node voltage and the branch current are shown in FIG. 10. When the output current is negative, the state diagram of the circuit in each mode in one PWM switching period is shown in fig. 5, and the waveforms of the driving pulse signal of each switching tube, the main node voltage and the branch current are shown in fig. 11.
The following analysis was performed for both cases where the output current was positive and negative, respectively. Since the load inductance is large enough, the load current is considered constant during one PWM switching period.
The forward direction of reference for each electrical variable in the loop coincides with the direction of the arrow in fig. 3.
The input parameters are shown in table 1:
input DC voltage (V)DC) | 400V |
Auxiliary voltage (V)AUX) | 20V |
Switching frequency (f)sw) | 20KHz |
Cm_oss | 100pF |
Ca_oss | 1000pF |
Ir | 2A |
T1A | 10ns |
T3B | 10ns |
TABLE 1 input parameters
Specific values of inductance and transformer calculated from constraints of input parameters are shown in Table 2
Commutation inductance (L)r) | 4.21uH |
Excitation inductor (L)m) | 954nH |
Secondary side voltage (V) of transformerA'UX) | 60V |
TABLE 2
DP3=DN3=T2-323.5ns \ equation (109)
The above embodiments are not limited to the technical solutions of the embodiments themselves, and the embodiments may be combined with each other into a new embodiment. The above embodiments are only for illustrating the technical solutions of the present invention and are not limited thereto, and any modification or equivalent replacement without departing from the spirit and scope of the present invention should be covered within the technical solutions of the present invention.
Claims (4)
1. An auxiliary resonance converter pole inverter with phase-correlated magnetizing current symmetrical reset is characterized in that: the auxiliary converter transformer comprises a first main switching tube (S1), a second main switching tube (S2), a first converter diode (Dc1), a second converter diode (Dc2), a first freewheeling diode (Dx1), a second freewheeling diode (Dx2), a direct current power supply (VDC) auxiliary power supply (VAUX) Load (Load), a first voltage division capacitor (Cd1), a second voltage division capacitor (Cd2), a resonant inductor (Lr1), a resonant inductor (Lr2), an auxiliary converter transformer primary winding (T1), an auxiliary converter transformer secondary side first winding (T2), a second winding (T3) at the auxiliary converter secondary side, a second auxiliary switching tube (Sa1), a third auxiliary switching tube (Sa3), a fourth auxiliary switching tube (Sa4), a leading bridge arm (AC-Lag) lagging bridge arm (AC-Lm) exciting inductor (Sa4), a first main switching tube (S2), a second switching tube (S638), a second auxiliary switching tube (Cd1), the two switching tubes form a main switching bridge arm; the drain electrode of the first main switching tube (S1), the cathode of the first commutation diode (Dc1) and the cathode of the second freewheeling diode (Dx2) are connected with the anode of a direct-current power supply (VDC); the negative electrode of the direct current power supply (VDC) is connected with the source electrode of the second main switching tube (S2), the positive electrode of the second commutation diode (Dc2) and the positive electrode of the first freewheeling diode (Dx 1); one end of a Load (Load) is connected with a point O of the middle point of the bridge arm of the main switch, and the other end of the Load (Load) is connected with the middle points of a first voltage-dividing capacitor (Cd1) and a second voltage-dividing capacitor (Cd 2); one end of a resonant inductor (Lr1) is connected with the point O of the midpoint of the main switch bridge arm, and the other end of the resonant inductor is connected with the synonym end of the auxiliary side first winding (T2) of the auxiliary converter transformer; the dotted terminal of the auxiliary side first winding (T2) of the auxiliary converter transformer is connected with the anode of the first converter diode (Dc1) and the cathode of the first freewheeling diode (Dx 1); one end of the resonant inductor (Lr2) is connected with the point O of the midpoint of the main switch bridge arm, and the other end of the resonant inductor is connected with the synonym end of the secondary side second winding (T3) of the auxiliary converter transformer; secondary winding of auxiliary converter transformerThe dotted terminal of the group (T3) is connected with the cathode of the second commutation diode (Dc2) and the anode of the second freewheeling diode (Dx 2); the source electrode of the first auxiliary switching tube (Sa1) and the drain electrode of the second auxiliary switching tube (Sa2) are connected to a point Q, and the two switching tubes form a leading bridge arm (AC-Lang) of the commutation auxiliary circuit; the source electrode of the third auxiliary switching tube (Sa3) and the drain electrode of the fourth auxiliary switching tube (Sa4) are connected to the R point, and the two switching tubes form a hysteresis bridge arm (AC-Lead) of the commutation auxiliary circuit; the drain electrode of the first auxiliary switch tube (Sa1) and the drain electrode of the third auxiliary switch tube (Sa3) are connected with the positive electrode of the auxiliary power supply (VAUX), the negative electrode of the auxiliary power supply (VAUX) is connected with the source electrode of the second auxiliary switch tube (Sa2), and the source electrode of the fourth auxiliary switch tube (Sa 4); the dotted end of the primary winding (T1) of the auxiliary converter transformer is connected with the midpoint Q point of the leading auxiliary switch bridge arm, and the unlike end is connected with the midpoint R point of the lagging auxiliary switch bridge arm; the exciting inductance Lm is connected in parallel with two ends of a primary winding (T1) of the auxiliary converter transformer; the number of turns of a first winding (T2) and a second winding (T3) on the secondary side of the auxiliary converter transformer is the same, the number of turns of a primary winding (T1) of the auxiliary converter transformer and the turn ratio of T2 (or T3) are 1/n, and the first freewheeling diode (D)x1) And a second freewheeling diode (D)x2) Is applied to the first commutation diode (D)c1) And a second commutation diode (D)c2) Providing follow current paths for reverse current in reverse recovery process, wherein the follow current paths are respectively T2->Lr1->S2->DX1->T2And T3->DX2->S1->Lr2->T3。
2. A phase-correlated magnetizing current symmetrically reset auxiliary resonant commutating pole inverter of claim 1, characterized by:
when the load current is positive, the working mode and the switching time interval are as follows:
the circuit is in a steady state, S2、Sa1、Sa3In the on state, S1、Sa2、Sa4In an off state; current conversion diode DN1、DN2Freewheel diode Dx1、Dx2A voltage stabilizing diode Dz1、Dz2And the anti-parallel diode of the switching tube is in a turn-off state;
t0at time, turn off Sa3;
Sa3Delay DP1 after turn-off, turn on Sa4;
Sa4Delay DP2 after switching on, turn off S2;
S2Delay DP3 after shutdown, turn off Sa1;
Sa1Delay DP4 after turn-off, turn on Sa2;
Sa2Delay DP5 after conduction, turn on S1;
S1Delay after conduction TonTurn off S1;
S1Delay DP6 after turn-off, turn on S2;
At t0Time of day, Sa3Delay after shutdown TSW/2, turn off Sa4;
Sa4Delay DP7 after turn-off, turn on Sa3;
Sa3Delay DP8 after switching on, turn off Sa2;
Off Sa2Delay DP9, turn on Sa1;
The working mode and the switching time interval when the load current is negative are:
the circuit is in a steady state, S1、Sa1、Sa3In the on state, S2、Sa2、Sa4In an off state; current conversion diode DN1、DN2Freewheel diode Dx1、Dx2A voltage stabilizing diode Dz1、Dz2And the anti-parallel diode of the switching tube is in a turn-off state;
t0at time, turn off Sa3;
Sa3DN1 is delayed after the switch-off, and S is conducteda4;
Sa4DN2 is delayed after conduction and S is turned off1;
S1Delay DP3 after shutdown, turn off Sa1;
Sa1Delay DP4 after turn-off, turn on Sa2;
Sa2Delay DP5 after conduction, turn on S2;
S2Delay after conduction TonTurn off S2;
S2Delay DP6 after turn-off, turn on S1;
At t0Time of day, Sa3Delay after shutdown TSW/2, turn off Sa4;
Sa4DN7 is delayed after the switch-off, and S is conducteda3;
Sa3DN8 is delayed after conduction and S is turned offa2;
Turning off Sa2, delaying DN9, and turning on Sa 1;
wherein the following parameters are input quantities: vDCIs a dc bus voltage; vAUXIs the auxiliary supply voltage; t is1A_minThe shortest ZVS on-time for Sa 4; t is3BShortest on time of S1 (S2); i isrThe part of the commutation current peak value exceeding the load current; cm_ossIs a main switch tube S1-S2Parallel absorption capacitance: cm_oss=C1=C2;Ca_ossFor auxiliary switching of the tube Sa1-Sa4Parallel absorption capacitor Ca_oss=Ca1=Ca2=Ca3=Ca4(ii) a The following parameters can be expressed in terms of input quantity constraints; v'AUXIs the secondary side voltage of the transformer; l isrIs a commutation inductance; l ismIs an excitation inductor;the exciting current value before the current conversion of the auxiliary switch is in positive correlation with the load current value in each switching period;
wherein T is13_minTo ignore the current change before charging the commutation current, iLoadT obtained by adding 01-t3The time interval of (c); t is1A_minWhen the load current is 0, Sa4ZVS on time T1AThe value of (c).
3. A phase-correlated magnetizing current symmetrically reset auxiliary resonant commutating pole inverter of claim 2, characterized by:
the specific description of each mode and the calculation process of the interval time when the output current is positive are as follows:
mode 1 (t)<t0): the circuit is in a steady state, S2In a conducting state; load current ILoadBy S2Afterflow; sa1、Sa3Conducting, exciting current iLmBy Sa1、Sa3Free flow of value of
Mode 2 (t)0-t1):t0At time, turn off Sa3(ii) a Commutation inductor LrThrough a transformer and an excitation inductor LmAfter being connected in parallel with an auxiliary capacitor Ca3、Ca4Resonance occurs, the potential of the point R drops, and an equivalent circuit diagram is shown in FIG. 6; current converting inductive currentIncrease from zero; excitation currentChanging to the positive direction;
exciting the inductive current according to the relation between the instantaneous value of the inductive current and the integral of the terminal voltage and the initial value of the currentAnd the current of the current converter
Wherein ω isaFor resonant angular frequency:
at t1Time of day, Sa3Voltage resonance at both ends to VAUXThe time according to the present resonance mode is:
mode 3 (t)1-t2):t1At that time, the potential at the point R is reduced to 0, Da4Natural conduction, Sa4Reaching ZVS commutation conditions, fig. 7 is an equivalent circuit diagram of this mode; the voltage at two ends of the exciting inductor is opposite to the current direction, and the magnitude of the exciting current is linearly reduced; the current of the commutation inductor is linearly increased; t is tAAt that moment, the primary winding current is reduced to zero, Sa4May be in the time period t1-tAThe ZVS conduction is controlled between the two switches;
the primary winding current in the mode is as follows:
auxiliary pipe Sa4The soft on-time of (d) is:
Sa3turn off to Sa4The on-time interval DP1 is:
charging mode (t)1-t2) The current conversion inductance current is:
wherein: v'AUXIs the secondary side voltage of the transformer;
iLr(t2)=Ir+iLoad\ formula (33)
Simultaneous, charging mode (T)1-2) The duration of (c) is:
Sa4is conducted to S2The off-time interval DP2 is:
mode 4 (t)2-t3):t2At the moment, the main switch S2Off, fig. 8 is an equivalent circuit diagram of this mode; current-converting inductive current iLrPart I of the medium excess load currentrTo the capacitor C1Discharge C2Charging, and enabling the potential of the point O to start resonant rising;
potential v at point OOAnd a current of commutation iLrThe expression is as follows:
wherein:
t3at that time, the potential at the point O rises to VDC-V′AUX(ii) a The mode duration is:
wherein:
S1is conducted to Sa1The off-time interval DP3 is:
DP3=T2-3formula (46)
Mode 5 (t)3-t5):t3At that time, the potential at the point O rises to VDC-V′AUXTurn off Sa1Excitation current iLmIs increased toExcitation currentTo Ca1Charging Ca2Discharging, and enabling the potential of the point Q to start to approximately linearly decrease; t is t4At that time, the potential at the point Q is lowered to 0, Da2Conducting naturally;
t3-t4the duration is:
Sa1turn off to Sa2The on-time interval DP4 is:
DP4=T3-4formula (42)
Mode 6 (t)5-t6) At t5Time of day, D1The switch-on is carried out naturally,S1the ZVS commutation condition is met; current-converting inductive current iLrLinear decrease, tBAt the moment, the current changes the inductive current iLrDown to the load current iLoad(ii) a Main switch tube S1May be in the time period t5-tBThe ZVS conduction is realized by controlling the conduction;
t5at that time, the potential at the point O rises to VDC;S1The commutation time is as follows:
thus, obtaining: s1ZVS on mode duration is:
Sa2is conducted to S1The on-time interval DP5 is:
mode 7 (t)6-t8):tB-t6Determined by PWM control requirement, t6At time, turn off S1Load current iLoadTo C1Charging, C2Discharging, and linearly reducing the potential of the O point; t is t7At that time, the potential at the point O is reduced to 0, and the diode D2Conducting naturally; s2Can be at t7Then controlling the conduction;
t6-t7the duration is:
S1turn off to S2The on-time interval DP6 is:
DP6=T6-7\ formula (48)
Mode 8 (t)8-t9):t8At time, turn off Sa4FIG. 9 shows an equivalent circuit diagram of this mode, in which an excitation current is appliedTo Ca4Charging Ca3Discharging, and the potential of the R point begins to rise;
wherein:
at t9At the moment, the potential at the point R resonates to VAUXThe pattern duration is:
mode 9 (t)9-t10):t9At that time, the potential at the point R rises to VAUX,Da3Natural conduction, Sa3Reach ZVS commutation condition, tCAt the moment, the excitation current is reduced to zero; sa3May be in the time period T9CControl conduction between the two;
the excitation current in the mode is as follows:
Sa3the soft on-time of (d) is:
Sa4turn off to Sa3The on-time interval DP7 is:
Sa3is conducted to Sa2The off-time interval DP8 is:
mode 10 (t)10-t11):t10At time, turn off Sa2(ii) a Auxiliary converter transformer excitation currentTo Ca2Charging Ca1Discharge, potential approximation of Q-pointLinearly increasing; t is t11At that time, the potential at the point P rises to VAUX,Da1Conducting naturally; controlling conduction S before the next switching cyclea1;
The mode duration is:
Sa2turn off to Sa1The on-time interval DP9 is:
DP9=T10-11formula (59)
The specific description of each mode and the calculation process of the interval time when the output current is negative are as follows:
mode 1 (t)<t0): the circuit is in a steady state, S1In a conducting state; load current ILoadBy S1Follow current, Sa1、Sa3Conducting, exciting current iLmBy Sa1、Sa3Free flow of value of
Mode 2 (t)0-t1):t0At time, turn off Sa3(ii) a Commutation inductor LrThrough a transformer and an excitation inductor LmAfter being connected in parallel with an auxiliary capacitor Ca3、Ca4Resonance occurs, the potential of the point R drops, and an equivalent circuit diagram is shown in FIG. 6; current converting inductive currentIncrease from zero; excitation currentChanging to the positive direction;
exciting the inductive current according to the relation between the instantaneous value of the inductive current and the integral of the terminal voltage and the initial value of the currentAnd the current of the current converter
Wherein ω isaFor resonant angular frequency:
at t1Time of day, Sa3Voltage resonance at both ends to VAUXThe time according to the present resonance mode is:
mode 3 (t)1-t2):t1At that time, the potential at the point R is reduced to 0, Da4Natural conduction, Sa4Reaching ZVS commutation condition, FIG. 7 is the equivalent circuit diagram of this mode; the voltage at two ends of the exciting inductor is opposite to the current direction, and the magnitude of the exciting current is linearly reduced; the current of the commutation inductor is linearly increased; t is tAAt that moment, the primary winding current is reduced to zero, Sa4May be in the time period t1-tAThe ZVS conduction is controlled between the two switches;
the primary winding current in the mode is as follows:
auxiliary pipe Sa4The soft on-time of (d) is:
Sa3turn off to Sa4The on-time interval DN1 is: (ii) a
Charging mode (t)1-t2) The current conversion inductance current is:
wherein: v'AUXIs the secondary side voltage of the transformer;
iLr(t2)=Ir+iLoad\ formula (33)
Simultaneous, charging mode (T)1-2) The duration of (c) is:
Sa4is conducted to S1The off-time interval DN2 is:
mode 4 (t)2-t3):t2At the moment, the main switch S1Off, fig. 8 is an equivalent circuit diagram of this mode; current-converting inductive current iLrPart I of the medium excess load currentrTo the capacitor C2Discharge C1Charging, and the potential of the point O starts to decrease in resonance;
potential v at point OOAnd a current of commutation iLrThe expression is as follows:
wherein:
t3at that time, the potential at point O is lowered to V'AUX(ii) a Book mouldThe duration of formula is:
wherein:
S1is conducted to Sa1The off-time interval DN3 is:
DN3=T2-3formula (46)
Mode 5 (t)3-t5):t3At that time, the potential at point O is lowered to V'AUXTurn off Sa1Excitation current iLmIs increased toExcitation currentTo Ca1Charging Ca2Discharging, and enabling the potential of the point Q to start to approximately linearly decrease; t is t4At that time, the potential at the point Q is lowered to 0, Da2Conducting naturally;
t3-t4the duration is:
Sa1turn off to Sa2The on-time interval DN4 is:
DN4=T3-4formula (42)
Mode 6 (t)5-t6) At t5Time of day, D2Natural conduction, S2The ZVS commutation condition is met; current-converting inductive current iLrLinear decrease, tBAt the moment, the current changes the inductive current iLrDown to the load current iLoad(ii) a Main switch tube S2May be in the time period t5-tBThe ZVS conduction is realized by controlling the conduction;
t5at that time, the potential at the point O rises to VDC;S2The commutation time is as follows:
thus, obtaining: s2ZVS on mode duration is:
Sa2is conducted to S1The on-time interval DN5 is:
mode 7 (t)6-t8):tB-t6Determined by PWM control requirement, t6At time, turn off S2Load current iLoadTo C2Charging, C1Discharging, and linearly increasing the potential of the O point; t is t7At that time, the potential at the point O rises to VDCDiode D1Conducting naturally; s1Can be at t7Then controlling the conduction;
t6-t7the duration is:
S1turn off to S2The on-time interval DN6 is:
DN6=T6-7\ formula (48)
Mode 8 (t)8-t9):t8At time, turn off Sa4Book, bookThe equivalent circuit diagram of the mode is shown in FIG. 9, the exciting currentTo Ca4Charging Ca3Discharging, and the potential of the R point begins to rise;
wherein:
at t9At the moment, the potential at the point R resonates to VAUXThe pattern duration is:
mode 9 (t)9-t10):t9At that time, the potential at the point R rises to VAUXDa3Natural conduction, Sa3Reach ZVS commutation condition, tCAt the moment, the excitation current is reduced to zero; sa3May be in the time period T9CControl conduction between the two;
the excitation current in the mode is as follows:
Sa3the soft on-time of (d) is:
Sa4turn off to Sa3The on-time interval DN7 is:
Sa3is conducted to Sa2The off-time interval DN8 is:
mode 10 (t)10-t11):t10At time, turn off Sa2(ii) a Auxiliary converter transformer excitation currentTo Ca2Charging Ca1Discharging, and enabling the potential of the point Q to rise approximately linearly; t is t11At that time, the potential at the point P rises to VAUX,Da1Conducting naturally; controlling conduction S before the next switching cyclea1;
The mode duration is:
Sa2turn off to Sa1The on-time interval DN9 is:
DN9=T10-11formula (59).
4. A phase-correlated magnetizing current symmetrically reset auxiliary resonant commutating pole inverter of claim 3, characterized by: according to the analysis of the circuit structure and the working principle, the main switch needs to design a converter inductor, a transformer turn ratio and a switch parallel absorption capacitor when finishing zero voltage conversion; the auxiliary switch needs to design an excitation inductor to complete zero voltage commutation;
the above design of each element parameter will be completed as follows (analysis with output current as positive):
when V'AUXLess than VDCWhen/2, the S is cut off under the condition that the commutation current is larger than the load current by a certain value2Ensuring that the switching tube reliably completes current conversion; and the turn-off loss of the main switch is proportional to the square of the channel current at the turn-off instant [8,13 ]]Thus S2The turn-off loss of the main switch is approximately negligible (turn-off loss is less than 1/10) when the formula is satisfied:
wherein ILoad_rmsIs the effective value of the load current;
during actual circuit operation, load current detection has errors, resulting in IrError of (2), influence commutation time T2-5And ZVT on-time T5BAfter summation of the formula IrDerivation is carried out asrThe dead time of the main switch when the formula is met can be a fixed value;
simultaneous:
thus, obtaining:
wherein the value range of beta obtained by the solution of the sum is as follows:
to ensure reliable commutation of the lagging arm and Sa4Sufficient ZVS on-time, taken together, to obtain:
to ensure magnetizing current in commutation inductor LrAfter the linear discharge phase (t ═ t)4) And a resonant inductor LrBefore the linear charging phase (t ═ t)1) Equal in magnitude and opposite in direction (neglecting the change of magnetizing current in the resonant commutation stage of the hysteresis arm at the primary side):
wherein T is13T is obtained by summing up different time patterns of load1-t3Of each switching cycle, therebyDifferent; it can be seen from the sum that when the load current is 0,and T1AMinimum value, L calculated under this conditionmAccording to the condition that S is greater than 0 when any load current isa4There is a requirement for enough ZVS on-time;
will iLoadT is the sum of 01-t3The time interval of (c):
T13=T13_minformula (104)
Simultaneous:
wherein T is1A_minWhen the load current is 0, Sa4ZVS on time T1AThe value of (c).
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Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN114024439A (en) * | 2021-10-23 | 2022-02-08 | 山西大学 | Symmetrical excitation coupling inductance voltage division auxiliary commutation inverter |
TWI812530B (en) * | 2022-05-27 | 2023-08-11 | 瑞鼎科技股份有限公司 | Single inductor bipolar outputs (sibo) power converter |
Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20030174521A1 (en) * | 2002-03-08 | 2003-09-18 | Issa Batarseh | Low cost AC/DC converter with power factor correction |
CN1937382A (en) * | 2006-10-13 | 2007-03-28 | 南京航空航天大学 | Zero-voltage switch combined full-bridge three-level direct current converter |
CN1937381A (en) * | 2006-10-13 | 2007-03-28 | 南京航空航天大学 | Zero-voltage switch full-bridge direct current converter |
CN101604917A (en) * | 2009-06-24 | 2009-12-16 | 南京航空航天大学 | Adopt the Zero-voltage switch full-bridge direct current converter of passive auxiliary network |
CN106787904A (en) * | 2016-11-30 | 2017-05-31 | 辽宁石油化工大学 | The resonance polar form soft switching inverting circuit of transformer assist exchanging circuit |
CN106887947A (en) * | 2017-04-12 | 2017-06-23 | 华中科技大学 | A kind of Bridgeless power factor correction converter of high efficiency half |
CN206673827U (en) * | 2017-04-12 | 2017-11-24 | 华中科技大学 | A kind of Bridgeless power factor correction converter of high efficiency half |
-
2020
- 2020-04-16 CN CN202010301490.4A patent/CN111934576B/en active Active
Patent Citations (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20030174521A1 (en) * | 2002-03-08 | 2003-09-18 | Issa Batarseh | Low cost AC/DC converter with power factor correction |
CN1937382A (en) * | 2006-10-13 | 2007-03-28 | 南京航空航天大学 | Zero-voltage switch combined full-bridge three-level direct current converter |
CN1937381A (en) * | 2006-10-13 | 2007-03-28 | 南京航空航天大学 | Zero-voltage switch full-bridge direct current converter |
CN101604917A (en) * | 2009-06-24 | 2009-12-16 | 南京航空航天大学 | Adopt the Zero-voltage switch full-bridge direct current converter of passive auxiliary network |
CN106787904A (en) * | 2016-11-30 | 2017-05-31 | 辽宁石油化工大学 | The resonance polar form soft switching inverting circuit of transformer assist exchanging circuit |
CN106887947A (en) * | 2017-04-12 | 2017-06-23 | 华中科技大学 | A kind of Bridgeless power factor correction converter of high efficiency half |
CN206673827U (en) * | 2017-04-12 | 2017-11-24 | 华中科技大学 | A kind of Bridgeless power factor correction converter of high efficiency half |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN114024439A (en) * | 2021-10-23 | 2022-02-08 | 山西大学 | Symmetrical excitation coupling inductance voltage division auxiliary commutation inverter |
CN114024439B (en) * | 2021-10-23 | 2023-07-18 | 山西大学 | Symmetrical excitation coupling inductance voltage division auxiliary converter inverter |
TWI812530B (en) * | 2022-05-27 | 2023-08-11 | 瑞鼎科技股份有限公司 | Single inductor bipolar outputs (sibo) power converter |
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