CN111737893A - Permanent magnet synchronous motor modeling method based on predictable iron loss - Google Patents

Permanent magnet synchronous motor modeling method based on predictable iron loss Download PDF

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CN111737893A
CN111737893A CN202010439873.8A CN202010439873A CN111737893A CN 111737893 A CN111737893 A CN 111737893A CN 202010439873 A CN202010439873 A CN 202010439873A CN 111737893 A CN111737893 A CN 111737893A
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张承宁
把鑫
张硕
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Beijing Institute of Technology BIT
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Abstract

The invention provides a permanent magnet synchronous motor modeling method based on predictable iron loss, which is superior to the conventional method of the existing model, and realizes accurate calculation of output characteristics of a permanent magnet synchronous motor under different operating conditions by adopting variable inductance and adopting different values of synchronous inductance and leakage inductance under different operating conditions of the motor. The variable equivalent magnetizing iron loss resistor is adopted to calculate the iron core loss caused by the magnetizing flux linkage, and the resistor is connected in parallel at two ends of the magnetizing branch, so that the accurate calculation of the iron core loss caused by the magnetizing flux linkage in the full working domain of the motor is realized. The core loss caused by the leakage flux linkage is calculated based on the variable equivalent leakage iron loss resistor, the resistor is connected to two ends of the leakage inductor in parallel, and the accurate calculation of the core loss caused by the leakage flux linkage of the motor in the full working domain is realized.

Description

Permanent magnet synchronous motor modeling method based on predictable iron loss
Technical Field
The invention relates to the technical field of permanent magnet synchronous motor modeling, in particular to a permanent magnet synchronous motor modeling technology based on predictable iron loss.
Background
Currently, in the field of modeling of permanent magnet synchronous motors, an equivalent circuit model based on predictable iron loss is one of the more common and effective modeling methods. The equivalent iron loss resistor with fixed resistance and the inductor with fixed parameters are mostly adopted, and the iron core loss of the motor caused by a leakage flux chain can be ignored in certain modeling processes. However, the existing setting of the model also has some obvious defects, such as: 1. the equivalent iron loss resistance with the fixed resistance value is mostly determined by measurement data when the motor runs at a rated speed, however, the iron core loss of the motor is a quantity closely related to the rotating speed of the motor and the running working condition of the motor (the magnetic flux density distribution of a motor stator), the adoption of the equivalent iron loss resistance with the fixed resistance value inevitably causes a large calculation error, the iron core loss of the motor in the whole working domain cannot be effectively calculated, and then errors in the aspects of calculating the output power, the iron core loss, the efficiency, the temperature rise and the like of the motor by applying an equivalent circuit model of the permanent magnet synchronous motor are caused; 2. because the value of the inductance parameter in the equivalent circuit model is a quantity closely related to the operation condition of the motor, errors in the aspects of calculating the output torque, the output power and the like of the motor by applying the equivalent circuit model can be caused by adopting the inductance with fixed parameters; 3. when the motor operates in no-load mode, the content of the leakage magnetic chain is low, the caused core loss is low, when the motor operates in load mode, the content of the leakage magnetic chain is obviously increased, the caused core loss is high, and therefore the model accuracy is low due to the fact that the processing mode of neglecting the core loss caused by the leakage magnetic chain is adopted. Therefore, how to provide a modeling method which can not only retain the advantages of the existing modeling mode based on predictable iron loss, but also effectively overcome the defects is a technical problem to be solved in the field.
Disclosure of Invention
In view of this, the invention provides a modeling method for a permanent magnet synchronous motor based on predictable iron loss, which specifically comprises the following steps:
step one, establishing each single-phase equivalent circuit model of the permanent magnet synchronous motor under a three-phase alternating current abc coordinate system, and expressing the model as the following form:
Vn＝En+jωLsInm+ZnlIn+RnIn
Figure BDA0002503725900000011
In＝Inm+Icm
Figure BDA0002503725900000012
wherein the subscript n represents any one of three phases of abc, EnFor the phase induced electromotive force vector, LsIs a variable synchronous inductance, LnlThe phase variable leakage inductance, RsIs the internal resistance, R, of the phase windingcmIs a variable equivalent magnetizing iron loss resistance, RclIs a variable equivalent leakage iron loss resistance component, VnIs the phase terminal voltage vector, InIs the phase current vector; i isnmCurrent vector, I, flowing through the magnetizing branch for this phasecmThe current vector of the phase flowing through a variable equivalent magnetizing iron loss resistor is shown in the specification, omega is the electrical angular velocity, ZnlFor the phase variable leakage inductance LnlEquivalent variable leakage iron loss resistance RclEquivalent drain impedance formed in parallel, j represents an imaginary unit;
step two, respectively establishing d-axis and q-axis equivalent circuit models of the permanent magnet synchronous motor under a quadrature-direct axis d-q coordinate system, wherein the d-axis and q-axis equivalent circuit models are expressed in the following forms:
Figure BDA0002503725900000021
Figure BDA0002503725900000022
Figure BDA0002503725900000023
Figure BDA0002503725900000024
Figure BDA0002503725900000025
wherein, Vd、Vod、Id、Iod、Icd、LdThe voltage of the terminal of the d axis, the voltage of a magnetizing branch, the current, the magnetizing current, the iron loss current and the variable magnetizing inductance are respectively; vq、Voq、Iq、Ioq、Icq、LqThe terminal voltage, the magnetizing branch voltage, the current, the magnetizing current, the iron loss current and the variable magnetizing inductance of the q axis are respectively; l islThe leakage inductance is variable of the permanent magnet synchronous motor; zlIs variable leakage inductance LlEquivalent variable leakage iron loss resistance RclEquivalent drain impedance formed in parallel; p is a differential operator, i.e., p ═ d/dt.
Further, when each single-phase equivalent circuit model in the abc three phases operates in no-load, the resistance value of the variable equivalent magnetizing iron loss resistor can be calculated as follows:
Figure BDA0002503725900000026
when the load runs, the variable equivalent magnetizing iron loss resistance and the variable equivalent leakage iron loss resistance are calculated respectively based on the following formulas:
Vc＝En±jωLs(In-Icm)
Figure BDA0002503725900000027
Vnl＝ZnlIn
Figure BDA0002503725900000028
wherein, VcIs a variable equivalent magnetizing iron loss resistor RcmVoltage vector, V, acrossnlA variable equivalent leakage iron loss resistance RclVoltage vector, P, at both endst_coremThe total core loss caused by the magnetized flux linkage in the permanent magnet synchronous motor is calculated based on a finite element method; pt_corelThe total core loss of the permanent magnet synchronous motor caused by the magnetic flux linkage and the leakage flux linkage has Pcore＝3(Icm 2Rcm+Icl 2Rcl) The relationship (2) of (c). When the permanent magnet synchronous motor is used as a motor, the permanent magnet synchronous motor is used as a motorVcGet the "+" sign in the bullets; when the permanent magnet synchronous motor is used as a generator, a minus number is taken.
Further, for the variable equivalent magnetizing iron loss resistance and the variable equivalent leakage iron loss resistance in the d-q axis equivalent circuit model, and the total iron core loss P caused by the magnetizing flux linkage and the leakage flux linkage of the permanent magnet synchronous motorcoreCalculated based on the following formulas, respectively:
Figure BDA0002503725900000031
Figure BDA0002503725900000032
Figure BDA0002503725900000033
the method provided by the invention is superior to the conventional method of the existing model, establishes the single-phase and d-q axis equivalent circuit model of the permanent magnet synchronous motor capable of predicting the iron loss, calculates the output characteristic and the iron core loss of the motor by utilizing the variable inductance and the variable equivalent iron loss resistance, solves the problem of lower calculation precision of the existing equivalent circuit model, and realizes the beneficial effects of at least the following aspects:
1. the variable inductance is adopted, and the synchronous inductance and the leakage inductance adopt different values under different operation conditions of the motor, so that the accurate calculation of the output characteristics of the permanent magnet synchronous motor under different operation conditions is realized.
2. The invention adopts the variable equivalent magnetizing iron loss resistor to calculate the iron core loss caused by the magnetizing flux linkage, and the resistor is connected in parallel at the two ends of the magnetizing branch, thereby realizing the accurate calculation of the iron core loss caused by the magnetizing flux linkage in the full working domain of the motor.
3. The invention adopts the variable equivalent leakage iron loss resistor to calculate the iron core loss caused by the leakage flux linkage, and the resistor is connected in parallel at the two ends of the leakage inductance, thereby realizing the accurate calculation of the iron core loss caused by the leakage flux linkage in the full working domain of the motor.
Drawings
FIG. 1 is a single-phase equivalent circuit model of a permanent magnet synchronous motor under an abc coordinate system;
FIG. 2 is a d-axis equivalent circuit model of a permanent magnet synchronous motor in a d-q-axis coordinate system;
FIG. 3 is a q-axis equivalent circuit model of the permanent magnet synchronous motor in a d-q-axis coordinate system.
Detailed Description
The technical solutions of the present invention will be described clearly and completely with reference to the accompanying drawings, and it should be understood that the described embodiments are some, but not all embodiments of the present invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The invention provides a permanent magnet synchronous motor modeling method based on predictable iron loss, which specifically comprises the following steps:
step one, as shown in fig. 1, each single-phase equivalent circuit model of the permanent magnet synchronous motor is established under a three-phase alternating current abc coordinate system, and taking phase a as an example, the equivalent circuit model can be expressed as the following form:
Va＝Ea+jωLsIam+ZalIa+RaIa
Figure BDA0002503725900000041
Ia＝Iam+Icm
Figure BDA0002503725900000042
wherein, VaIs a terminal voltage vector; eaIs an induced electromotive force vector; i isaIs a phase current vector; i isamIs the current vector flowing through the magnetizing branch; i iscmIs the current vector flowing through the variable equivalent magnetizing iron loss resistor; l issThe variable synchronous inductor is a variable synchronous inductor of the permanent magnet synchronous motor; l isalVariable leakage inductance; raThe internal resistance of each phase of winding; rclIs a variable equivalent leakage iron loss resistance; rcmIs a variable equivalent magnetizing iron loss resistor; omega is the electrical angular velocity; zalThe leakage impedance equivalent to the variable leakage inductance and the variable equivalent leakage iron loss resistance connected in parallel with the variable leakage inductance, and j represents an imaginary number unit;
step two, as shown in fig. 2 and fig. 3, respectively establishing d-axis and q-axis equivalent circuit models of the permanent magnet synchronous motor under a quadrature-direct axis d-q coordinate system, wherein the d-axis and q-axis equivalent circuit models are expressed in the following forms:
Figure BDA0002503725900000043
Figure BDA0002503725900000044
Figure BDA0002503725900000045
Figure BDA0002503725900000046
Figure BDA0002503725900000047
wherein, Vd、Vod、Id、Iod、Icd、LdThe voltage of the terminal of the d axis, the voltage of a magnetizing branch, the current, the magnetizing current, the iron loss current and the variable magnetizing inductance are respectively; vq、Voq、Iq、Ioq、Icq、LqThe terminal voltage, the magnetizing branch voltage, the current, the magnetizing current, the iron loss current and the variable magnetizing inductance of the q axis are respectively; l islThe leakage inductance is variable of the permanent magnet synchronous motor; zlIs variable leakage inductance LlEquivalent variable leakage iron loss resistance RclEquivalent drain impedance formed in parallel; p is a differential operator, i.e., p ═ d/dt.
Because when permanent magnet synchronous motor is unloaded, the magnetic leakage content is very little, so under the motor unloaded operating mode, can neglect the magnetic leakage and the iron core loss that arouses by the magnetic leakage flux linkage, the resistance of variable equivalent magnetization iron loss resistance can be calculated and is:
Figure BDA0002503725900000048
when the permanent magnet synchronous motor runs under a load, the variable equivalent magnetizing iron loss resistance and the variable equivalent leakage iron loss resistance in the equivalent circuit model a are calculated respectively based on the following formulas:
Vc＝Ea±jωLs(Ia-Icm)
Figure BDA0002503725900000051
Val＝ZalIa
Figure BDA0002503725900000052
wherein, VcIs a variable equivalent magnetizing iron loss resistor RcmVoltage vector, V, acrossnlA variable equivalent leakage iron loss resistance RclVoltage vector, P, at both endst_coremThe total core loss caused by the magnetized flux linkage in the permanent magnet synchronous motor is calculated based on a finite element method; pt_corelThe total core loss of the permanent magnet synchronous motor caused by the magnetic flux linkage and the leakage flux linkage has Pcore＝3(Icm 2Rcm+Icl 2Rcl) The relationship (2) of (c). When the permanent magnet synchronous machine is used as a motor, with respect to VcGet the "+" sign in the bullets; when the permanent magnet synchronous motor is used as a generator, a minus number is taken.
For variable equivalent magnetizing iron loss resistance and variable equivalent leakage iron loss resistance in the d-q axis equivalent circuit model and total iron core loss P caused by magnetizing flux linkage and leakage flux linkage of the permanent magnet synchronous motorcoreCalculated based on the following formulas, respectively:
Figure BDA0002503725900000053
Figure BDA0002503725900000054
Figure BDA0002503725900000055
the core concept of the invention is that: in the stator iron core of the permanent magnet synchronous motor, with the increase of exciting current, the flux linkage in the iron core is increased according to a nonlinear relation, and the calculation error of an equivalent circuit model is increased by adopting fixed value inductance, so that the variable inductance is adopted in the invention. In a stator core nonlinear magnetic system of a permanent magnet synchronous motor, if winding current has a tiny disturbance, magnetic common energy in a stator core also generates a tiny variable quantity, self inductance of a certain phase of the permanent magnet synchronous motor is a second-order partial derivative of the magnetic common energy in the stator core to the phase current, mutual inductance of a certain two phases of the permanent magnet synchronous motor is a second-order partial derivative of the magnetic common energy in the stator core to the two-phase current, and then a numerical method is adopted to discretize a second-order partial differential equation. Taking the permanent magnet phase a as an example, under a certain operation condition, the phase a self-inductance LaaCan be calculated as:
Figure BDA0002503725900000056
in the formula, WcmThe magnetic energy generated by a magnetized flux linkage in a stator iron core of the permanent magnet synchronous motor is shared; i.e. iam，ibmAnd icmthe magnetic currents of three phases of the abc of the permanent magnet synchronous motor are respectively, theta is the position of the rotor, and △ i is the small disturbance of the current.
Under a certain operating condition, the leakage inductance L of the phase aalCan be calculated as:
Figure BDA0002503725900000057
in the formula, WclThe magnetic flux leakage chain is used for generating magnetic energy in the stator iron core of the permanent magnet synchronous motor; i.e. ial，iblAnd iclthe magnetic leakage currents of three phases abc of the permanent magnet synchronous motor are respectively, theta is the position of the rotor, and △ i is the small disturbance of the current.
According to the method, the inductance values of the permanent magnet synchronous motor under different operating conditions, namely under different phase currents, are calculated, and then the equation of the variable inductance is calculated by applying a numerical fitting method.
When the permanent magnet synchronous motor operates under a certain working condition, a magnetic flux density track at a certain point of a stator core is in a three-dimensional rotation mode in an electric cycle, and radial, circumferential and axial magnetic flux density components of the three-dimensional rotation magnetic flux density track can be expanded as follows according to Fourier series:
Figure BDA0002503725900000061
Figure BDA0002503725900000062
Figure BDA0002503725900000063
in the formula, Br、BθAnd BzRespectively radial, circumferential and axial components of any three-dimensional rotating magnetic flux density vector in the permanent magnet synchronous motor core material; b isrmk、BθmkAnd BzmkAre respectively Br、BθAnd BzThe amplitude of the kth harmonic of (a);
Figure BDA0002503725900000067
and
Figure BDA0002503725900000068
are respectively Br、BθAnd BzPhase angle of the k-th harmonic of (1).
Any subharmonic of radial, circumferential and axial components of the three-dimensional rotating magnetic flux density vector can form an alternating track or a standard elliptic track in a three-dimensional space. If the track of a certain harmonic of the three-dimensional rotating magnetic flux density vector is a one-dimensional alternating track, the alternating core loss corresponding to the track can be calculated as follows:
Figure BDA0002503725900000064
in the formula, PaTotal alternating iron loss of the iron core material; phaIs the alternating hysteresis loss; peaIs an alternating eddy current loss; paaLosses are added for alternation. f is the magnetic field variation frequency; b ismIs the amplitude of the alternating magnetic flux density; chaAnd h is the coefficient of the alternating hysteresis loss; ceIs the eddy current loss coefficient; caaIs the coefficient of alternating parasitic losses. The above coefficients can be obtained by fitting the iron loss data of the iron core material in the one-dimensional sinusoidal alternating magnetic field.
If the track of a certain harmonic of the three-dimensional rotating magnetic flux density vector is an elliptical track, the major axis and the minor axis of the ellipse can be respectively calculated as:
Figure BDA0002503725900000065
Figure BDA0002503725900000066
in the formula, BmskAnd BmckThe major axis B of the elliptic track formed by the k-th harmonic of each magnetic flux density component is taken as the larger valuekmajThe smaller value is the minor axis B of the elliptic orbit formed by the kth harmonic of each magnetic flux density componentkmin。
In each element of the finite element analysis method, the total hysteresis loss is the sum of hysteresis losses caused by the harmonics of each of the flux density components in each direction of the three-dimensional flux density trajectory vector, and can be calculated by the following formula:
Figure BDA0002503725900000071
in the formula, PthTo account for the total hysteresis loss of each sub-harmonic of each component of flux density in a finite element analysis unit; rBk＝Bkmin/BkmajThe axial ratio of the elliptical track formed for the kth harmonic of each magnetic flux density component; prhkThe magnetic flux density trace is circular and the amplitude is BkmajRotational hysteresis loss in time; pahkThe magnetic flux density track is sine alternating and the amplitude is BkmajAlternating hysteresis losses.
In each element of the finite element analysis method, the total eddy current loss is the sum of eddy current losses caused by the harmonics of the magnetic flux density components in each direction of the three-dimensional magnetic flux density trajectory vector, and can be calculated as:
Figure BDA0002503725900000072
in the formula, PteTo account for the total eddy current losses of the individual harmonics of the magnetic flux density components in each direction in a finite element analysis unit; ceIs the eddy current loss coefficient; k is the harmonic number; f is the magnetic field variation frequency; b iskmajThe major axis length of the elliptical trajectory formed for the kth harmonic of each magnetic flux density component; b iskminThe minor axis length of the elliptical track formed for the k-th harmonic of each magnetic flux density component.
In each element of the finite element analysis method, the total parasitic loss is the sum of the parasitic losses caused by the harmonics of the three-dimensional flux density trajectory vector components in each direction, and can be calculated as:
Figure BDA0002503725900000073
in the formula, PtaTo account for the total parasitic losses of the individual harmonics of the magnetic flux density components in each direction in a finite element analysis unit; carTo attachA loss factor; t is the electrical cycle; b isrmk、BθmkAnd BzmkAre respectively Br、BθAnd BzThe amplitude of the kth harmonic of (a).
The core loss of the entire motor of the permanent magnet synchronous motor can be calculated as:
Figure BDA0002503725900000074
in the formula, NeThe number P of the units divided in the iron core of the permanent magnet synchronous motor in the finite element analysis methodthThe total hysteresis loss of each harmonic component of the magnetic flux density in each calculation unit is calculated; pteCalculating the total eddy current loss containing each harmonic component of the magnetic flux density in each calculation unit; ptaThe total additional loss of each harmonic component of the magnetic flux density in each calculation unit is calculated.
It should be understood that, the sequence numbers of the steps in the embodiments of the present invention do not mean the execution sequence, and the execution sequence of each process should be determined by the function and the inherent logic of the process, and should not constitute any limitation on the implementation process of the embodiments of the present invention.
Although embodiments of the present invention have been shown and described, it will be appreciated by those skilled in the art that changes, modifications, substitutions and alterations can be made in these embodiments without departing from the principles and spirit of the invention, the scope of which is defined in the appended claims and their equivalents.

Claims (3)

1. A permanent magnet synchronous motor modeling method based on predictable iron loss is characterized in that: the method specifically comprises the following steps:
step one, establishing each single-phase equivalent circuit model of the permanent magnet synchronous motor under a three-phase alternating current abc coordinate system, and expressing the model as the following form:
Vn＝En+jωLsInm+ZnlIn+RnIn
Figure FDA0002503725890000011
In＝Inm+Icm
Figure FDA0002503725890000012
wherein the subscript n represents any one of three phases of abc, EnFor the phase induced electromotive force vector, LsIs a variable synchronous inductance, LnlThe phase variable leakage inductance, RsIs the internal resistance, R, of the phase windingcmIs a variable equivalent magnetizing iron loss resistance, RclIs a variable equivalent leakage iron loss resistance component, VnIs the phase terminal voltage vector, InIs the phase current vector; i isnmCurrent vector, I, flowing through the magnetizing branch for this phasecmThe current vector of the phase flowing through a variable equivalent magnetizing iron loss resistor is shown in the specification, omega is the electrical angular velocity, ZnlFor the phase variable leakage inductance LnlEquivalent variable leakage iron loss resistance RclEquivalent drain impedance formed in parallel, j represents an imaginary unit;
step two, respectively establishing d-axis and q-axis equivalent circuit models of the permanent magnet synchronous motor under a quadrature-direct axis d-q coordinate system, wherein the d-axis and q-axis equivalent circuit models are expressed in the following forms:
Figure FDA0002503725890000013
Figure FDA0002503725890000014
Figure FDA0002503725890000015
Figure FDA0002503725890000016
Figure FDA0002503725890000017
wherein, Vd、Vod、Id、Iod、Icd、LdThe voltage of the terminal of the d axis, the voltage of a magnetizing branch, the current, the magnetizing current, the iron loss current and the variable magnetizing inductance are respectively; vq、Voq、Iq、Ioq、Icq、LqThe terminal voltage, the magnetizing branch voltage, the current, the magnetizing current, the iron loss current and the variable magnetizing inductance of the q axis are respectively; l islThe leakage inductance is variable of the permanent magnet synchronous motor; zlIs variable leakage inductance LlEquivalent variable leakage iron loss resistance RclEquivalent drain impedance formed in parallel; p is a differential operator, i.e., p ═ d/dt.
2. The method of claim 1, wherein: when each single-phase equivalent circuit model in the abc three phases operates in no-load, the resistance value of the variable equivalent magnetizing iron loss resistor can be calculated as follows:
Rcm＝3Vc 2/Pt_core
when the load runs, the variable equivalent magnetizing iron loss resistance and the variable equivalent leakage iron loss resistance are calculated respectively based on the following formulas:
Vc＝En±jωLs(In-Icm)
Rcm＝3Vc 2/Pt_corem
Vnl＝ZnlIn
Figure FDA0002503725890000021
wherein, VcIs a variable equivalent magnetizing iron loss resistor RcmVoltage vector, V, acrossnlA variable equivalent leakage iron loss resistance RclVoltage vector, P, at both endst_coremThe total core loss caused by the magnetized flux linkage in the permanent magnet synchronous motor calculated based on the finite element method；Pt_corelThe total core loss of the permanent magnet synchronous motor caused by the magnetic flux linkage and the leakage flux linkage has Pcore＝3(Icm 2Rcm+Icl 2Rcl) The relationship (2) of (c). When the permanent magnet synchronous machine is used as a motor, with respect to VcGet the "+" sign in the bullets; when the permanent magnet synchronous motor is used as a generator, a minus number is taken.
3. The method of claim 1, wherein: for variable equivalent magnetizing iron loss resistance and variable equivalent leakage iron loss resistance in the d-q axis equivalent circuit model and total iron core loss P caused by magnetizing flux linkage and leakage flux linkage of the permanent magnet synchronous motorcoreCalculated based on the following formulas, respectively:
Figure FDA0002503725890000022
Figure FDA0002503725890000023
Figure FDA0002503725890000024
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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112511058A (en) * 2020-12-16 2021-03-16 哈尔滨工业大学 Method for rapidly, accurately and comprehensively calculating characteristics of servo motor influenced by temperature
CN113111556A (en) * 2021-04-15 2021-07-13 浙江大学 Induction motor iron loss analysis method considering influence of magnetic field and stress in hypergravity environment

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JP2010072773A (en) * 2008-09-17 2010-04-02 Meidensha Corp Method for analyzing in-magnet eddy current loss for permanent magnet type motor
US20160091569A1 (en) * 2014-09-26 2016-03-31 Skf Magnetic Mechatronics Method and system for determining core losses in a permanent magnet synchronous motor
CN107493051A (en) * 2017-09-18 2017-12-19 南京理工大学 A kind of ultrahigh speed direct torque control method for permanent magnetic synchronous electric machine based on core loss
CN110442944A (en) * 2019-07-29 2019-11-12 江苏大学 A kind of modeling method of the change leakage field permanent magnet synchronous motor based on multi-state operation

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2010072773A (en) * 2008-09-17 2010-04-02 Meidensha Corp Method for analyzing in-magnet eddy current loss for permanent magnet type motor
US20160091569A1 (en) * 2014-09-26 2016-03-31 Skf Magnetic Mechatronics Method and system for determining core losses in a permanent magnet synchronous motor
CN107493051A (en) * 2017-09-18 2017-12-19 南京理工大学 A kind of ultrahigh speed direct torque control method for permanent magnetic synchronous electric machine based on core loss
CN110442944A (en) * 2019-07-29 2019-11-12 江苏大学 A kind of modeling method of the change leakage field permanent magnet synchronous motor based on multi-state operation

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112511058A (en) * 2020-12-16 2021-03-16 哈尔滨工业大学 Method for rapidly, accurately and comprehensively calculating characteristics of servo motor influenced by temperature
CN113111556A (en) * 2021-04-15 2021-07-13 浙江大学 Induction motor iron loss analysis method considering influence of magnetic field and stress in hypergravity environment

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