CN111628274A

CN111628274A - Antenna device and electronic apparatus

Info

Publication number: CN111628274A
Application number: CN201910614002.2A
Authority: CN
Inventors: 王岩; 李建铭; 王吉康; 尤佳庆; 王汉阳
Original assignee: Huawei Technologies Co Ltd
Current assignee: Huawei Technologies Co Ltd
Priority date: 2019-02-27
Filing date: 2019-07-08
Publication date: 2020-09-04
Anticipated expiration: 2039-07-08
Also published as: CN111628274B

Abstract

According to the antenna scheme provided by the application, the excitation unit is erected above the floor of the electronic equipment (such as a mobile phone) and is fed, so that the floor is effectively excited to generate radiation. Therefore, the radiation capability of the floor is not influenced by the clearance between the display screen and the floor, and the antenna scheme provided by the application is applicable to the electronic equipment with the drastically reduced antenna space, namely a full-screen electronic equipment. In addition, the floor is used as one of the main radiation apertures of electronic equipment (such as a mobile phone), and the performance of the antenna can be obviously improved by exciting the floor to generate radiation.

Description

Antenna device and electronic apparatus

Technical Field

The present invention relates to the field of antenna technology, and in particular, to an antenna device applied to an electronic device.

Background

In order to provide more comfortable visual perception for users, the Industrial Design (ID) of full-screen has become a design trend of portable electronic devices such as mobile phones. Full screen means a very large screen fraction (typically above 90%). The frame width of full-face screen reduces by a wide margin, needs to carry out the new layout to cell-phone internal components, like leading camera, receiver, fingerprint identification ware, antenna etc.. Especially for antenna designs, the headroom is reduced and the antenna space is further compressed. The size, bandwidth and efficiency of the antenna are related and affected with each other, the size (space) of the antenna is reduced, and the efficiency-bandwidth product (efficiency-bandwidth product) of the antenna is reduced. Thus, full screen ID presents a significant challenge to the antenna design of a cell phone.

Commonly used antenna designs in electronic devices such as mobile phones may be planar inverted f (planar inverted f) antennas, inverted f (inverted f) antennas, monopole (monopole) antennas, T-shaped antennas, loop antennas, and the like. These antenna designs, which have an antenna length at least one quarter to one half of the low frequency wavelength, have high antenna space requirements.

How to design an antenna in a limited space and meet the performance requirements of the antenna is a research direction in the industry.

Disclosure of Invention

The embodiment of the invention provides an antenna device and electronic equipment, which can effectively stimulate a floor to generate radiation, and can be applied to electronic equipment with sharply reduced antenna space, namely a full-face screen, because the radiation capability of the floor is not influenced by the clearance between a display screen and the floor.

In a first aspect, the present application provides an antenna apparatus, as shown in fig. 2A-2F, which may include: a floor 15 of the electronic device, an excitation unit 23. Wherein:

the floor 15 includes opposing first (e.g., side 21-1) and second (e.g., side 21-5) edges, and opposing third (e.g., bottom 21-7) and fourth (e.g., top 21-3) edges.

The excitation unit 23 may have a first branch 29-2 and two second branches (29-1, 29-3). The second branch 29-1 and the second branch 29-3 can be connected to both ends of the first branch 29-2, respectively. The end of the second branch 29-1 far from the first branch 29-2 is connected with the floor 15, and the end of the second branch 29-3 far from the first branch 29-2 is connected with the floor 15. The second branch 29-1 and the second branch 29-3 may be used to erect the first branch 29-2 on the floor 15, with a void formed between the first branch 29-2 and the floor 15.

The energizing unit 23 may be erected on the floor 15 adjacent a first edge of the floor 15. Here, the proximity may mean that the distance between the excitation unit 23 and the first side is less than a certain distance, such as 4 mm. The specific distance is not limited to 4mm, but may also be 3 mm, 2mm, 1 mm, or the like. At this time, a distance L1 from the exciting unit 23 to the first side is smaller than a distance L2 from the exciting unit 23 to the second side.

The difference between the distance p1 from the first end of the excitation element 23 to the third side and the distance p2 from the second end of the excitation element 23 to the fourth side is less than a first value, such as 15 mm. The first value is not limited to 15 mm, and may be 12 mm, 20 mm, or the like. The first end is the end of the excitation unit 23 near the third side, and the second end is the end of the excitation unit 23 near the fourth side.

The exciter unit 23 may be provided with a feed port 27, and the signal source is located in the feed port 27. A first slit may be formed on the first branch 29-2 of the excitation unit 23, and a first capacitor may be connected in series between two first branches on two sides of the first slit. The first capacitance can be used to achieve a co-current distributed over the excitation unit 23.

It can be seen that the antenna device provided in the first aspect effectively excites the floor to generate radiation by erecting an excitation unit above the floor of an electronic device (such as a mobile phone) and feeding the excitation unit. Therefore, the radiation capability of the floor is not influenced by the clearance between the display screen and the floor, and the antenna scheme provided by the application is applicable to the electronic equipment with the drastically reduced antenna space, namely a full-screen electronic equipment. In addition, the floor is used as one of the main radiation apertures of electronic equipment (such as a mobile phone), and the performance of the antenna can be obviously improved by exciting the floor to generate radiation.

In connection with the first aspect, in some embodiments, the excitation unit 23 may be parallel to the first edge (e.g., side 21-1) of the floor panel 15, or the excitation unit 23 and the first edge (e.g., side 21-1) of the floor panel 15 may exhibit a small included angle therebetween, i.e., may be approximately parallel therebetween. The smaller included angle may be less than the first angle, such as 5 °. The first angle is not limited to 5 °, and may be an angle of 3 °, 7 °, or the like. At this time, the angle α between the excitation unit 23 and the first side is smaller than the angle β between the excitation unit 23 and the third side. The excitation unit 23 may be parallel to the first side of the floor 15, i.e. the angle α is equal to 0 °, in which case the excitation unit 23 may excite the floor 15 to generate a stronger current at the first side, and the excitation unit 23 may excite the floor 15 to generate resonance more easily.

In connection with the first aspect, in some embodiments, the first slit may be opened in the middle of the first branch 29-2, so that the same-direction current on the excitation unit 23 is stronger, and the floor 15 is easier to excite to generate radiation. The first capacitance may be a lumped capacitance or a distributed capacitance (e.g., a distributed capacitance formed by slits opened in the excitation unit 23).

In conjunction with the first aspect, in some embodiments, the feeding form at the feeding port 27 may include, but is not limited to, the following two ways:

in one implementation, as shown in fig. 2E, the feeding port 27 may be specifically disposed on the first branch 29-2, and may be specifically implemented by forming a slot 1 on the first branch 29-2. The first branch 29-2 is divided into two parts (29-2-A, 29-2-B) by the gap 1, and a signal source can be connected in series between the first branch 29-2-A and the first branch 29-2-B.

In another implementation manner, as shown in fig. 2F, the feeding port 27 may be specifically disposed on the second branch 29-1 or the second branch 29-3, and may be specifically implemented by opening a slot 2 on the second branch. The inductor L connected in series in fig. 2F can be used to implement impedance matching, and a matching network integrated at the feed end will be described later, which is not described herein again.

In connection with the first aspect, in some embodiments, first branch 29-2 may be a horizontal branch, parallel to floor 15. Optionally, the second branch 29-1 and the second branch 29-3 may be vertical branches perpendicular to the floor 15, and are used for suspending the first branch 29-2 on the floor 15.

In combination with the first aspect, in some embodiments, the excitation unit 23 may be parallel to the first side, where the included angle α is 0 and the included angle β is 90 °, where the excitation unit 23 is easier to excite the floor 15 to generate radiation.

In connection with the first aspect, in some embodiments, the excitation unit 23 may be erected at the first edge of the floor, where L1 is equal to 0, where the excitation unit 23 is more likely to excite the floor 15 to generate radiation. That is, the closer the excitation unit 23 is to the first side, the easier it is to excite the floor 15 to generate radiation.

In connection with the first aspect, in some embodiments, the distance p1 and the distance p2 may be equal, both equal to (Lg-Le)/2. In this case, the excitation unit 23 may be erected in the middle of the floor panel adjacent to the first side, and the excitation unit 23 may excite the floor panel 15 to resonate more easily.

In combination with the first aspect, in some embodiments, the matching network integrated at the feed port may include a capacitor C and an inductor L, the capacitor C being connected in series with the feed port, the inductor L being connected in parallel with the feed port. The capacitor C may be referred to as a second capacitor and the inductor L may be referred to as a first inductor.

With reference to the first aspect, in some embodiments, the antenna apparatus provided by the present application may further implement a dual band, or a wide band, or multiple bands, and may be implemented by a matching network or adding more magnetic loops. The description is as follows.

1. Dual-band antenna scheme based on matching network

In order to realize dual-band matching, the matching network may be an LC parallel circuit (composed of parallel L2 and C2) connected in series after the capacitor C1 is connected in series, and finally an inductor L2 is connected in parallel. That is, the matching network integrated at the feed port may include: the series capacitor C1, the LC parallel circuit and the inductor L2 are connected in series, the capacitor C1 and the LC parallel circuit are connected in series at the feed port at a time, and the inductor L2 is connected in parallel at the feed port. The capacitor C1 may be referred to as a third capacitor, the inductor L2 may be referred to as a second inductor, the capacitor C2 in the LC parallel circuit may be referred to as a fourth capacitor, and the inductor L2 in the LC parallel circuit may be referred to as a third inductor. Optionally, the dual bands may be a low band (e.g. at 800 MHz) and a GPS L1 band (at 1.5 GHz), and the configuration of the matching network for the dual bands may be as follows: c1 ═ 1pF, L1 ═ 6nH, C2 ═ 2.2pF, and L2 ═ 4.5 nH.

2. Dual-band or broadband or multi-band antenna scheme based on multi-magnetic-ring

To implement a dual band or a wide band, a parasitic element (also called a parasitic magnetic ring) may be installed on the floor 15. That is, the antenna device provided by the present application may further include a parasitic element. On the floor 15, the parasitic element, like the excitation element 23, may be mounted near a first edge (e.g., side 21-1) of the floor. Here, nearby may mean that the distance between the parasitic element and the first edge of the floor (e.g., side 21-1) is less than a certain distance (e.g., 4 millimeters). At this time, a distance L3 from the parasitic element to the first side of the floor is smaller than a distance L4 from the parasitic element to the second side of the floor.

When the excitation unit 23 excites the floor 15 to generate radiation, the floor 15 is coupled with the parasitic unit to generate radiation, so that dual-band radiation can be realized.

In some embodiments, the structure of the parasitic element and the structure of the excitation element 23 may be the same. The parasitic element may have a third branch and two fourth branches. The third branch is similar to the first branch 29-2 in the excitation unit 23, and the fourth branch is similar to the second branches 29-1 and 29-3 in the excitation unit 23. Like the structure of the excitation unit 23, the two fourth branches of the parasitic unit may be connected to both ends of the third branch, respectively. The end of the fourth branch far away from the first branch is connected with the floor 15. The two fourth knuckles can be used to mount the third knuckle on the floor 15 so that the third knuckle forms a void with the floor 15. As with the excitation unit 23, the parasitic element may have a capacitance in series therewith. This capacitance may be referred to as a fifth capacitance. In order to connect the fifth capacitor in series, a gap may be formed in the third branch, and the fifth capacitor may be connected in series between two portions of the third branch on both sides of the gap. This gap may be referred to as a second gap.

The parasitic magnetic loop is not limited to the same structure as the exciting unit 23, and the parasitic element may be other antennas, such as a bracket antenna, a suspension antenna, etc., in order to realize multiple frequency bands or wide frequency bands. The support antenna may include an IFA antenna, an ILA antenna, or the like.

In combination with the first aspect, in some embodiments, to implement MIMO, the antenna apparatus provided by the present application may include a plurality of antenna elements, and one antenna element may have one excitation element 23, or may have one excitation element 23 and M (M is a positive integer) parasitic elements. The plurality of antenna elements may be disposed adjacent to respective sides of the floor 15. That is, in one antenna unit, the excitation unit 23 is erected adjacent to the edge of the floor, and the parasitic unit is also erected adjacent to the edge of the floor.

In a second aspect, the present application provides an electronic device comprising a non-metallic back cover, and an antenna arrangement as described in the first aspect above.

Drawings

In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings required to be used in the embodiments of the present application will be described below.

FIG. 1 is a schematic diagram of an internal environment of an electronic device;

fig. 2A is a schematic diagram of an overall model of an antenna device provided in the present application;

FIG. 2B is a plan view of the antenna structure provided herein in the X-Z plane;

fig. 2C is a detailed view of a loop excitation element in the antenna structure provided herein;

fig. 2D is a schematic diagram of a feeding pattern at a feeding port in an antenna structure provided by the present application;

fig. 2E is a schematic diagram of one feed form of the antenna arrangement provided herein;

fig. 2F is a schematic diagram of another feeding form of the antenna device provided in the present application;

fig. 3A is a schematic diagram illustrating an S11 simulation of the antenna structure provided in the present application under several matching networks;

fig. 3B is a simulation diagram of the efficiency of the antenna structure provided in the present application under several matching networks;

fig. 3C is a schematic diagram of a matching network of the antenna structure provided herein;

fig. 4A is a simulated vector current profile for the antenna structure provided herein;

fig. 4B is a front view of a three-position radiation pattern for the antenna structure provided by the present application operating at 900 MHz;

fig. 4C is a top view of a three-position radiation pattern for the antenna structure provided by the present application operating at 900 MHz;

fig. 5A is a schematic view of an application of the antenna structure provided in the present application in a complete machine model;

fig. 5B is a schematic diagram illustrating simulation S11 of the antenna structure provided in the present application at several p values;

fig. 5C is a schematic diagram illustrating an efficiency simulation of the antenna structure provided in the present application at several p-values;

fig. 6A is a schematic diagram illustrating simulation S11 of the antenna structure provided in the present application at several Le values;

fig. 6B is a schematic diagram illustrating an efficiency simulation of the antenna structure provided in the present application at several Le values;

fig. 7A is a schematic diagram illustrating simulation S11 of the antenna structure provided in the present application at several values of h;

fig. 7B is a schematic diagram illustrating efficiency simulation of the antenna structure provided in the present application at several values of h;

fig. 8A is a schematic diagram illustrating simulation S11 of the antenna structure provided in the present application at several w values;

fig. 8B is a schematic diagram illustrating an efficiency simulation of the antenna structure provided herein at several w values;

fig. 9A is a schematic diagram of a simulation S11 of the antenna structure provided in the present application when d is 4mm and w is 2 mm;

fig. 9B is a schematic diagram illustrating an efficiency simulation of the antenna structure provided in the present application when d is 0mm and w is 2 mm;

fig. 10A is a schematic diagram of an S11 simulation of the antenna structure provided in the present application at several p values;

fig. 10B is a schematic diagram illustrating an efficiency simulation of the antenna structure provided in the present application at several p-values;

fig. 10C is an antenna radiation pattern for the antenna structure provided herein at several p-values;

fig. 11A is a schematic diagram illustrating simulation S11 of the antenna structure provided in the present application at several Lg values;

fig. 11B is a schematic diagram illustrating efficiency simulation of the antenna structure provided in the present application at several Lg values;

fig. 11C is a schematic diagram illustrating simulation S11 of the antenna structure provided in the present application at several Wg values;

fig. 11D is a schematic diagram illustrating efficiency simulation of the antenna structure provided herein at several Wg values;

fig. 12A is a schematic diagram of a matching network implementing dual bands;

fig. 12B is a simulation diagram of S11 when the antenna structure provided by the present application is configured with the matching network shown in fig. 12A;

FIG. 13A is a schematic diagram of a multi-band or wide-band antenna structure based on multiple magnetic rings;

FIG. 13B is a bird's eye view of the antenna structure shown in FIG. 13A;

fig. 13C is a simulation diagram of S11 of the antenna structure shown in fig. 13A under two matching network parameters;

FIG. 13D is a graph of a simulation of the efficiency of the antenna structure shown in FIG. 13A under two matching network parameters;

FIG. 14 is a schematic diagram of another multi-band or wide-band antenna structure based on multiple magnetic loops;

FIG. 15A is a schematic view of the layout of the excitation unit and the parasitic unit on the floor according to the present application;

FIG. 15B is a schematic diagram of another arrangement of the excitation unit and the parasitic unit on the floor in the present application;

fig. 16 is a schematic layout of active and parasitic elements on a floor to implement MIMO;

fig. 17A shows a schematic diagram of an antenna arrangement with an IFA as a parasitic element;

fig. 17B shows a schematic diagram of an antenna arrangement with ILA as a parasitic element;

fig. 17C shows a schematic diagram of an antenna arrangement with a levitated antenna as the parasitic element.

Detailed Description

The embodiments of the present invention will be described below with reference to the drawings.

The technical scheme provided by the application is suitable for the electronic equipment adopting one or more of the following communication technologies: bluetooth (BT) communication technology, Global Positioning System (GPS) communication technology, wireless fidelity (Wi-Fi) communication technology, global system for mobile communications (GSM) communication technology, Wideband Code Division Multiple Access (WCDMA) communication technology, Long Term Evolution (LTE) communication technology, 5G communication technology, SUB-6G communication technology, future other communication technologies, and the like. In the present application, the electronic device may be a mobile phone, a tablet computer, a Personal Digital Assistant (PDA), or the like.

Fig. 1 illustrates an internal environment of an electronic device on which the antenna design provided herein is based. As shown in fig. 1, the electronic device 10 may include: display screen 11, printed circuit board PCB13, floor 15, bezel 17, and back cover 19. The display screen 11, the printed circuit board PCB13, the floor 15 and the rear cover 19 may be arranged in different layers, respectively, which layers may be parallel to each other, the plane of each layer may be referred to as the X-Z plane, and the direction perpendicular to the X-Z plane is the Y direction. That is, the display screen 11, the printed circuit board PCB13, the floor 15, and the rear cover 19 may be layered in the Y direction.

The printed circuit board PCB13 may be an FR-4 dielectric board, a Rogers (Rogers) dielectric board, a hybrid Rogers and FR-4 dielectric board, or the like. Here, FR-4 is a code for a grade of flame-resistant material, Rogers dielectric plate a high-frequency plate.

The rear cover 19 is a rear cover made of a non-conductive material, such as a non-metal rear cover, e.g., a glass rear cover, a plastic rear cover, etc.

Wherein the floor 15 is grounded, may be disposed between the PCB13 and the rear cover 19. The floor 15 may also be referred to as a PCB backplane. Specifically, the floor 15 may be a layer of metal etched on the surface of the PCB13, and the layer of metal may be attached to a metal bezel (not shown) through a series of metal clips, and integrated with the metal bezel. The floor 15 may be used for grounding of electronic components carried on the printed circuit board PCB 13. In particular, the electronic components carried on the printed circuit board PCB13 may be grounded by wiring to the floor 15 to prevent electrical shock to a user or damage to equipment.

The frame 17 may be disposed around the edge of the floor 15, and may cover the printed circuit board PCB13 between the rear cover 19 and the display screen 11 and the floor 15 from the side, so as to achieve the purpose of dust-proof and water-proof. The frame 17 may be a metal frame or a non-metal frame. The bezel 17 may include: a bezel at the top of electronic device 10 (which may be referred to as a top bezel) 27-3, a bezel at the bottom of electronic device 10 (which may be referred to as a bottom bezel) 27-7, and bezels at the sides of electronic device 10 (which may be referred to as side bezels) 27-1 and 27-5. The top of the electronic device 10 may be provided with a front-facing camera (not shown), an earpiece (not shown), a proximity light sensor (not shown), an ambient light sensor (not shown), and the like. The bottom of the electronic device 10 may be provided with a USB charging interface (not shown), a microphone (not shown), and the like. The electronic device 10 may be provided with a volume adjustment key (not shown), a power key (not shown) on the side.

Fig. 1 schematically shows only the respective portions included in the electronic apparatus 10, and the actual shape, actual size, and actual configuration of the respective portions are not limited to fig. 1. The display screen 11 of the electronic device 10 may be a large-sized display screen, and the screen proportion may reach more than 90%.

Based on the internal environment of the electronic device shown in fig. 1, the present application will provide a magnetic loop feed based floor radiation antenna scheme. The antenna scheme provided by the application effectively excites the floor 15 to generate radiation by erecting an excitation unit above the floor 15 and feeding the excitation unit. Thus, the antenna scheme provided by the application is applicable to electronic equipment with drastically reduced antenna space, such as a full-screen ID, because the radiation capability of the floor 15 is not affected by the clearance between the display screen 11 and the floor 15. In addition, the floor 15 serves as one of the main radiation apertures of the electronic device 10, and exciting the floor 15 to generate radiation can significantly improve antenna performance.

Fig. 2A-2C illustrate an antenna arrangement provided herein. Fig. 2A is a schematic diagram of an overall model of the antenna device, fig. 2B is a plan view of the antenna structure in an X-Z plane, and fig. 2C is a detailed view of a ring-shaped excitation unit in the antenna structure. As shown in fig. 2A to 2C, the antenna device may include a ground plane (15), and an excitation unit (23). Wherein:

the floor 15 may have opposing side edges 21-1 and 21-5, and opposing top and bottom edges 21-3 and 21-7. The edges of the floor 15 are next to the edges of the edge frame 17, respectively. Specifically, the side 21-1 is adjacent to the side border 17-1, the top 21-3 is adjacent to the top border 17-3, the side 21-5 is adjacent to the side border 17-5, and the bottom 21-7 is adjacent to the bottom border 17-7. Alternatively, the floor panel 15 may be rectangular, the side edges 21-1 and 21-5 may be two opposing long edges, and the top edge 21-3 and bottom edge 21-7 may be two opposing short edges.

The energizing unit 23 may be mounted on the floor 15 adjacent to an edge of the floor 15. This edge may be referred to as a first edge of the floor 15. Here, the proximity may mean that the distance between the excitation unit 23 and the first edge of the floor 15 is less than a certain distance, such as 4 mm. The smaller the distance between the excitation unit 23 and the first edge of the floor 15, the easier it is to excite the floor 15 to generate radiation, and the following content will be analyzed, which will not be described herein again. Alternatively, the first edge of the floor panel 15 may be the long edge of the floor panel 15.

The excitation unit 23 may be parallel to the first edge of the floor panel 15 or the excitation unit 23 and the first edge of the floor panel 15 may also present a smaller angle therebetween. I.e. the excitation unit 23 and the first side may be parallel or nearly parallel. The smaller included angle may be less than the first angle, such as 5 °. The first angle is not limited to 5 °, and may be an angle of 3 °, 7 °, or the like.

The excitation unit 23 may have a first branch 29-2 and two second branches (29-1, 29-3). The second branch 29-1 and the second branch 29-3 can be connected to both ends of the first branch 29-2, respectively. The ends of first branch 29-2 may include an end 22-1 proximate top edge 21-3 and an end 22-3 proximate bottom edge 21-7. The end of the second branch 29-1 far from the first branch 29-2 is connected with the floor 15, and the end of the second branch 29-3 far from the first branch 29-2 is connected with the floor 15. Second branch 29-1 and second branch 29-3 may be used to mount first branch 29-2 on floor 15, with a void formed between first branch 29-2 and floor 15, i.e., first branch 29-2 does not contact floor 15. Alternatively, first branch 29-2 may be a horizontal branch, parallel to floor 15. Optionally, the second branch 29-1 and the second branch 29-3 may be vertical branches perpendicular to the floor 15, and are used for suspending the first branch 29-2 on the floor 15.

Fig. 2B and 2C also exemplarily show the size of the floor 15, the size of the energizing unit 23, and the position of the energizing unit 23 on the floor 15. Specifically, the length Lg of the floor panel 15 may be 140 mm, and the width Wg of the floor panel 15 may be 70 mm. Here, the width Wg of the floor panel 15 is the length of the short side (21-3, 21-7 in FIG. 2B) of the floor panel 15, and the length Lg of the floor panel 15 is the length of the long side (21-1, 21-5 in FIG. 2B) of the floor panel 15. The length Le of the excitation unit 23 may be 40 mm and the height h of the excitation unit 23 may be 4 mm. Here, the length Le of the excitation unit 23 is the length of the first branch 29-2, and the height h of the excitation unit 23 is the length of the second branch. The distance w between the excitation unit 23 and the first edge (e.g., side edge 21-1) of the floor 15 may be 2mm, and the distance p between the end 22-3 of the excitation unit 23 and the bottom edge 21-7 of the floor 15 may be 50 mm. Without being limited to the figures, Lg, Wg, Le, h, w, p may be other values, and the influence of the values on the antenna performance will be described in detail later.

As shown in fig. 2D, the excitation unit 23 may be provided with a feeding port 27, and the signal source is located in the feeding port 27. In one implementation, as shown in fig. 2E, the feeding port 27 may be specifically disposed on the first branch 29-2, and may be specifically implemented by forming a slot 1 on the first branch 29-2. The first branch 29-2 is divided into two parts (29-2-A, 29-2-B) by the gap 1, and a signal source can be connected in series between the first branch 29-2-A and the first branch 29-2-B. In another implementation manner, as shown in fig. 2F, the feeding port 27 may be specifically disposed on the second branch 29-1 or the second branch 29-3, and may be specifically implemented by opening a slot 2 on the second branch. The inductor L connected in series in fig. 2F can be used to implement impedance matching, and a matching network integrated at the feed end will be described later, which is not described herein again.

As shown in FIG. 2D, a capacitor C1 may be connected in series with the excitation unit 23, and the capacitor C1 may be referred to as a first capacitor. The first capacitance can be used to achieve a co-current distributed over the excitation unit 23. In order to connect the first capacitors in series, as shown in fig. 2E and 2F, the first branch 29-2 may be formed with a slit 1. The slot 1 may divide the first branch 29-2 into two parts (29-2-a, 29-2-B), and a first capacitance may be connected in series between the first branch 29-2-a and the first branch 29-2-B. The slot 1 in which the first capacitance is located may be referred to as the first slot. Alternatively, the first slit may be opened in the middle of the first branch 29-2, so that the same-direction current on the excitation unit 23 is stronger, and the floor 15 is easier to excite to generate radiation. The first capacitance may be a lumped capacitance or a distributed capacitance (e.g., a distributed capacitance formed by slits opened in the excitation unit 23).

In one embodiment, as shown in fig. 2E, the excitation unit 23 may be formed with only one slot, such as slot 1, and the first capacitor and the signal source may form a series circuit in the slot 1, and then the series circuit may be integrally connected in series between two first branches (i.e., the first branch 29-2-a and the first branch 29-2-B) on two sides of the slot 1. That is to say, the slot where the first capacitor is located and the slot where the feed port is located may be the same slot, but not limited thereto, the slot where the first capacitor is located and the slot where the feed port is located may also be two different slots.

A matching network may be integrated at the feeding port 27, and the matching network may be used to adjust (by adjusting antenna radiation coefficient, impedance, etc.) the frequency range covered by the antenna device provided by the present application. The matching network may include various structures capable of impedance matching, such as an impedance transformation line or a lumped element network. The lumped elements may comprise elements such as capacitors or inductors. Specifically, the input impedance of the antenna can be adjusted by changing the line width of the impedance transformation line and changing the electrical characteristic parameters (such as capacitance value, inductance value and the like) of the components in the lumped element network, so as to realize impedance matching.

The matching principle of the excitation unit 23 is explained below. When no matching element is used (i.e. no matching network) the input impedance is mainly in the inductive region in the desired frequency band (e.g. 690MHz-960 MHz). At this time, the simulation of S11 of the antenna device may be as shown by a curve a1 in fig. 3A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B1 and c1 in fig. 3B. When only a capacitor C (e.g., C ═ 1pF) is connected in series at the feed port, the input impedance behaves in the desired frequency band (e.g., 690MHz-2700 MHz): in the low frequency band (690 MHz-960MHz for example) is located in the capacitive region, and in the high frequency band (1700 MHz-2700MHz for example) is located in the inductive region. The simulation of S11 of the antenna device at this time can be shown as curve a2 in fig. 3A, and the system efficiency and radiation efficiency of the antenna device can be shown as curves B2 and c2 in fig. 3B. As shown in fig. 3C, when the matching network at the feed port is formed by first connecting the capacitor C (e.g., C ═ 1pF) in series and then connecting the inductor L (e.g., L ═ 4.5nH) in parallel, the simulation S11 of the antenna device can be shown as the curve a3 in fig. 3A, and the system efficiency and the radiation efficiency of the antenna device can be shown as the curves B3 and C3 in fig. 3B.

It can be seen that curve a1 has no resonance, curve a2 has a shallower resonance, and curve a3 has a deeper resonance. In addition, the antenna efficiency represented by the curve b3 is also significantly better than the antenna efficiency represented by the curves b1 and b 2. That is, the exciting unit 23 can be well impedance-matched by connecting the capacitor C in series and then connecting the inductor L in parallel at the feeding port, so that the exciting unit 23 can effectively excite the floor 15 to generate radiation. That is, the matching network integrated at the feeding port may include a capacitor C connected in series with the feeding port and an inductor L connected in parallel with the feeding port. The capacitor C may be referred to as a second capacitor and the inductor L may be referred to as a first inductor.

The operation principle of the antenna device provided by the present application is described below by taking a 900MHz operating frequency band as an example. The matching network integrated at the feed port is assumed to be a capacitor of 1pF connected in series and an inductor of 4.5nH connected in parallel. The current distribution of the antenna device provided by the present application at 900MHz may be as shown in fig. 4A, the excitation unit 23 is distributed with the equidirectional current 31, and the equidirectional current 31 distributed on the annular excitation unit 23 may be equivalent to a magnetic current, so the excitation unit 23 may be referred to as a "magnetic ring". The co-current 31 excites the ground plate 15 to generate a longitudinal current 33, thereby exciting the ground plate 15 to resonate and exciting the ground plate 15 to radiate. Fig. 4B and 4C are a front view and a bird's eye view of a three-dimensional radiation pattern simulated when the antenna device provided by the present application operates at 900MHz, respectively. As shown in fig. 4B-4C, the three-dimensional radiation pattern is shaped like the radiation pattern of an 1/2 wavelength dipole, and is primarily tilted to one side because the current of the floor 15 is primarily concentrated on the side 21-1 of the floor 15.

It can be seen that by erecting the excitation unit 23 above the floor 15, feeding the excitation unit 23, and providing a suitable matching network at the feeding port, the floor 15 can be effectively excited to generate radiation. Therefore, the requirement on the antenna space can be reduced, the electronic equipment with the sharply reduced antenna space, such as the full-screen ID, is suitable, and the antenna performance can be remarkably improved.

The following describes an application of the antenna design scheme provided by the present application in an actual complete machine model.

For example, the distance p between the excitation unit 23 and the bottom edge 21-7 of the floor 15 shown in fig. 5A is an important parameter of the excitation unit 23 in an actual complete machine model. Assuming Lg is 140 mm, Wg is 70 mm, Le is 40 mm, and h is 4mm, taking the GPSL5 operating band as an example, fig. 5B and 5C show S11 simulation and antenna efficiency of the antenna device when p is two different values. When p is 65 mm, the simulation of S11 of the antenna device may be as shown by curve a1 in fig. 5B, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B1 and C1 in fig. 5C. When p is 45 mm, the simulation of S11 of the antenna device may be as shown by curve a2 in fig. 5C, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves b2 and C2 in fig. 5C.

It can be seen that, in both cases of p being 65 mm and p being 45 mm, the resonance position and the resonance depth simulated by S11 are substantially the same, and the peak value of the system efficiency is about-6 dB. In fact, the system efficiency when p is 65 mm is slightly higher than that when p is 45 mm, and the reason will be analyzed in the following. In addition, the upper hemispherical proportion when p is 65 mm is about 45.18%, and the upper hemispherical proportion when p is 65 mm is about 55.88%. The higher the upper hemisphere fraction, the stronger the radiation in the longitudinal direction of the antenna, i.e. in the Z direction.

The distance p between the excitation unit 23 and the bottom edge 21-1 of the floor 15, the size of the excitation unit 23, and the distance w between the excitation unit 23 and the side edge 21-1 of the floor 15 are not limited, but may also be important parameters of the antenna device provided by the present application in an actual whole machine model. The values of these parameters affect the antenna performance. The effect of a certain parameter on the antenna performance will be described in detail below on the basis of a single variable (i.e. a single parameter changes, and other parameters do not change).

(1) Influence of the size of the exciter unit 23 on the antenna performance

The length Le of the excitation unit 23 is increased, the resonance of the antenna is at a lower frequency band, and the resonance depth becomes deeper; the length Le of the excitation unit 23 is reduced, the resonance of the antenna is at a higher frequency band, and the resonance depth becomes shallow.

For example, taking a 900MHz working frequency band as an example, fig. 6A and 6B show S11 simulation and antenna efficiency of the antenna device when Le is several different values. When Le is 35 mm, the simulation of S11 of the antenna device may be as shown by curve a1 in fig. 6A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B1 and c1 in fig. 6B. When Le is 40 mm, the simulation of S11 of the antenna device may be as shown by curve a2 in fig. 6A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B2 and c2 in fig. 6B. When Le is 45 mm, the simulation of S11 of the antenna device may be as shown by curve a3 in fig. 6A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B3 and c3 in fig. 6B.

Of the antenna performance under these different Le, when Le is 45 mm, the resonant frequency of the antenna device is the lowest (closest to 850MHz), and the resonant depth is the deepest (reaching-8 dB). When Le is 35 mm, the resonant frequency of the antenna device is the highest (closest to 1GHz) and the resonant depth is the shallowest (about-4 dB). It can be seen that as the length Le becomes shorter from 45 mm to 40 mm, 35 mm, the resonance of the antenna moves to a high frequency and the resonance depth becomes shallower.

In the case where the resonance becomes shallow due to the reduction in the length Le of the excitation unit 23, the resonance depth can be reduced by reducing the parallel inductance. For example, as shown in fig. 6A and 6B, a curve a4 represents an S11 simulation of the antenna device when Le is 35 mm and L is 3.5nH, and curves B4 and c4 represent system efficiency and radiation efficiency of the antenna device when Le is 35 mm and L is 3.5 nH. It can be seen that reducing the shunt inductance L from L-4.5 nH to L-3.5 nH can draw the resonance depth from-4 dB to-6 dB.

The height h of the excitation unit 23 is reduced, and the resonance of the antenna is shifted to a high frequency, so that the resonance depth becomes shallow.

For example, taking a 900MHz operating frequency band as an example, fig. 7A and 7B show S11 simulation and antenna efficiency of the antenna device when h is several different values. Here, when h is 4mm, the simulation of S11 of the antenna device may be as shown by a curve a1 in fig. 7A, and the system efficiency and the radiation efficiency of the antenna device may be as shown by curves B1 and c1 in fig. 7B. When h is 3 mm, the simulation of S11 of the antenna device may be as shown by curve a2 in fig. 7A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B2 and c2 in fig. 7B. When h is 2mm, the simulation of S11 of the antenna device may be as shown by curve a3 in fig. 7A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B3 and c3 in fig. 7B.

Of the antenna performance at several different h, when h is 4mm, the resonant frequency of the antenna device is the lowest (about 900MHz), and the resonant depth is the deepest (up to-7 dB). When h is 2mm, the resonant frequency of the antenna device is the highest (close to 1GHz), and the resonant depth is the shallowest (about-4 dB). It can be seen that as the height h is reduced from 4mm to 3 mm, 2mm, the resonance of the antenna moves to a high frequency and the depth of resonance becomes shallower.

In the case where the resonance shifts to a high frequency due to the decrease in the height h of the excitation unit 23, the resonance can be returned to a low frequency by increasing the length Le. For example, as shown in fig. 7A and 7B, a curve a4 represents an S11 simulation of the antenna device when h is 2mm and Le is (40+10) mm, and curves B4 and c4 represent system efficiency and radiation efficiency of the antenna device when h is 2mm and Le is (40+10) mm. It can be seen that lengthening the exciter element 23 from 40 mm to (40+10) mm results in a return of the antenna resonance to low frequencies (900MHz), where the peak efficiency of the antenna is only reduced by about 0.6dB, without significant degradation, the antenna bandwidth is also slightly reduced, and the antenna performance is not very sensitive to the height of the exciter element 23.

(2) Influence of the position of the exciter unit 23 on the floor 15 on the antenna performance

The position of the excitation unit 23 can be represented by two dimensional parameters: the distance w between the excitation unit 23 and a first edge of the floor, e.g. side edge 21-1, and the distance p between the excitation unit 23 and a third edge of the floor, e.g. bottom edge 21-7. The first and third edges may be two edges of the floor 15 that are connected, and they may be perpendicular to each other.

2-A. Effect of distance w on antenna Performance

The smaller the distance w, the closer the energizing unit 23 is to the side 21-1 of the floor 15. When w is 0mm, it means that the excitation unit 23 is erected at the side 21-1. The greater the distance w, the closer the excitation unit 23 is to the middle of the floor 15 in the Y direction.

The distance w is reduced, so that the resonance of the antenna can move to a low frequency, and the resonance depth becomes deeper; by increasing the distance w, the resonance of the antenna can be shifted to a high frequency, and the resonance depth becomes shallow. This is because the intrinsic current of the floor 15 is mainly concentrated on the floor 15 due to the edge-seeking effect, and when the excitation unit 23 moves towards the middle of the floor 15 (i.e. w becomes larger), the intrinsic current on the excitation unit 23 is difficult to couple with the intrinsic current of the floor 15, so that the floor 15 is difficult to be excited to generate radiation.

For example, taking a 900MHz operating frequency band as an example, fig. 8A and 8B show S11 simulation and antenna efficiency of the antenna device when w is several different values. D in fig. 8A and 8B is 0mm (d represents the height of the metal frame), which means that no metal frame is provided at the side edge of the floor panel 15, i.e., the frame 27 is a non-metal frame. Here, when w is 0mm, the simulation of S11 of the antenna device may be as shown by a curve a1 in fig. 8A, and the system efficiency and the radiation efficiency of the antenna device may be as shown by curves B1 and c1 in fig. 8B. When w is 2mm, the simulation at S11 of the antenna device may be as shown by curve a2 in fig. 8A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B2 and c2 in fig. 8B. When w is 4mm, the simulation at S11 of the antenna device may be as shown by curve a3 in fig. 8A, and the system efficiency and radiation efficiency of the antenna device may be as shown by curves B3 and c3 in fig. 8B.

Of the antenna performance at several different w values, w is 0mm, the resonant frequency of the antenna device is the lowest (about 900MHz), and the resonant depth is the deepest (up to-6 dB). when w is 4mm, the resonant frequency of the antenna device is the highest (approximately 1GHz), and the resonant depth is the shallowest (approximately-3 dB). It can be seen that as the height w increases from 0mm to 2mm, 4mm, the resonance of the antenna shifts to high frequencies and the depth of resonance becomes shallower, the peak efficiency and bandwidth of the system also decreases significantly.

In addition, the metal frame (d is not equal to 0) disposed on the side of the floor 15 can make the resonance of the antenna move to high frequency, and the resonance depth becomes shallow. This is because the metal frame may correspond to the extension of the floor 15, and the intrinsic current of the floor 15 is mainly concentrated on the metal frame due to the edge-seeking effect, which corresponds to the outward expansion of the floor 15. At this time, the system efficiency peak and the bandwidth of the antenna are also reduced.

For example, taking the 900MHz operating band as an example, as shown in fig. 9A and 9B, when d is 4mm (d represents the height of the metal frame) and w is 2mm, the simulation of S11 of the antenna device may be as shown by a curve a3 in fig. 9A, and the system efficiency and the radiation efficiency of the antenna device may be as shown by curves B3 and c3 in fig. 9B. When d is 0mm (d represents the height of the metal frame) and w is 2mm, the simulation of S11 of the antenna device can be shown as curve a2 in fig. 9A, and the system efficiency and radiation efficiency of the antenna device can be shown as curves B2 and c2 in fig. 9B. It can be seen that in the case where w is 2mm, the antenna performance is significantly weaker when d is 4mm than when d is 0mm, the resonance shifts to a high frequency, the resonance depth becomes shallow, and the peak value and bandwidth of the system efficiency are significantly reduced.

2-B. Effect of distance p on antenna Performance

The smaller the distance p, the closer the excitation unit 23 is to the bottom edge 21-7 of the floor 15. The greater the distance p, the further away the excitation unit 23 is from the bottom edge 21-7 of the floor 15 in the Z-direction.

Assuming that the length Lg of the floor panel 15 is 140 mm and the length of the excitation unit 23 is 40 mm, when p is 50 mm, when p is (Lg-Le)/2, it can be said that the excitation unit 23 is disposed in the middle of the floor panel 15 in the Z direction. Increasing p (e.g., 50 mm +10 mm) or decreasing p (e.g., 50 mm-10 mm) may cause the excitation unit 23 to be offset from the middle of the floor 15, which may result in shallower resonant depths of the antenna, smaller system efficiency peaks, and smaller bandwidths. This is because, in the middle of the floor 15 in the Z direction, the intrinsic current of the floor 15 is strongest, and the intrinsic current at a position far from the middle is weakened. When the excitation unit 23 is far away from the middle of the floor 15 in the Z direction, the coupling between the cocurrent on the excitation unit 23 and the intrinsic current on the floor 15 becomes weak, and the floor 15 is not easily excited to generate radiation, resulting in poor antenna performance.

For example, taking a 900MHz operating band as an example, fig. 10A and 10B show S11 simulation and antenna efficiency of the antenna device when p is several different values. It can be seen that when p is 50 mm, the resonant depth of the antenna is deepest, and the peak value and bandwidth of the system efficiency are the largest; when p is 40 mm, 60 mm, 30 mm, and 70 mm, the resonance depth of the antenna becomes shallow, and the peak value and bandwidth of the system efficiency become small.

In addition, the closer the excitation unit 23 is to the bottom edge 21-7 of the floor 15 (i.e., the smaller p), the larger the upper hemispherical proportion of the antenna radiation pattern, the stronger the radiation in the longitudinal direction of the antenna, i.e., the stronger the radiation in the Z direction. The further away the excitation unit 23 is from the bottom edge 21-7 of the floor 15 (i.e. the larger p), the smaller the upper hemispherical proportion of the antenna radiation pattern, the weaker the radiation in the longitudinal direction of the antenna, i.e. in the Z-direction.

For example, taking 900MHz working frequency band as an example, fig. 10C shows the antenna radiation pattern of the antenna device when p is several different values. As shown in fig. 10C, when p is 50 mm, the upper hemisphere proportion is 50%; when p is 40 mm, the upper hemisphere proportion is 51.9%; when p is 30 mm, the upper hemisphere proportion is 53.7%; when p is 60 mm, the upper hemisphere proportion is 48.2%; when p is 70 mm, the upper hemisphere proportion is 46.4%.

(3) Influence of the size of the floor 15 on the antenna performance

The size of the floor 15 can be represented by two dimensional parameters: the length Lg of the floor 15, and the width Wg of the floor 15.

3-A. Effect of Length Lg on antenna Performance

Assuming that Wg is 70 mm, as shown in fig. 11A and 11B, when Lg is lengthened or shortened by 12 mm based on 140 mm, the resonance position of the antenna is substantially unchanged because the width of the floor 15 is large and the characteristic impedance of the floor 15 is small. The resonance of the antenna device provided by the present application is more affected by the length Le of the exciting unit 23 because the characteristic impedance of the exciting unit 23 is larger.

3-B. Effect of Width Wg on antenna Performance

As shown in fig. 11C and 11D, when Wg is widened by 10 mm or narrowed by 10 mm based on 70 mm, the resonance position of the antenna is substantially unchanged. However, when the panel 15 becomes narrower (i.e., Wg decreases), the resonance of the antenna becomes deeper, and the peak value and bandwidth of the system efficiency become larger. This is because the narrower the floor 15, the more concentrated the intrinsic current of the floor 15 is on the floor 15, so that the stronger the coupling between the excitation unit 23, which is erected in the vicinity of the floor 5, and the floor 15, the easier it is to excite the floor 15 to generate radiation.

The dimensions of the excitation unit 23 and the floor 15 may be determined according to the dimensions of the whole model to which the antenna device provided in the present application is actually applied. In order to realize that the excitation unit 23 effectively excites the floor 15 to radiate, the relative position relationship between the excitation unit 23 and the floor 15 can be as follows:

1. the excitation unit 23 may be parallel to the first edge of the floor panel 15 (e.g., side 21-1), or the excitation unit 23 and the first edge of the floor panel 15 (e.g., side 21-1) may be at a relatively small angle, i.e., may be approximately parallel. The smaller included angle may be less than the first angle, such as 5 °. The first angle is not limited to 5 °, and may be an angle of 3 °, 7 °, or the like. At this time, the angle α between the excitation unit 23 and the first side is smaller than the angle β between the excitation unit 23 and the third side. In particular, when the included angle α is 0 and the included angle β is 90 °, the excitation unit 23 is parallel to the first side, and the excitation unit 23 can excite the floor panel 15 to generate radiation more easily.

2. The energizing unit 23 can be mounted on the floor 15 adjacent a first edge (e.g., side 21-1) of the floor 15. Here, the proximity may mean that the distance between the excitation unit 23 and the first side is less than a certain distance, such as 4 mm. The specific distance is not limited to 4mm, but may also be 3 mm, 2mm, 1 mm, or the like. At this time, the distance L1 from the exciting element 23 to the first side is smaller than the distance L2 from the exciting element 23 to the second side (e.g., side 21-5). The first and second edges are opposite edges of the floor panel 15. L1 may be equal to 0, when the excitation unit 23 is erected at the first edge of the floor, the excitation unit 23 is easier to excite the floor 15 to generate radiation. That is, the closer the excitation unit 23 is to the first side, the easier it is to excite the floor 15 to generate radiation.

It will be appreciated that when the excitation unit 23 is parallel to the first side, the distance between the excitation unit 23 and the first side is unique; when the excitation unit 23 and the first side are approximately parallel, the distance between the excitation unit 23 and the first side may be the distance from a certain point (e.g., a center point) on the excitation unit 23 to the first side, or an average value of a plurality of distances from each of a plurality of points on the excitation unit 23 to the first side.

3. The difference between the distance p1 from the first end of the excitation unit 23 to the third edge (e.g., bottom edge 21-7) of the floor 15 and the distance p2 from the second end of the excitation unit 23 to the fourth edge (e.g., top edge 21-3) of the floor 15 is less than a first value, such as 15 millimeters. The first value is not limited to 15 mm, and may be 12 mm, 20 mm, or the like. The third and fourth sides are the other two opposing sides of the floor panel 15, except for the first (e.g., side 21-1) and second (e.g., side 21-5) opposing sides. The first end is the end of the excitation unit 23 near the third side, and the second end is the end of the excitation unit 23 near the fourth side. When the excitation unit 23 is parallel to the first side, p1+ p2+ Le ═ Lg; when the excitation unit 23 and the first side are not parallel with an angle α (α ≠ 0) therebetween, p1+ p2+ Le > Lg. When the difference between p1 and p2 is 0, the excitation unit 23 can excite the floor 15 to generate resonance more easily, and p1 and p2 are equal and are both equal to (Lg-Le)/2.

The foregoing describes an antenna design operating in a single frequency band, which may be the 900MHz low frequency band, GPS L5 or GPS L1, among others. The antenna device provided by the application can also realize double frequency bands or wide frequency bands or multiple frequency bands, and can be realized by a matching network or adding more magnetic rings. The description is as follows.

1. Dual-band antenna scheme based on matching network

As shown in fig. 12A, in order to implement dual-band matching, the matching network may be an LC parallel circuit (formed by parallel L2 and C2) connected in series after the capacitor C1 is connected in series, and finally connected in parallel with the inductor L2. That is, the matching network integrated at the feed port may include: the series capacitor C1, the LC parallel circuit and the inductor L2 are connected in series, the capacitor C1 and the LC parallel circuit are connected in series at the feed port at a time, and the inductor L2 is connected in parallel at the feed port. The capacitor C1 may be referred to as a third capacitor, the inductor L2 may be referred to as a second inductor, the capacitor C2 in the LC parallel circuit may be referred to as a fourth capacitor, and the inductor L2 in the LC parallel circuit may be referred to as a third inductor. Optionally, the dual bands may be a low band (e.g. at 800 MHz) and a GPS L1 band (at 1.5 GHz), and the configuration of the matching network for the dual bands may be as follows: c1 ═ 1pF, L1 ═ 6nH, C2 ═ 2.2pF, and L2 ═ 4.5 nH. By providing the dual-band matching network at the feeding port, the antenna performance of the antenna device provided by the present application can be simulated as shown in fig. 12B, which is S11 of the antenna device shown in fig. 12B.

As shown in fig. 13A-13B, a parasitic element (also called a parasitic magnetic ring) may be installed on the floor 15 to implement a dual band or a wide band. That is, the antenna device provided by the present application may further include a parasitic element. On the floor 15, the parasitic element, like the excitation element 23, may be mounted near a first edge (e.g., side 21-1) of the floor. Here, nearby may mean that the distance between the parasitic element and the first edge of the floor (e.g., side 21-1) is less than a certain distance (e.g., 4 millimeters). At this time, a distance L3 from the parasitic element to the first side of the floor is smaller than a distance L4 from the parasitic element to the second side of the floor.

The structure of the parasitic element and the structure of the exciting element 23 may be the same. The parasitic element may have a third branch and two fourth branches. The third branch is similar to the first branch 29-2 in the excitation unit 23, and the fourth branch is similar to the second branches 29-1 and 29-3 in the excitation unit 23. Like the structure of the excitation unit 23, the two fourth branches of the parasitic unit may be connected to both ends of the third branch, respectively. The end of the fourth branch far away from the first branch is connected with the floor 15. The two fourth knuckles can be used to mount the third knuckle on the floor 15 so that the third knuckle forms a void with the floor 15. As with the excitation unit 23, the parasitic element may have a capacitance in series therewith. This capacitance may be referred to as a fifth capacitance. In order to connect the fifth capacitor in series, a gap may be formed in the third branch, and the fifth capacitor may be connected in series between two portions of the third branch on both sides of the gap. This gap may be referred to as a second gap.

Fig. 13C and 13D show antenna performance under two matching network parameters. When the series capacitance C of the excitation unit 23 is 2.0pF, the parallel inductance L is 3.5nH, the length of the excitation unit 23 is 20 mm, and the length of the parasitic unit is 50 mm, the simulation of S11 of the antenna device may be as shown by a curve a1 in fig. 13C, and the simulation of the efficiency of the antenna device may be as shown by curves b1 and C1 in fig. 13D. It can be seen that the antenna device operates in dual frequency bands: the antenna efficiency of the 800MHz frequency band and the 960MHz frequency band are basically consistent and have no efficiency pits. When the exciting unit 23 has a series capacitance C of 3.0pF, a shunt inductance L of 3.5nH, a length of the exciting unit 23 of 12 mm, and a length of the parasitic unit of 60 mm, the S11 simulation of the antenna device may be as shown by a curve a2 in fig. 13C, and the efficiency simulation of the antenna device may be as shown by curves b2 and C2 in fig. 13D. It can be seen that the antenna device operates in dual frequency bands: the antenna efficiency of the 800MHz frequency band and the 1.1GHz frequency band are basically consistent and the two frequency bands have no efficiency pits.

To cover more frequency bands or wider frequency bands, more parasitic magnetic loops may be provided on the floor 15, as shown in fig. 14. Specifically, three resonant frequency points can be realized by using two parasitic magnetic rings; by using three parasitic magnetic rings, four resonant frequency points can be realized; n (N is a positive integer) parasitic magnetic rings are used, and N +1 resonant frequency points can be realized. Each parasitic magnetic ring is provided with a series capacitor.

Not limited to being disposed near the side edges of the floor 15 as shown in FIG. 15A, the excitation unit 23 and the parasitic element, or only the excitation unit 23, may be disposed near the bottom edge 21-7 or the top edge 21-3 of the floor 15, as shown in FIG. 15B. That is, the first edge of the floor panel may be a side edge of the floor panel 15, such as side edge 21-1 or side edge 21-5, or may be a bottom edge 21-7 or top edge 21-3 of the floor panel 15.

In order to implement Multiple Input Multiple Output (MIMO), the antenna device provided in the present application may include a plurality of antenna elements, and one antenna element may have one excitation element 23, or may have one excitation element 23 and M (M is a positive integer) parasitic elements. The plurality of antenna elements may be disposed adjacent to respective sides of the floor 15. For example, as shown in fig. 16, 4 antenna elements may be provided near 4 of the floor 15, respectively, in which case 4 × 4MIMO may be realized. If two antenna elements in fig. 16 are removed, 2 × 2MIMO can be achieved. If some more antenna elements are added near the floor in fig. 16, higher-order MIMO can be realized.

The parasitic magnetic loop is not limited to the same structure as the exciting unit 23, and the parasitic element may be other antennas, such as a bracket antenna, a suspension antenna, etc., in order to realize multiple frequency bands or wide frequency bands. The bracket antenna may include an Inverted F Antenna (IFA), an Inverted L Antenna (ILA), and the like. Fig. 17A illustrates a parasitic IFA antenna, fig. 17B illustrates a parasitic ILA antenna, and fig. 17C illustrates a parasitic floating metal antenna (FLM). The parasitic suspended metal antenna may be affixed or printed on the inside or outside surface of a non-metallic back cover (e.g., a glass back cover).

In some embodiments, the IFA antenna may also act as an excitation unit, i.e. feed the IFA, and may couple energy into a magnetic loop of the same structure as the excitation unit 23. The magnetic loop may then couple energy to the floor, exciting the floor to produce radiation. At this time, the matching network of the IFA antenna as the excitation unit may be a capacitor connected in series with 1pF, and then connected in parallel with a 4nH inductor; a capacitor of 0.8pF can be connected in series on the magnetic ring as a parasitic element.

Similarly, the ILA may also act as an excitation unit, i.e., feed the ILA, and the ILA antenna may couple energy to a magnetic loop of the same configuration as excitation unit 23. The magnetic loop may then couple energy to the floor, exciting the floor to produce radiation.

The capacitance and inductance mentioned in the above contents of the present application can be realized by lumped elements, and also can be realized by distributed elements.

The above description is only for the specific embodiments of the present application, but the scope of the present application is not limited thereto, and any person skilled in the art can easily conceive of the changes or substitutions within the technical scope of the present application, and shall be covered by the scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.

Claims

1. An antenna arrangement of an electronic device, the antenna arrangement comprising: a floor of the electronic device, an excitation unit, wherein:

the excitation unit is provided with a first branch and two second branches, and the two second branches are respectively connected to two ends of the first branch; one end of the second branch knot, which is far away from the first branch knot, is connected with the floor; the two second branches are used for erecting the first branches on the floor, and gaps are formed between the first branches and the floor;

the floor panel comprises first and second opposite sides and third and fourth opposite sides, wherein L1 is smaller than L2, L1 is the distance from the excitation unit to the first side of the floor panel, and L2 is the distance from the excitation unit to the second side of the floor panel; the difference between p1 and p2 is smaller than a first value, the p1 is the distance from the first end of the excitation unit to the third edge, and the p2 is the distance from the second end of the excitation unit to the fourth edge of the floor; the first end is one end of the excitation unit close to the third edge, and the second end is one end of the excitation unit close to the fourth edge;

a feed port is arranged on the excitation unit; a first gap is formed in the first branch, and a first capacitor is connected between two parts of the first branches on two sides of the first gap in series.

2. The antenna device of claim 1, wherein L1 is equal to 0.

3. The antenna device according to any of claims 1-2, wherein the p1 is equal to the p 2.

4. The antenna device according to any of claims 1-3, characterized in that the first slot opens in the middle of the first stub.

5. The antenna device according to any of claims 1-4, characterized in that the feeding port is arranged in particular on the first stub or the feeding port is arranged in particular on the second stub.

6. The antenna device according to any of claims 1-5, wherein a matching network is integrated at the feed port, the matching network comprising a second capacitance and a first inductance, the second capacitance being connected in series with the feed port, the first inductance being connected in parallel with the feed port.

7. The antenna device according to any of claims 1-5, wherein a matching network is integrated at the feed port, the matching network comprising a third capacitor, a first parallel circuit and a second inductor, the first parallel circuit comprising a fourth capacitor and a third inductor connected in parallel, the third capacitor, the first parallel circuit in turn being connected in series to the feed port, the second inductor being connected in parallel to the feed port.

8. The antenna device according to any of claims 1-7, characterized in that the antenna device further comprises: one or more parasitic elements mounted on the floor, the parasitic elements having a distance L3 to the first edge that is less than a distance L4 to the second edge.

9. The antenna device of claim 8, wherein the parasitic element has a third branch and two fourth branches, the two fourth branches being connected to two ends of the third branch, respectively; one end of the fourth branch knot, which is far away from the third branch knot, is connected with the floor; the two fourth branches are used for erecting the third branches on the floor, and gaps are formed between the third branches and the floor; and a second gap is formed in the third branch, and a fifth capacitor is connected in series between two third branch parts on two sides of the second gap.

10. The antenna device of claim 8, wherein the parasitic element comprises any of: the antenna comprises an inverted-F antenna, an inverted-L antenna and a suspended metal antenna arranged on the inner surface or the outer surface of a non-metal rear cover of the electronic equipment.

11. The antenna arrangement according to any of claims 1-10, wherein the first capacitance is a lumped capacitance or a distributed capacitance.

12. An antenna arrangement of an electronic device, the antenna arrangement comprising: a floor of the electronic device and a plurality of antenna units disposed on the floor; wherein the antenna element has an excitation element, or the antenna element has an excitation element and M parasitic elements, M being a positive integer; wherein:

a feed port is arranged on the excitation unit; a first gap is formed in the first branch, and a first capacitor is connected in series between two parts of the first branches on two sides of the first gap;

the parasitic element is erected on the floor, and the distance L3 from the parasitic element to the first side is smaller than the distance L4 from the parasitic element to the second side.

13. The antenna apparatus of claim 12, wherein L1 is equal to 0.

14. The antenna device according to any of claims 12-13, wherein the p1 is equal to the p 2.

15. The antenna device according to any of claims 12-14, characterized in that the first slot opens in the middle of the first stub.

16. The antenna device according to any of claims 12-15, characterized in that the feeding port is arranged in particular on the first stub or the feeding port is arranged in particular on the second stub.

17. The antenna device according to any of claims 12-16, wherein a matching network is integrated at the feed port, the matching network comprising a second capacitance and a first inductance, the second capacitance being connected in series with the feed port, the first inductance being connected in parallel with the feed port.

18. The antenna device according to any of claims 12-16, wherein a matching network is integrated at the feed port, the matching network comprising a third capacitor, a first parallel circuit and a second inductor, the first parallel circuit comprising a fourth capacitor and a third inductor connected in parallel, the third capacitor, the first parallel circuit in turn being connected in series to the feed port, the second inductor being connected in parallel to the feed port.

19. The antenna device according to any of claims 12-18, wherein the parasitic element has a third branch and two fourth branches, the two fourth branches being connected at respective ends of the third branch; one end of the fourth branch knot, which is far away from the third branch knot, is connected with the floor; the two fourth branches are used for erecting the third branches on the floor, and gaps are formed between the third branches and the floor; and a second gap is formed in the third branch, and a fifth capacitor is connected in series between two third branch parts on two sides of the second gap.

20. The antenna device according to any of claims 12-18, characterized in that the parasitic element comprises any of: the antenna comprises an inverted-F antenna, an inverted-L antenna and a suspended metal antenna arranged on the inner surface or the outer surface of a non-metal rear cover of the electronic equipment.

21. An electronic device, wherein a rear cover of the electronic device is made of an insulating material, the electronic device comprising: the antenna device of any one of claims 1 to 20.