CN111525222A - Miniaturized coplanar waveguide equal-division power divider based on crossed slow-wave transmission line - Google Patents
Miniaturized coplanar waveguide equal-division power divider based on crossed slow-wave transmission line Download PDFInfo
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- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
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- H01P5/12—Coupling devices having more than two ports
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Abstract
The invention relates to a miniaturized coplanar waveguide equal power divider based on a crossed slow wave transmission line, and belongs to the field of radio frequency microwave circuits. Aiming at the problems of large size and poor isolation of the traditional equal-division power divider, an interdigital capacitor and a snake-shaped inductor structure are adopted, a cross slow-wave transmission line is designed, so that the transmission line per unit length has larger distributed series inductance and parallel capacitance compared with the common coplanar waveguide transmission line, and the cross slow-wave transmission line is used for replacing the traditional quarter-wavelength transmission line, so that the size of the power divider is reduced and is only 35.7% of that of the traditional power divider. Meanwhile, an isolation resistor of 100 omega is added between two output ports of the equal-division power divider to increase the isolation degree of the power divider. The problem of traditional equant power divider oversize and isolation are relatively poor among the prior art is solved.
Description
Technical Field
The invention belongs to the field of radio frequency microwave circuits, and relates to a miniaturized coplanar waveguide equal-division power divider based on a crossed slow-wave transmission line.
Background
The power divider is an important component of a radio frequency device, can equally or unequally divide a single signal into two or even a plurality of signals, and is widely applied to various radio frequency front ends and balanced systems. With the ultra-high speed development of modern communication technology in recent decades, miniaturized devices become an important development direction in the future, and therefore, the research on the miniaturized power divider has important significance. The traditional Wilkinson equal-division power divider is mainly composed of two quarter-wavelength transmission lines of 70.7 omega, and the physical length of the quarter-wavelength transmission lines is related to the wavelength, so that when the working frequency point of the quarter-wavelength transmission line is positioned in a low-frequency band, the size of the power divider is overlarge.
The traditional Wilkinson equal division power divider is realized by a microstrip line. Because the characteristic impedance range of the coplanar waveguide transmission line is wider than that of the microstrip line, the central conduction band and the ground plane are in the same plane, and good grounding is easy to realize when active and passive devices are connected in series or in parallel, the coplanar waveguide transmission line has the advantages of simple manufacture, small radiation loss and the like, and is widely applied to the design of various microwave integrated circuits. When the coplanar waveguide circuit is used for designing the power divider, after two sections of coplanar waveguide transmission lines are connected to the same signal input port, the distance of central conduction bands of two output ports of the coplanar waveguide power divider is often longer, and the middle parts of the two output ports are separated by a ground plane, so that an isolation resistor is not easy to add. Therefore, the equal-division power divider in the form of the coplanar waveguide circuit is mostly designed as a T-type power divider, and the T-type power divider is usually poor in isolation degree due to the fact that the T-type power divider does not have isolation resistance.
Disclosure of Invention
In view of the above, the present invention provides a miniaturized coplanar waveguide equal power splitter based on a cross slow wave transmission line. Aiming at the problems of large size and poor isolation of the traditional equal-division power divider, an interdigital capacitor and a snake-shaped inductor structure are adopted, a cross slow-wave transmission line is designed, so that the transmission line per unit length has larger distributed series inductance and parallel capacitance compared with the common coplanar waveguide transmission line, and the cross slow-wave transmission line is used for replacing the traditional quarter-wavelength transmission line, so that the size of the power divider is reduced and is only 35.7% of that of the traditional power divider. Meanwhile, an isolation resistor of 100 omega is added between two output ports of the equal-division power divider to increase the isolation degree of the power divider. The problem of traditional equant power divider oversize and isolation are relatively poor among the prior art is solved.
In order to achieve the purpose, the invention provides the following technical scheme:
a miniaturized coplanar waveguide equal power divider based on a crossed slow wave transmission line comprises,
the metal conduction band is arranged on the front surface and the back surface of the dielectric substrate (1);
the metal conduction band on the front surface of the dielectric substrate (1) comprises a signal input port transmission line (2), a signal first output port transmission line (3) and a signal second output port transmission line (4), two crossed slow-wave transmission lines (5) respectively positioned between the first input port transmission line (2) and the first output port transmission line (3) and between the first input port transmission line (2) and the second output port transmission line (4), 4 metal through holes I (6) which are in common ground plane with the first output port transmission line (3) and the second output port transmission line (4), and a patch isolation resistor (8); in addition, the cross slow wave transmission line (5) comprises 4 metal through holes II (7);
the front surface of the dielectric substrate (1) is provided with a patch isolation resistor (8), the upper side and the lower side of the back surface of the patch isolation resistor (8) corresponding to the position are respectively provided with a horizontal rectangular metal patch (9), each horizontal rectangular metal patch (9) is provided with 2 metal through holes I (6), and the left side and the right side of the patch isolation resistor (8) are communicated with a ground plane; in addition, in the cross slow wave transmission line (5), 2 vertical rectangular metal patches (10) are positioned on the back surface of the cross slow wave transmission line (5) close to the corners, and each vertical rectangular metal patch (10) is provided with 2 metal through holes II (7) respectively so as to enable the ground surfaces on the upper side and the lower side of the central conduction band of the cross slow wave transmission line (5) to be communicated.
Optionally, the crossed slow-wave transmission lines (5) are arranged symmetrically up and down;
each section of crossed slow-wave transmission line (5) comprises a section of long corner coplanar waveguide transmission line (11), a section of short coplanar waveguide transmission line (12), a section of short coplanar waveguide transmission line (13), two sections of folded thin transmission lines (14), 4 interdigital capacitor structures (15) and 2 metal through holes II (7) on the front surface; the back of the crossed slow-wave transmission line comprises 1 vertical rectangular metal patch (10), and 2 metal through holes II (7) are formed in the vertical rectangular metal patch (10).
Optionally, two corners of the long-corner coplanar waveguide transmission line (11) are respectively provided with a 90-degree corner.
Optionally, the two sections of the folded thin transmission lines (14) are respectively arranged on the left side and the right side;
two ends of the left folding thin transmission line (14) are respectively connected with a central conduction band of the shorter coplanar waveguide transmission line (12) and a central conduction band of the long corner coplanar waveguide transmission line (11);
the right folded thin transmission line (14) is respectively connected with the central conduction band of the shorter coplanar waveguide transmission line (12) and the central conduction band of the short coplanar waveguide transmission line (13);
two ends of the interdigital capacitor (15) are respectively connected with the folded thin transmission line (14) and the ground plane.
Optionally, the cross-type slow-wave transmission line (5) has a characteristic impedance of 70.7 Ω and a phase shift of 90 °, and can be equivalent to a quarter-wavelength transmission line;
the left ends of the two crossed slow wave transmission lines (5) are connected to one end of the signal input port transmission line (2), and the right ends of the two crossed slow wave transmission lines are respectively connected with the signal first output port transmission line (3) and the signal second output port transmission line (4);
ports at the signal input port transmission line (2), the first output port transmission line (3) and the second output port transmission line (4) are respectively used as a port 1, a port 2 and a port 3 of the power divider;
a port 1 of the power divider is used for inputting radio frequency signals, and a port 2 and a port 3 are used for outputting the radio frequency signals;
the impedances of the three ports of the power divider are all 50 omega, and the corresponding signal input port transmission line (2), the signal first output port transmission line (3) and the signal second output port transmission line (4) are all coplanar waveguide transmission lines with 50 omega characteristic impedance;
the patch isolation resistor (8) is used for isolating signal transmission between the signal first output port transmission line (3) and the signal second output port transmission line (4) and preventing crosstalk of reflected signals between the two signal output ports caused by impedance mismatching of the two signal output ports and an external port, and the resistance value of the patch isolation resistor (8) is 100 omega;
the medium substrate is provided with 8 metal through holes, the medium substrate comprises 4 metal through holes II (7) used for connecting an upper ground plane and a lower ground plane of two sections of crossed slow wave transmission lines (5), and the first output port transmission line 3 and the second output port transmission line 4 share the 4 metal through holes I (6) on the ground plane; the first metal through hole (6) and the second metal through hole (7) are used for connecting the front side and the back side of the dielectric substrate (1) with the metal conducting belts.
Optionally, the characteristic impedances of the long-corner coplanar waveguide transmission line (11), the short coplanar waveguide transmission line (12) and the short coplanar waveguide transmission line (13) are all 70.7 Ω, and the phase shifts are θ1、θ2And theta3(ii) a The two sections of the folded thin transmission lines (14) are equivalent to series inductors LxThe 4 interdigital capacitor structures 15 are equivalent to 4 parallel capacitors CXThe ground plane above and below the interdigital capacitor 15 is equivalent to a series inductor Lx1(ii) a Satisfy Lx＝2Lx1(ii) a The circuit diagram is formed by combining three sections of transmission lines and two X-type unit circuits; wherein the first phase shift is theta1Is a corner coplanar waveguide transmission line (11) and the second phase shift is theta2Is a shorter coplanar waveguide transmission line (12) and the third phase shift is theta3Is a short coplanar waveguide transmission line (13); the phase shift of X-type cross section in the cross type unit circuit is thetax；
The total phase shift theta of the crossed slow wave transmission line is obtained as follows:
θ＝θ1+θ2+θ3+2θx
wherein:
where ω represents the angular frequency of operation;
solving the characteristic impedance of the cross slow-wave transmission line by using Bloch impedance, wherein a transfer matrix of an equivalent circuit of the cross slow-wave transmission line is as follows:
wherein:
obtaining the characteristic impedance Z of the cross slow-wave transmission linelineComprises the following steps:
the invention has the beneficial effects that: the coplanar waveguide circuit form is combined with the cross slow wave transmission line, and the designed cross slow wave transmission line is used for replacing a quarter-wavelength transmission line in the traditional equal-division power divider, so that the size of the power divider is reduced. When the coplanar waveguide power divider is designed, because the distance between the central conduction bands of the two output ports of the coplanar waveguide power divider is often far and the ground planes are separated from each other in the middle, the coplanar waveguide power divider is not easy to add isolation resistors, the coplanar waveguide power divider is often designed as a T-shaped power divider, and the isolation degree of the T-shaped power divider is often poor because the T-shaped power divider does not have the isolation resistors. According to the invention, the isolation resistor of 100 omega is added between the two output ports of the power divider, so that the isolation effect of the power divider is improved. The size of the designed power divider is obviously reduced compared with the size of the traditional power divider, and meanwhile, the power divider has good isolation.
Additional advantages, objects, and features of the invention will be set forth in part in the description which follows and in part will become apparent to those having ordinary skill in the art upon examination of the following or may be learned from practice of the invention. The objectives and other advantages of the invention may be realized and attained by the means of the instrumentalities and combinations particularly pointed out hereinafter.
Drawings
For the purposes of promoting a better understanding of the objects, aspects and advantages of the invention, reference will now be made to the following detailed description taken in conjunction with the accompanying drawings in which:
fig. 1 is a schematic front structural view of a miniaturized coplanar waveguide equal power divider based on a cross slow wave transmission line according to the present invention.
Fig. 2 is a schematic diagram of a back structure of the miniaturized coplanar waveguide equal-power splitter based on the cross-type slow-wave transmission line.
Fig. 3 is a schematic front view of a cross slow-wave transmission line according to the present invention.
Fig. 4 is a schematic diagram of a back structure of a cross slow-wave transmission line according to the present invention.
Fig. 5 is an equivalent circuit diagram of the cross slow wave transmission line according to the present invention.
Fig. 6 is a modified equivalent circuit diagram of the cross-type slow wave transmission line equivalent circuit diagram of fig. 5.
Fig. 7 is a structural size diagram of a sample front surface of a miniaturized coplanar waveguide equal power divider based on a cross-type slow wave transmission line according to an embodiment of the invention.
Fig. 8 is a structural size diagram of a sample back surface of a miniaturized coplanar waveguide equal power divider based on a cross-type slow wave transmission line according to an embodiment of the invention.
Fig. 9 is a graph showing simulated S-parameters and simulated phase curves of the cross slow-wave transmission line according to the present invention.
Fig. 10 is a graph of simulated characteristic impedance of the cross slow-wave transmission line according to the present invention.
Fig. 11 is a simulated S-parameter graph of a sample of a miniaturized coplanar waveguide equal power divider based on a cross-type slow-wave transmission line according to an embodiment of the present invention.
Fig. 12 is a simulation graph of the amplitude difference and the phase difference of the output end signal of the sample of the miniaturized coplanar waveguide equal power divider based on the cross-type slow wave transmission line according to the embodiment of the invention.
Fig. 13 is a schematic structural diagram of a conventional coplanar waveguide equal-division power divider.
Fig. 14 is a simulated S parameter diagram of a conventional coplanar waveguide equal-division power divider.
Fig. 15 is a simulation graph of the amplitude difference and the phase difference of the output end signal of the conventional coplanar waveguide equal-division power divider.
Reference numerals: the device comprises a dielectric substrate 1, a signal input port transmission line 2, a signal first output port transmission line 3, a signal second output port transmission line 4, a cross slow wave transmission line 5, a metal through hole I6, a metal through hole II 7, a patch isolation resistor 8, a horizontal rectangular metal patch 9, a vertical rectangular metal patch 10, a long corner coplanar waveguide transmission line 11, a short coplanar waveguide transmission line 12, a short coplanar waveguide transmission line 13, a folding thin transmission line 14 and an interdigital capacitor 15.
Detailed Description
The embodiments of the present invention are described below with reference to specific embodiments, and other advantages and effects of the present invention will be easily understood by those skilled in the art from the disclosure of the present specification. The invention is capable of other and different embodiments and of being practiced or of being carried out in various ways, and its several details are capable of modification in various respects, all without departing from the spirit and scope of the present invention. It should be noted that the drawings provided in the following embodiments are only for illustrating the basic idea of the present invention in a schematic way, and the features in the following embodiments and examples may be combined with each other without conflict.
Wherein the showings are for the purpose of illustrating the invention only and not for the purpose of limiting the same, and in which there is shown by way of illustration only and not in the drawings in which there is no intention to limit the invention thereto; to better illustrate the embodiments of the present invention, some parts of the drawings may be omitted, enlarged or reduced, and do not represent the size of an actual product; it will be understood by those skilled in the art that certain well-known structures in the drawings and descriptions thereof may be omitted.
The same or similar reference numerals in the drawings of the embodiments of the present invention correspond to the same or similar components; in the description of the present invention, it should be understood that if there is an orientation or positional relationship indicated by terms such as "upper", "lower", "left", "right", "front", "rear", etc., based on the orientation or positional relationship shown in the drawings, it is only for convenience of description and simplification of description, but it is not an indication or suggestion that the referred device or element must have a specific orientation, be constructed in a specific orientation, and be operated, and therefore, the terms describing the positional relationship in the drawings are only used for illustrative purposes, and are not to be construed as limiting the present invention, and the specific meaning of the terms may be understood by those skilled in the art according to specific situations.
The invention relates to a miniaturized coplanar waveguide power divider based on a crossed slow-wave transmission line, wherein metal conduction bands are arranged on two surfaces of a dielectric substrate 1, and the structures of the front surface and the back surface of the dielectric substrate are shown in figures 1 and 2.
The front metal layer comprises a signal input port transmission line 2, a signal first output port transmission line 3, a signal second output port transmission line 4, two crossed slow wave transmission lines 5 respectively positioned between the first input port transmission line 2 and the first output port transmission line 3 and between the first input port transmission line 2 and the second output port transmission line 4, 4 metal through holes I6 and a patch isolation resistor 8, wherein the first metal through holes I and the second metal through holes I are in common ground connection with the first output port transmission line 3 and the second output port transmission line 4. In addition, the cross-type slow wave transmission line (5) comprises 4 metal through holes II (7).
Fig. 2 shows the back surface of the dielectric substrate, wherein 2 horizontal rectangular metal patches 9 are respectively located on the upper and lower sides of the corresponding position of the back surface of the isolation resistor, and each horizontal rectangular metal patch 9 is provided with 2 metal through holes one 6, so that the ground planes on the left and right sides of the patch isolation resistor 8 are communicated; in addition, in the cross slow wave transmission line (5), 2 vertical rectangular metal patches 10 are positioned on the back surface of the cross slow wave transmission line 5 close to the corners, and each vertical rectangular metal patch 10 is provided with 2 metal through holes II 7 respectively, so that the ground surfaces on the upper side and the lower side of the central conduction band of the cross slow wave transmission line 5 are communicated.
The two sections of crossed slow-wave transmission lines 5 in the power divider are symmetrically arranged up and down. The front and back surfaces of each cross slow wave transmission line 5 are shown in fig. 3 and 4. As shown in fig. 3, each of the crossed slow-wave transmission lines 5 includes a long-corner coplanar waveguide transmission line 11, a short coplanar waveguide transmission line 12, a short coplanar waveguide transmission line 13, two folded thin transmission lines 14, 4 interdigital capacitor structures 15, and 2 metal vias two (7) on the front surface. Two corners of the long-corner coplanar waveguide transmission line 11 are respectively provided with 90-degree corners. The two ends of the left folding thin transmission line 14 are respectively connected with the central conduction band of the shorter coplanar waveguide transmission line 12 and the central conduction band of the long corner coplanar waveguide transmission line 11; the right folded thin transmission line 14 is respectively connected with the central conduction band of the shorter coplanar waveguide transmission line 12 and the central conduction band of the short coplanar waveguide transmission line 13; two ends of the interdigital capacitor 15 are respectively connected with the folded thin transmission line 14 and the ground plane. The back surface of each cross slow-wave transmission line 5 is shown in fig. 4, and includes a vertical rectangular metal patch 10, and each vertical rectangular metal patch 10 has two metal vias two (7).
In the structure diagram of the power divider in fig. 1, each cross-type slow-wave transmission line has a characteristic impedance of 70.7 Ω, and a phase shift of 90 °, which may be equivalent to a quarter-wavelength transmission line. The left ends of the two crossed slow wave transmission lines are connected to one end of the signal input port transmission line 2, and the right ends of the two crossed slow wave transmission lines are connected to the signal first output port transmission line 3 and the signal second output port transmission line 4 respectively. The ports of the signal input port transmission line 2, the first output port transmission line 3, and the second output port transmission line 4 are respectively used as the port 1, the port 2, and the port 3 of the power divider. The port 1 of the power divider is used for inputting radio frequency signals, and the port 2 and the port 3 are used for outputting the radio frequency signals. The impedances of the three ports of the power divider are all 50 Ω, and the corresponding signal input port transmission line 2, the signal first output port transmission line 3 and the signal second output port transmission line 4 are all coplanar waveguide transmission lines with characteristic impedance of 50 Ω.
The patch isolation resistor 8 is used for isolating signal transmission between the signal first output port transmission line 3 and the signal second output port transmission line 4, so as to prevent crosstalk of reflected signals between the two signal output ports caused by impedance mismatching between the two signal output ports and an external port, and the resistance value of the patch isolation resistor 8 is 100 Ω. The medium substrate is provided with 8 metal through holes, the metal through holes comprise 4 metal through holes II (7) used for connecting the upper ground plane and the lower ground plane of the two crossed slow wave transmission lines 5, and the first output port transmission line 3 and the second output port transmission line 4 share 4 metal through holes I (6) on the ground plane. The inner walls of the through holes are coated with metal and are used for connecting the front metal conducting belts and the back metal conducting belts of the dielectric substrate 1.
An equivalent circuit diagram of the cross type slow wave transmission line 5 is shown in fig. 5. The characteristic impedances of the long corner coplanar waveguide transmission line 11, the short coplanar waveguide transmission line 12 and the short coplanar waveguide transmission line 13 are all 70.7 omega, and the phase shifts are respectively theta1、θ2And theta3. The two-segment folded thin transmission line 14 is equivalent to a series inductor Lx，4The interdigital capacitor structure 15 is equivalent to 4 parallel capacitors CXThe ground plane above and below the interdigital capacitor 15 is equivalent to a series inductor Lx1. FIG. 6 is an equivalent circuit diagram obtained by cross-transforming the middle circuit of FIG. 5, which is substantially the same as the equivalent circuit diagram of FIG. 5 and satisfies Lx＝2Lx1. The circuit diagram is formed by combining three sections of transmission lines and two X-type unit circuits. Wherein the first phase shift is theta1Is a corner coplanar waveguide transmission line 11, and the second phase shift is theta2Is a shorter coplanar waveguide transmission line 12, and the third phase shift is theta3Is a short coplanar waveguide transmission line 13. The X-shaped cross section in the cross type unit circuit is modified from FIG. 5 by a phase shift of θx。
From the equivalent circuit of fig. 5, the total phase shift θ of the cross slow wave transmission line can be obtained as follows:
θ＝θ1+θ2+θ3+2θx
wherein:
where ω represents the angular frequency of operation.
For the characteristic impedance of the cross slow-wave transmission line, the Bloch impedance can be used for solving, and the transfer matrix of the equivalent circuit of the cross slow-wave transmission line shown in fig. 5 is as follows:
wherein:
characteristic resistance of cross slow-wave transmission lineanti-ZlineComprises the following steps:
in the prior research, in order to realize the parallel capacitor C in the equivalent circuit of the cross type slow wave transmission line shown in FIG. 6XTypically in the form of a two or more layer stripline circuit board, which adds complexity to the design and processing. The cross slow wave transmission line provided by the invention utilizes the special structural characteristic that two ground planes and a central conduction band of the coplanar waveguide transmission line are in the same plane, so that two parallel capacitors C in an X-type structureXAnd realizing cross connection in the same plane. Compared with the traditional pi-type slow wave transmission line, the cross-type slow wave transmission line has wider working bandwidth.
Because the folded thin transmission line 14 and the interdigital capacitor 15 are adopted in the crossed slow-wave transmission line, compared with a common 70.7 omega coplanar waveguide transmission line, the transmission line has larger distributed series inductance and ground parallel capacitance per unit length, and the size is more compact under the condition of realizing 70.7 omega characteristic impedance and quarter-wavelength electrical length.
By adjusting the number of interdigital fingers, the length of interdigital fingers, the width of interdigital fingers, the distance between interdigital fingers, the length, the width and the bending times of the folded thin transmission line 14, and the width and the length of the ground plane positioned above and below the interdigital capacitor 15, the series total inductance and the parallel total capacitance can be changed, so that the central frequency point and the bandwidth of the working frequency band of the power divider are changed.
The sample of the embodiment is a miniaturized coplanar waveguide equal-power divider based on a crossed slow-wave transmission line with the working frequency of 0.9 GHz. The coplanar waveguide circuit of the sample of this example was etched on a teflon dielectric substrate having a relative dielectric constant ofr Thickness 1 mm.0805 model chip resistor with isolation resistance 100 Ω and resistor package size 2.0mm × 1.2.2 mm was used in the sample of this example.
The circuit size of the power divider of the sample of the embodiment is 21.9mm × 30mm, namely 0.07 lambdag×0.09λg，λgAs shown in fig. 7, in the case of using the same dielectric substrate and the same central operating frequency as the sample of the embodiment, as shown in fig. 13, the size of the conventional coplanar waveguide power divider is 63.5mm × 28.8.8 mm, and it can be seen that the size of the sample of the embodiment is only 35.9% of that of the conventional coplanar waveguide power divider in fig. 13.
The dimension labels of the miniaturized coplanar waveguide equal-power divider based on the cross slow-wave transmission line in the embodiment of the invention are shown in fig. 7 and 8, and the specific values of the labeled dimension in the figure are shown in table 1:
TABLE 1 actual values of the dimensions (unit: mm) of the samples of the examples are noted
The cross slow-wave transmission line in the invention is simulated by using electromagnetic simulation software Zeland IE3D, and the obtained simulated S parameters and phase are shown in FIG. 9. Simulation results show that the working frequency point of the crossed slow wave transmission line is 0.9GHz, and the | S of the slow wave transmission line11The bandwidth range of | less than-15 dB is 0GHz to 2.1GHz, and the relative bandwidth is 233.3%. At the working frequency point of 0.9GHz, the return loss of the transmission line is 44.3dB, the insertion loss is not more than 0.1dB, and the phase is 90 degrees. The characteristic impedance of the cross-type slow-wave transmission line is shown in fig. 10, and at the operating frequency point of 0.9GHz, the real part of the impedance is 70.7 Ω, and the imaginary part is-0.34 Ω.
An electromagnetic simulation software Zeland IE3D is used to simulate the miniaturized coplanar waveguide equal-power divider of the cross slow-wave transmission line of the sample of the embodiment of the invention, and the obtained simulation S parameter is shown in fig. 11. I S11And | is the module value of the reflection coefficient of the signal input end. I S21I and I S31And | is a modulus of transmission coefficient of the signal from the port 1 of the power divider to the port 2 and the port 3 respectively. I S32And | is the modulus of the transmission coefficient of the signal from port 2 to port 3.
Simulation results fig. 11 shows that the operating frequency of the sample of this example is 0.9 GHz. When | S11The example sample bandwidth ranges from 0.61GHz to 1.16GHz with a relative bandwidth of 61.1% when | is less than-15 dB. At the working frequency point of 0.9GHz, the | S thereof11The | is-26.7 dB, showing that the signal input port of the sample of this embodiment has good impedance matching. | S at this frequency point21I and I S31And the | is-3.14 dB and-3.13 dB respectively, which shows that the loss of the signal at the working frequency point is very low and a good equal division effect is realized. Further, the | S' of the sample of this example over the operating bandwidth21I and I S31All | are greater than-3.3 dB, which shows that the sample of the embodiment can achieve good signal equal division effect in the whole bandwidth range. The amplitude difference and phase difference of the output signals of the two signal output ports 2 and 3 of the sample of the embodiment are shown in fig. 12. The graph shows that the amplitude difference between the output signals of the signal output port 3 and the signal output port 2 is less than 0.03dB and the phase difference between the two output signals is less than 0.1 degree in the range of 0.61GHz-1.16GHz, which shows that the sample of the embodiment well realizes the constant-amplitude in-phase output of the signals in the working bandwidth range. | S at an operating frequency point of 0.9GHz32And the I is less than-15 dB, which indicates that the power divider has good isolation.
Fig. 13 is a schematic structural diagram of a conventional coplanar waveguide equal-division power divider, and fig. 14 shows simulation results of the conventional coplanar waveguide equal-division power divider at | S when the working frequency is 0.9GHz under the condition that the same dielectric substrate is adopted as the sample of the embodiment11The bandwidth range for | less than-15 dB is 0.57GHz-1.23GHz with a relative bandwidth of 73.3%. At the working frequency point of 0.9GHz, | S11I is-25.6 dB, | S21I and I S31All | are-3.2 dB, | S32And | is-25.5 dB. The simulation curve diagram of the amplitude difference and the phase difference of the signals at the output end of the traditional coplanar waveguide equal-division power divider is shown in fig. 15, and the result shows that the amplitude difference of the output signals of the port 3 and the port 2 in the pass band of 0.57GHz-1.23GHz is less than 0.01dB, and the phase difference of the two output signals is less than 0.1 degrees.
The invention is based on the miniaturized coplanar waveguide equal power divider of the cross slow wave transmission line, which can realize the obvious size miniaturization effect, the size of the divider is only 35.9% of the traditional size, and the divider also realizes the good port isolation.
Finally, the above embodiments are only intended to illustrate the technical solutions of the present invention and not to limit the present invention, and although the present invention has been described in detail with reference to the preferred embodiments, it will be understood by those skilled in the art that modifications or equivalent substitutions may be made on the technical solutions of the present invention without departing from the spirit and scope of the technical solutions, and all of them should be covered by the claims of the present invention.
Claims (6)
1. Miniaturized coplane waveguide equipartition merit based on crossing slow wave transmission line divides ware, its characterized in that: comprises the steps of (a) preparing a mixture of a plurality of raw materials,
the metal conduction band is arranged on the front surface and the back surface of the dielectric substrate (1);
the metal conduction band on the front surface of the dielectric substrate (1) comprises a signal input port transmission line (2), a signal first output port transmission line (3) and a signal second output port transmission line (4), two crossed slow-wave transmission lines (5) respectively positioned between the first input port transmission line (2) and the first output port transmission line (3) and between the first input port transmission line (2) and the second output port transmission line (4), 4 metal through holes I (6) which are in common ground plane with the first output port transmission line (3) and the second output port transmission line (4), and a patch isolation resistor (8); in addition, the cross slow wave transmission line (5) comprises 4 metal through holes II (7);
the front surface of the dielectric substrate (1) is provided with a patch isolation resistor (8), the upper side and the lower side of the back surface of the patch isolation resistor (8) corresponding to the position are respectively provided with a horizontal rectangular metal patch (9), each horizontal rectangular metal patch (9) is provided with 2 metal through holes I (6), and the left side and the right side of the patch isolation resistor (8) are communicated with a ground plane; in addition, in the cross slow wave transmission line (5), 2 vertical rectangular metal patches (10) are positioned on the back surface of the cross slow wave transmission line (5) close to the corners, and each vertical rectangular metal patch (10) is provided with 2 metal through holes II (7) respectively so as to enable the ground surfaces on the upper side and the lower side of the central conduction band of the cross slow wave transmission line (5) to be communicated.
2. The miniaturized coplanar waveguide equal power divider based on the crossed slow wave transmission line according to claim 1, characterized in that: the crossed slow wave transmission lines (5) are arranged up and down symmetrically;
each section of crossed slow-wave transmission line (5) comprises a section of long corner coplanar waveguide transmission line (11), a section of short coplanar waveguide transmission line (12), a section of short coplanar waveguide transmission line (13), two sections of folded thin transmission lines (14), 4 interdigital capacitor structures (15) and 2 metal through holes II (7) on the front surface; the back of the crossed slow-wave transmission line comprises 1 vertical rectangular metal patch (10), and 2 metal through holes II (7) are formed in the vertical rectangular metal patch (10).
3. The miniaturized coplanar waveguide equal power divider based on the crossed slow wave transmission line according to claim 2, characterized in that: and 90-degree corners are respectively arranged at two corners of the long-corner coplanar waveguide transmission line (11).
4. The miniaturized coplanar waveguide equal power divider based on the crossed slow wave transmission line according to claim 2, characterized in that: the two sections of thin folding transmission lines (14) are respectively arranged on the left side and the right side;
two ends of the left folding thin transmission line (14) are respectively connected with a central conduction band of the shorter coplanar waveguide transmission line (12) and a central conduction band of the long corner coplanar waveguide transmission line (11);
the right folded thin transmission line (14) is respectively connected with the central conduction band of the shorter coplanar waveguide transmission line (12) and the central conduction band of the short coplanar waveguide transmission line (13);
two ends of the interdigital capacitor (15) are respectively connected with the folded thin transmission line (14) and the ground plane.
5. The miniaturized coplanar waveguide equal power divider based on the crossed slow wave transmission line according to claim 1, characterized in that: the cross slow wave transmission line (5) has 70.7 omega characteristic impedance and 90-degree phase shift and can be equivalent to a quarter-wavelength transmission line;
the left ends of the two crossed slow wave transmission lines (5) are connected to one end of the signal input port transmission line (2), and the right ends of the two crossed slow wave transmission lines are respectively connected with the signal first output port transmission line (3) and the signal second output port transmission line (4);
ports at the signal input port transmission line (2), the first output port transmission line (3) and the second output port transmission line (4) are respectively used as a port 1, a port 2 and a port 3 of the power divider;
a port 1 of the power divider is used for inputting radio frequency signals, and a port 2 and a port 3 are used for outputting the radio frequency signals;
the impedances of the three ports of the power divider are all 50 omega, and the corresponding signal input port transmission line (2), the signal first output port transmission line (3) and the signal second output port transmission line (4) are all coplanar waveguide transmission lines with 50 omega characteristic impedance;
the patch isolation resistor (8) is used for isolating signal transmission between the signal first output port transmission line (3) and the signal second output port transmission line (4) and preventing crosstalk of reflected signals between the two signal output ports caused by impedance mismatching of the two signal output ports and an external port, and the resistance value of the patch isolation resistor (8) is 100 omega;
the medium substrate is provided with 8 metal through holes, the medium substrate comprises 4 metal through holes II (7) used for connecting an upper ground plane and a lower ground plane of two sections of crossed slow wave transmission lines (5), and the first output port transmission line 3 and the second output port transmission line 4 share the 4 metal through holes I (6) on the ground plane; the first metal through hole (6) and the second metal through hole (7) are used for connecting the front side and the back side of the dielectric substrate (1) with the metal conducting belts.
6. The miniaturized coplanar waveguide equal power divider based on the crossed slow wave transmission line according to claim 2, characterized in that: the characteristic impedance of the long corner coplanar waveguide transmission line (11), the characteristic impedance of the short coplanar waveguide transmission line (12) and the characteristic impedance of the short coplanar waveguide transmission line (13) are all 70.7 omega, and the phase shift is theta1、θ2And theta3(ii) a The two sections of the folded thin transmission lines (14) are equivalent to series inductors LxThe 4 interdigital capacitor structures 15 are equivalent to 4 parallel capacitors CXOn interdigital capacitor 15The lower ground plane is equivalent to a series inductor Lx1(ii) a Satisfy Lx＝2Lx1(ii) a The circuit diagram is formed by combining three sections of transmission lines and two X-type unit circuits; wherein the first phase shift is theta1Is a corner coplanar waveguide transmission line (11) and the second phase shift is theta2Is a shorter coplanar waveguide transmission line (12) and the third phase shift is theta3Is a short coplanar waveguide transmission line (13); the phase shift of X-type cross section in the cross type unit circuit is thetax；
The total phase shift theta of the crossed slow wave transmission line is obtained as follows:
θ＝θ1+θ2+θ3+2θx
wherein:
where ω represents the angular frequency of operation;
solving the characteristic impedance of the cross slow-wave transmission line by using Bloch impedance, wherein a transfer matrix of an equivalent circuit of the cross slow-wave transmission line is as follows:
wherein:
obtaining the characteristic impedance Z of the cross slow-wave transmission linelineComprises the following steps:
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