CN111446877B - Control method and system based on two-phase three-bridge-arm inverter circuit - Google Patents

Control method and system based on two-phase three-bridge-arm inverter circuit Download PDF

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CN111446877B
CN111446877B CN202010220408.5A CN202010220408A CN111446877B CN 111446877 B CN111446877 B CN 111446877B CN 202010220408 A CN202010220408 A CN 202010220408A CN 111446877 B CN111446877 B CN 111446877B
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phase
voltage
inverter circuit
bridge arm
bridge
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CN111446877A (en
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胡建明
廖春富
朱佳军
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Guangdong Huanyu Electronic Technology Co ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation

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  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The invention discloses a control method and a system based on a two-phase three-bridge-arm inverter circuit, wherein the control method comprises the following steps: detecting the current output voltage of the output side of the two-phase three-bridge-arm inverter circuit, and performing difference operation on the current output voltage and a set reference voltage to obtain an offset difference value; adjusting the current modulation wave signal based on the offset difference value by using a proportional-integral controller; comparing the adjusted modulation wave signal with a set carrier signal to generate a group of on-off complementary PWM signals corresponding to each bridge arm in the two-phase three-bridge arm inverter circuit; and controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each set of on-off complementary PWM signals so as to output a final voltage waveform. The control method is simple, the control effect can be realized by adopting a simple controller, and the control method is suitable for occasions with high cost requirements and low control precision requirements, such as an elevator backup power supply.

Description

Control method and system based on two-phase three-bridge-arm inverter circuit
Technical Field
The invention relates to the technical field of inverter control, in particular to a control method and a control system based on a two-phase three-bridge-arm inverter circuit.
Background
An inverter is a power electronic device that converts direct current into alternating current, and is applied to various power systems. The current power utilization voltage grades required by various power utilization equipment can be divided into 220V and 380V, most of the power utilization equipment only needs one power utilization voltage, and a small part of the power utilization equipment simultaneously needs the two power utilization voltages, such as an elevator system.
The three-phase three-leg inverter and the three-phase four-leg inverter in the prior art can simultaneously output 220V and 380V voltages, if the voltage with a half-wave load output is required to be met, the current can be realized only by controlling the power supply output on the three-phase four-leg inverter based on a controller, but the control algorithm for the three-phase four-leg inverter is complex, the coordinate system conversion and the current sampling are required, the requirements cannot be met by adopting a simple controller or a control method, and great cost pressure can be brought to the development of some simple backup power supplies. At present, a controller or a control method is lacked, the inverter circuit is controlled to output 220V and 380V voltages simultaneously on the basis of the inverter circuit technology, and a control algorithm with a half-wave type load is met.
Disclosure of Invention
The invention aims to overcome the defects of the prior art, and provides a control method and a control system based on a two-phase three-bridge-arm inverter circuit.
Correspondingly, the embodiment of the invention provides a control method based on a two-phase three-bridge-arm inverter circuit, which comprises the following steps:
detecting the current output voltage of the output side of the two-phase three-bridge-arm inverter circuit, and performing difference operation on the current output voltage and a set reference voltage to obtain an offset difference value;
adjusting the current modulation wave signal based on the offset difference value by using a proportional-integral controller;
comparing the adjusted modulation wave signal with a set carrier signal to generate two groups of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and simultaneously generating a group of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal;
controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each set of on-off complementary PWM signals to output a final voltage waveform;
the detecting a current output voltage at an output side of the two-phase three-bridge arm inverter circuit, and performing a difference operation on the current output voltage and a set reference voltage to obtain an offset difference value includes:
detecting a first output voltage U between a first phase voltage output end and a zero line output end of the output side of the two-phase three-bridge arm inverter circuitANThrough said first output voltage UANSubtracting the set reference voltage U to obtain a first offset difference value;
detecting a second output voltage U between a second phase voltage output end of the output side of the two-phase three-bridge arm inverter circuit and a zero line output endBNThrough said second output voltage UBNSubtracting the set reference voltage U to obtain a second offset difference value;
based on the first output voltage UANAnd the second output voltage UBNObtaining a third output voltage U between a first phase voltage output end and a second phase voltage output end of the two-phase three-bridge arm output sideABAnd through the third output voltage UABAnd a set reference voltage
Figure GDA0002961473350000021
And subtracting to obtain a third offset.
Optionally, the adjusting, by the proportional-integral controller, the current modulation wave signal based on the offset difference includes:
based on the first offset difference, the amplitude U of the first modulated wave S1 is adjusted by a first proportional integral controller1Is adjusted to be U'1And the first modulated wave S1 obtained by the first multiplier at time T is:
S1＝U′1sin(ωt)
based on the second offset difference, the amplitude U of the second modulated wave S2 is adjusted by a second proportional-integral controller2Is adjusted to be U'2(ii) a Adjusting a phase difference Δ θ of the second modulated wave S2 to Δ θ' with a third proportional-integral controller based on the third offset amount; and obtaining a second modulated wave S2 at time T by the phase shifter and the second multiplier as:
Figure GDA0002961473350000031
wherein sin (ω t) is a unit sine signal, ω is a frequency, t is a time, U'1Is the amplitude, U 'of first modulated wave S1 at the time T'2Δ θ' is the phase difference of the second modulated wave S2 at the time T, and te ∈ T, which is the amplitude of the second modulated wave S2 at the time T.
Optionally, the comparing the adjusted modulation wave signal with a set carrier signal to generate two sets of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and generating a set of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal includes:
the first modulation wave S1 at the time T is compared with the carrier signal in a superposition mode, and a first group of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge-arm inverter circuit are generated according to a matching jump principle;
the second modulation wave S2 at the time T is compared with the carrier signal in a superposition mode, and a second group of on-off complementary PWM signals corresponding to a second bridge arm in the two-phase three-bridge-arm inverter circuit are generated according to a matching jump principle;
and performing superposition comparison on a third modulation wave S3 and the carrier signal, and generating a third group of on-off complementary PWM signals corresponding to a third bridge arm in the two-phase three-bridge-arm inverter circuit according to a matching and hopping principle, wherein the third modulation wave S3 is as follows:
Figure GDA0002961473350000032
in the formula, M is the amplitude of the carrier signal, and the carrier signal is a triangular carrier.
Optionally, the controlling the working state of a corresponding one of the two-phase three-leg inverter circuits based on each set of on-off complementary PWM signals to output a final voltage waveform includes:
controlling the interactive on-off of a first switch tube and a second switch tube on the first bridge arm based on the first group of on-off complementary PWM signals;
controlling the interactive on-off of a third switching tube and a fourth switching tube on the second bridge arm based on the second group of on-off complementary PWM signals;
and controlling the interactive on-off of a fifth switching tube and a sixth switching tube on the third bridge arm based on the third group of on-off complementary PWM signals.
In addition, an embodiment of the present invention further provides a control system based on a two-phase three-bridge-arm inverter circuit, where the control system includes:
the voltage detection module is used for detecting the current output voltage at the output side of the two-phase three-bridge-arm inverter circuit and carrying out difference operation on the current output voltage and a set reference voltage so as to obtain an offset difference value;
the waveform adjusting module is used for adjusting the current modulating wave signal based on the offset difference value by utilizing a proportional-integral controller;
the signal generation module is used for comparing the adjusted modulation wave signal with a set carrier signal to generate two groups of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and simultaneously generating a group of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal;
the state control module is used for controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each group of on-off complementary PWM signals so as to output a final voltage waveform;
the voltage detection module comprises a first voltage detection circuit and a second voltage detection circuit;
the first voltage detection circuit is used for detecting a first output voltage U between a first phase voltage output end and a zero line output end of the output side of the two-phase three-bridge-arm inverter circuitANThrough said first output voltage UANIs subtracted from the set reference voltage U,obtaining a first offset difference value;
the second voltage detection circuit is used for detecting a second output voltage U between a second phase voltage output end and a zero line output end of the output side of the two-phase three-bridge-arm inverter circuitBNThrough said second output voltage UBNSubtracting the set reference voltage U to obtain a second offset difference value; and based on the first output voltage UANAnd the second output voltage UBNObtaining a third output voltage U between a first phase voltage output end and a second phase voltage output end of the two-phase three-bridge arm output sideABAnd through the third output voltage UABAnd a set reference voltage
Figure GDA0002961473350000041
And subtracting to obtain a third offset.
Optionally, the waveform adjusting module includes a first proportional-integral controller, a second proportional-integral controller, and a third proportional-integral controller;
the first proportional integral controller is used for regulating the amplitude U of the first modulated wave S1 based on the first offset difference1Is adjusted to be U'1And the first modulated wave S1 obtained by the first multiplier at time T is:
S1＝U′1sin(ωt)
the second proportional integral controller is used for regulating the amplitude U of the second modulation wave S2 based on the second offset difference2Is adjusted to be U'2；
The third proportional-integral controller is configured to adjust the phase difference Δ θ of the second modulated wave S2 to Δ θ' based on the third offset amount, and obtain, through the phase shifter and the second multiplier, the second modulated wave S2 at time T as:
Figure GDA0002961473350000051
wherein sin (ω t) is a unit sine signal, ω is a frequency, t is a time, U'1The amplitude of the first modulated wave S1 at the time T，U′2Δ θ' is the phase difference of the second modulated wave S2 at the time T, and te ∈ T, which is the amplitude of the second modulated wave S2 at the time T.
Optionally, the signal generating module includes a first PWM generating circuit, a second PWM generating circuit, and a third PWM generating circuit;
the first PWM generating circuit is used for performing superposition comparison on the first modulation wave S1 at the time T and the carrier signal, and generating a first group of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge-arm inverter circuit according to a matching and jumping principle;
the second PWM generating circuit is configured to compare the second modulation wave S2 at the time T with the carrier signal in a superposition manner, and generate a second set of on-off complementary PWM signals corresponding to a second bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle;
the third PWM generating circuit is configured to perform superposition comparison on a third modulated wave S3 and the carrier signal, and generate a third set of on-off complementary PWM signals corresponding to a third bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle, where the third modulated wave S3 is:
Figure GDA0002961473350000052
wherein M is the amplitude of the carrier signal, and the carrier signal is a triangular carrier.
In the embodiment of the invention, based on the current output voltage of the two-phase three-bridge arm inverter circuit, the switching time of each switching tube in the two-phase three-bridge arm inverter circuit is adjusted by adopting a PWM control technology, so that the required sinusoidal alternating-current voltage is generated at the output side of the two-phase three-bridge arm inverter circuit. Compared with a three-phase four-bridge arm inverter in the prior art, the control method provided by the invention is simpler, coordinate system transformation and current sampling are not needed, and the cost of a control system can be greatly reduced, so that the total cost of a corresponding two-phase three-bridge arm inverter product is effectively reduced.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
FIG. 1 is a schematic diagram of a two-phase three-leg inverter circuit according to an embodiment of the present invention;
fig. 2 is a schematic structural diagram of a two-phase three-bridge arm inverter circuit disclosed in the embodiment of the present invention;
fig. 3 is a schematic flow chart of a control method based on a two-phase three-bridge-arm inverter circuit according to an embodiment of the present invention;
FIG. 4 is a schematic diagram of a forming process of a PWM control signal of a first bridge arm according to the embodiment of the invention;
fig. 5 is a schematic structural composition diagram of a control system based on a two-phase three-bridge inverter circuit according to an embodiment of the present invention;
fig. 6 is a schematic diagram of a specific implementation process of a control system based on a two-phase three-bridge inverter circuit according to an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Referring to fig. 1 to 2, fig. 1 is a schematic diagram of a two-phase three-leg inverter circuit according to an embodiment of the present invention, and fig. 2 is a schematic diagram of a structure of the two-phase three-leg inverter circuit according to the embodiment of the present invention.
As shown in fig. 1, a two-phase three-bridge arm inverter circuit includes a dc power supply 100, an energy storage unit, an inverter control unit, and a filtering unit; the dc power supply 100 is connected to the energy storage unit, and the energy storage unit is connected to the inverter control unit.
Specifically, the inversion control unit comprises a first bridge arm, a second bridge arm and a third bridge arm which are arranged in parallel, and the filtering unit comprises a first LC filter, a second LC filter and a first filtering inductor; the input end of the first LC filter is connected with the output end a of the first bridge arm, and the output end of the first LC filter is connected with a first phase voltage output end A; the input end of the second LC filter is connected with the output end B of the second bridge arm, and the output end of the second LC filter is connected with the second phase voltage output end B; one end of the first filter inductor is connected with the output end N1 of the third bridge arm, and the other end of the first filter inductor is connected with the zero line output end N.
Further, as shown in fig. 2, the energy storage unit includes a first bus capacitor DC1 and a second bus capacitor DC2 that are serially connected, one end of the first bus capacitor DC1 is connected to the positive electrode of the DC power supply 100, one end of the second bus capacitor DC2 is connected to the negative electrode of the DC power supply 100, and the zero line output terminal N is led out from a connection conductor between the first bus capacitor DC1 and the second bus capacitor DC 2.
Further, as shown in fig. 2, a first switching tube Q1 and a second switching tube Q2 are connected in series in the first arm, and an emitter of the first switching tube Q1 is connected to a collector of the second switching tube Q2; a third switching tube Q3 and a fourth switching tube Q4 are sequentially connected in series on the second bridge arm, and an emitter of the third switching tube Q3 is connected with a collector of the fourth switching tube Q4; a fifth switching tube Q5 and a sixth switching tube Q6 are connected in series in sequence on the third arm, and an emitter of the fifth switching tube Q5 is connected with a collector of the sixth switching tube Q6.
The collector of the first switching tube Q1, the collector of the third switching tube Q3 and the collector of the fifth switching tube Q5 are respectively connected with one end of the first bus capacitor DC 1; the emitter of the second switch tube Q2, the emitter of the fourth switch tube Q4 and the emitter of the sixth switch tube Q6 are respectively connected with one end of the second bus capacitor DC 2.
Further, as shown in fig. 2, the first LC filter includes a second filter inductor L1 and a first filter capacitor C1, a first end of the second filter inductor L1 is connected to the connection conductor between the first switch tube Q1 and the second switch tube Q2, a second end of the second filter inductor L1 is connected to the first phase voltage output terminal a, a first end of the first filter capacitor C1 is connected to a second end of the second filter inductor L1, and a second end of the first filter capacitor C1 is connected to the neutral line output terminal N; the second LC filter comprises a third filter inductor L2 and a second filter capacitor C2, a first end of the third filter inductor L2 is connected to a connection wire between the third switch tube Q3 and the fourth switch tube Q4, a second end of the third filter inductor L2 is connected to the second phase voltage output end B, a first end of the second filter capacitor C2 is connected to a second end of the third filter inductor L2, and a second end of the second filter capacitor C2 is connected to the neutral line output end N; a first end of the first filter inductor L3 is connected to a connection conductor between the fifth switching tube Q5 and the sixth switching tube Q6, and a second end of the first filter inductor L3 is connected to the neutral line output end N.
Based on the two-phase three-bridge arm inverter circuit provided in fig. 2, fig. 3 shows a schematic flow chart of a control method based on the two-phase three-bridge arm inverter circuit in the embodiment of the present invention.
As shown in fig. 3, a control method based on a two-phase three-bridge arm inverter circuit includes the following steps:
s101, detecting the current output voltage of the output side of the two-phase three-bridge arm inverter circuit, and performing difference operation on the current output voltage and a set reference voltage to obtain an offset difference value;
it should be noted that, because three bridge arms in the two-phase three-bridge-arm inverter circuit are controlled by an external controller, and when the two-phase three-bridge-arm inverter circuit initially works, the external controller already forms PWM control signals for the three bridge arms, the control method provided in the embodiment of the present invention reversely adjusts the PWM control signals of the three bridge arms by using the current output voltage at the output side of the two-phase three-bridge-arm inverter circuit, so as to achieve the purpose of outputting the required sinusoidal ac voltage.
The specific implementation process comprises the following steps: detecting a first output voltage U between a first phase voltage output end A and a zero line output end N of the output side of the two-phase three-bridge arm inverter circuitANThrough said first output voltage UANSubtracting the set reference voltage U to obtain a first offset difference value; detecting a second output voltage U between a second phase voltage output end B and a zero line output end N of the output side of the two-phase three-bridge arm inverter circuitBNThrough said second output voltage UBNSubtracting the set reference voltage U to obtain a second offset difference value; based on the first output voltage UANAnd the second output voltage UBNObtaining a third output voltage U between a first phase voltage output end A and a second phase voltage output end B of the two-phase three-bridge arm output sideABAnd through the third output voltage UABAnd a set reference voltage
Figure GDA0002961473350000081
Subtracting to obtain a third offset, wherein the third output voltage UABFor the first output voltage UANAnd the second output voltage UBNThe difference of (a).
The set reference voltage U is limited according to the maximum output power of the two-phase three-bridge arm inverter circuit in the working state. Due to the first output voltage UANAnd the second output voltage UBNThe effective values of the voltage values are the same, and a reference voltage U is adopted to carry out difference operation in the implementation process; but due to said first output voltage UANAnd the second output voltage UBNThe phase difference of the third output voltage U is 120 degrees, and the third output voltage U is obtained after the difference operation and simplification of the phase difference and the second output voltage UABIs the first output voltage UANOr the second output voltage UBNOf (a) effective value
Figure GDA0002961473350000091
Double, so the third output voltage UABUsing reference voltages in the implementation
Figure GDA0002961473350000092
And performing difference operation.
S102, adjusting a current modulation wave signal based on the offset difference value by using a proportional-integral controller;
the proportional-integral controller operates on the principle that a deviation formed by a given value and an actual output value is linearly combined according to proportion, integral and differential to form a control quantity, and then a controlled object is controlled. In the embodiment of the present invention, step S101 already realizes solving the deviation value of each output voltage, and in step S102, the current modulation wave signal corresponding to each output voltage is adjusted to obtain a better modulation wave signal, and three proportional-integral controllers are adopted to realize the solving according to the requirement of the modulation parameter.
The specific implementation process comprises the following steps: based on the first offset difference, the amplitude U of the first modulated wave S1 is adjusted by a first proportional integral controller1Is adjusted to be U'1And the first modulated wave S1 obtained by the first multiplier at time T is:
S1＝U′1sin(ωt)
based on the second offset difference, the amplitude U of the second modulated wave S2 is adjusted by a second proportional-integral controller2Is adjusted to be U'2(ii) a Adjusting a phase difference Δ θ of the second modulated wave S2 to Δ θ' with a third proportional-integral controller based on the third offset amount; and obtaining a second modulated wave S2 at time T by the phase shifter and the second multiplier as:
Figure GDA0002961473350000093
wherein sin (ω t) is a unit sine signal, ω is a frequency, typically 50Hz or 60Hz (mains frequency), and t is timeAre of U'1Is the amplitude, U 'of first modulated wave S1 at the time T'2Δ θ' is the phase difference of the second modulated wave S2 at the time T, and te ∈ T, which is the amplitude of the second modulated wave S2 at the time T. In addition, the phase shifter performs fine adjustment of the phase based on the phase difference originally present with respect to the unit sinusoidal signal when performing phase adjustment.
It should be noted that T in the above two expressions is an indefinite value, and in this case, the first modulated wave S1 at the time T and the second modulated wave S2 at the time T change with the value of T, which is not limited in any way in the embodiment of the present invention.
S103, comparing the adjusted modulation wave signal with a set carrier signal to generate two groups of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and simultaneously generating a group of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal;
the specific implementation process comprises the following steps: the first modulation wave S1 at the time T is compared with the carrier signal in a superposition mode, and a first group of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge-arm inverter circuit are generated according to a matching jump principle; the second modulation wave S2 at the time T is compared with the carrier signal in a superposition mode, and a second group of on-off complementary PWM signals corresponding to a second bridge arm in the two-phase three-bridge-arm inverter circuit are generated according to a matching jump principle; and performing superposition comparison on a third modulation wave S3 and the carrier signal, and generating a third group of on-off complementary PWM signals corresponding to a third bridge arm in the two-phase three-bridge-arm inverter circuit according to a matching and hopping principle, wherein the third modulation wave S3 is as follows: s3 ═ M/2, where M is the amplitude of the carrier signal, and the carrier signal is a triangular carrier.
Wherein the formation of the carrier signal is actually derived from a counter counting up and down in a controller of the peripheral, and the count up and down starts when the counter starts counting up from zero until the count value reaches the amplitude M; when the counter counts down until it returns to zero, it starts to count up again, and this cycle can generate a high frequency triangular wave signal, i.e. the carrier signal, as shown in fig. 4.
To further explain the generation process of any one set of on-off complementary PWM signals, fig. 4 shows a schematic diagram of a forming process of a PWM control signal of a first bridge arm in the embodiment of the present invention, and the first switching tube Q1 and the second switching tube Q2 are in an alternately on-off working state according to a normal working state of the two-phase three-bridge arm inverter circuit, which is specifically expressed as: when the first modulation wave S1 at the time T and the carrier signal are on the same coordinate axis and the starting points coincide, the first switching tube Q1 takes the off state as the starting point, and when the two waveform signals occur a first intersection point, a jump (closed state) occurs, and when the two waveform signals occur a second intersection point, a jump (off state) occurs again, and so on, the PWM control signal of the first switching tube Q1 is obtained; the second switch tube Q2 takes the closed state as the starting point, when the two waveform signals have the first intersection point, the two waveform signals have one jump (off state), and when the two waveform signals have the second intersection point, the two waveform signals have one jump (on state), and so on, the PWM control signal of the second switch tube Q2 is obtained. Therefore, a first group of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge arm inverter circuit can be obtained, as shown in FIG. 4, and the time length of each jump is the switching time length of the corresponding switching tube.
It should be noted that the first switch tube Q1 and the second switch tube Q2 cannot be closed at the same time, so as to avoid a direct short circuit of the power supply, and further to burn out the two-phase three-bridge inverter circuit.
And S104, controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each group of on-off complementary PWM signals so as to output a final voltage waveform.
The specific implementation process comprises the following steps: controlling the interactive on-off of a first switch tube Q1 and a second switch tube Q2 on the first bridge arm based on the first group of on-off complementary PWM signals; controlling the interactive on-off of a third switching tube Q3 and a fourth switching tube Q4 on the second bridge arm based on the second group of on-off complementary PWM signals; and controlling the mutual on-off of a fifth switch tube Q5 and a sixth switch tube Q6 on the third bridge arm based on the third group of on-off complementary PWM signals.
The three sets of on-off complementary PWM signals allow a corresponding bridge arm to be controlled simultaneously to perform a related action, and when a set of switching tubes on each bridge arm works, the two-phase three-bridge-arm inverter circuit generates different output states, including: generating a fourth output voltage with the rated voltage of U between the first phase voltage output end A and the zero line output end N by controlling the action of the first bridge arm; generating a fifth output voltage with a rated voltage of U between the second-phase voltage output end B and the zero line output end N by controlling the action of the second bridge arm; by controlling the simultaneous operation of the first bridge arm and the second bridge arm, a rated voltage of
Figure GDA0002961473350000111
The sixth output voltage of (1). The alternating on-off of the fifth switching tube Q5 and the sixth switching tube Q6 on the third bridge arm is to control the voltage unbalance between the first bus capacitor DC1 and the second bus capacitor DC2 caused by the half-wave load, and the switch tubes are closed to release the redundant energy on the corresponding bus capacitors, so as to mainly protect the two-phase three-bridge arm inverter circuit.
It should be noted that, the two-phase three-bridge inverter circuit selects a midpoint n2 between the first bus capacitor DC1 and the second bus capacitor DC2 on the direct current side as a zero potential point, so that voltage signals output from output points a, b, and n1 on three bridge arms in the two-phase three-bridge inverter circuit have ± UdTwo levels,/2, where UdIs the voltage value of the dc power supply 100.
Based on the description of the first set of on-off complementary PWM signals corresponding to the first arm shown in fig. 4 in step S103, the voltage signal output from the output point a on the first arm is continuously described: when the first switch tube Q1 is in a closed state, the starting point of the current trend is the positive pole of the dc power supply 100, so a high level is output at the output point a; when the second switch Q2 is in the closed state, the starting point of the current trend is the negative terminal of the dc power supply, so a low level will be output at the output point a. Therefore, a voltage signal output by an output point a on a first bridge arm in the two-phase three-bridge arm inverter circuit can be obtained, and the voltage signal is subjected to filtering processing by the first LC filter to obtain a fourth output voltage with a rated voltage U between the first phase voltage output end a and the zero line output end N, as shown in fig. 4.
Referring to fig. 5 to 6, fig. 5 is a schematic structural diagram of a control system based on a two-phase three-bridge inverter circuit in an embodiment of the present invention, and fig. 6 is a schematic diagram of an implementation process of the control system based on the two-phase three-bridge inverter circuit in the embodiment of the present invention.
As shown in fig. 5, a control system based on a two-phase three-bridge arm inverter circuit includes a voltage detection module, a waveform adjustment module, a signal generation module, and a state control module.
Specifically, the voltage detection module is configured to detect a current output voltage at an output side of the two-phase three-bridge inverter circuit, and perform a difference operation on the current output voltage and a set reference voltage to obtain an offset difference value; the waveform adjusting module is used for adjusting the current modulating wave signal based on the offset difference value by utilizing a proportional-integral controller; the signal generation module is used for comparing the adjusted modulation wave signal with a set carrier signal to generate two groups of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and simultaneously generating a group of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal; the state control module is used for controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each group of on-off complementary PWM signals so as to output a final voltage waveform.
Further, the voltage detection module comprises a first voltage detection circuit and a second voltage detection circuit. Wherein, as shown in FIG. 6, the first electrodeThe voltage detection circuit is used for detecting a first output voltage U between a first phase voltage output end and a zero line output end of the output side of the two-phase three-bridge arm inverter circuitANThrough said first output voltage UANSubtracting the set reference voltage U to obtain a first offset difference value; the second voltage detection circuit is used for detecting a second output voltage U between a second phase voltage output end and a zero line output end of the output side of the two-phase three-bridge-arm inverter circuitBNThrough said second output voltage UBNSubtracting the set reference voltage U to obtain a second offset difference value; and based on the first output voltage UANAnd the second output voltage UBNObtaining a third output voltage U between a first phase voltage output end and a second phase voltage output end of the two-phase three-bridge arm output sideABAnd through the third output voltage UABAnd a set reference voltage
Figure GDA0002961473350000121
And subtracting to obtain a third offset.
Further, the waveform adjusting module includes a first proportional-integral controller, a second proportional-integral controller, and a third proportional-integral controller. As shown in fig. 6, the specific applications include the following:
the first proportional integral controller is used for regulating the amplitude U of the first modulated wave S1 based on the first offset difference1Is adjusted to be U'1And the first modulated wave S1 obtained by the first multiplier at time T is:
S1＝U′1sin(ωt)
the second proportional integral controller is used for regulating the amplitude U of the second modulation wave S2 based on the second offset difference2Is adjusted to be U'2(ii) a The third proportional-integral controller is configured to adjust the phase difference Δ θ of the second modulated wave S2 to Δ θ' based on the third offset amount, and obtain, through the phase shifter and the second multiplier, the second modulated wave S2 at time T as:
Figure GDA0002961473350000131
wherein sin (ω t) is a unit sine signal, ω is a frequency, t is a time, U'1Is the amplitude, U 'of first modulated wave S1 at the time T'2Δ θ' is the phase difference of the second modulated wave S2 at the time T, and te ∈ T, which is the amplitude of the second modulated wave S2 at the time T.
Further, the signal generation module comprises a first PWM generation circuit, a second PWM generation circuit and a third PWM generation circuit. As shown in fig. 6, the first PWM generating circuit is configured to perform superposition comparison on the first modulated wave S1 at the time T and the carrier signal, and generate a first set of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle; the second PWM generating circuit is configured to compare the second modulation wave S2 at the time T with the carrier signal in a superposition manner, and generate a second set of on-off complementary PWM signals corresponding to a second bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle; the third PWM generating circuit is configured to perform superposition comparison on a third modulated wave S3 and the carrier signal, and generate a third set of on-off complementary PWM signals corresponding to a third bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle, where the third modulated wave S3 is:
Figure GDA0002961473350000132
wherein M is the amplitude of the carrier signal, and the carrier signal is a triangular carrier.
It should be noted that, because the control object of the state control module is the two-phase three-bridge arm inverter circuit, the three sets of on-off complementary PWM signals generated by the signal generation module respectively control the actions of the three bridge arms in the inverter circuit, so as to meet the requirement that the inverter circuit can generate the required voltage at its output end in a stable working state.
The control system is configured to execute the control method based on the two-phase three-bridge-arm inverter circuit, and for specific implementation of each module and devices inside each module in the control system, reference is made to the above-mentioned embodiment, which is not described herein again.
In the embodiment of the invention, based on the current output voltage of the two-phase three-bridge arm inverter circuit, the switching time of each switching tube in the two-phase three-bridge arm inverter circuit is adjusted by adopting a PWM control technology, so that the required sinusoidal alternating-current voltage is generated at the output side of the two-phase three-bridge arm inverter circuit. Compared with a three-phase four-bridge arm inverter in the prior art, the control method provided by the invention is simpler, coordinate system transformation and current sampling are not needed, and the cost of a control system can be greatly reduced, so that the total cost of a corresponding two-phase three-bridge arm inverter product is effectively reduced.
In addition, the two-phase three-bridge-arm inverter circuit-based control method and system provided by the embodiment of the invention are described in detail, a specific example is adopted to explain the principle and the implementation mode of the invention, and the description of the embodiment is only used for helping to understand the method and the core idea of the invention; meanwhile, for a person skilled in the art, according to the idea of the present invention, there may be variations in the specific embodiments and the application scope, and in summary, the content of the present specification should not be construed as a limitation to the present invention.

Claims (7)

1. A control method based on a two-phase three-bridge arm inverter circuit is characterized by comprising the following steps:
detecting the current output voltage of the output side of the two-phase three-bridge-arm inverter circuit, and performing difference operation on the current output voltage and a set reference voltage to obtain an offset difference value;
adjusting the current modulation wave signal based on the offset difference value by using a proportional-integral controller;
comparing the adjusted modulation wave signal with a set carrier signal to generate two groups of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and simultaneously generating a group of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal;
controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each set of on-off complementary PWM signals to output a final voltage waveform;
the detecting a current output voltage at an output side of the two-phase three-bridge arm inverter circuit, and performing a difference operation on the current output voltage and a set reference voltage to obtain an offset difference value includes:
detecting a first output voltage U between a first phase voltage output end and a zero line output end of the output side of the two-phase three-bridge arm inverter circuitANThrough said first output voltage UANSubtracting the set reference voltage U to obtain a first offset difference value;
detecting a second output voltage U between a second phase voltage output end of the output side of the two-phase three-bridge arm inverter circuit and a zero line output endBNThrough said second output voltage UBNSubtracting the set reference voltage U to obtain a second offset difference value;
based on the first output voltage UANAnd the second output voltage UBNObtaining a third output voltage U between a first phase voltage output end and a second phase voltage output end of the two-phase three-bridge arm output sideABAnd through the third output voltage UABAnd a set reference voltage
Figure FDA0002961473340000011
And subtracting to obtain a third offset.
2. The control method according to claim 1, wherein the adjusting the current modulation wave signal based on the offset difference value by using a proportional-integral controller comprises:
based on the first offset difference, the amplitude U of the first modulated wave S1 is adjusted by a first proportional integral controller1Is adjusted to be U'1And obtaining time T by a first multiplierThe first modulated wave S1 is:
S1＝U′1sin(ωt)
based on the second offset difference, the amplitude U of the second modulated wave S2 is adjusted by a second proportional-integral controller2Is adjusted to be U'2(ii) a Adjusting a phase difference Δ θ of the second modulated wave S2 to Δ θ' with a third proportional-integral controller based on the third offset amount; and obtaining a second modulated wave S2 at time T by the phase shifter and the second multiplier as:
Figure FDA0002961473340000021
wherein sin (ω t) is a unit sine signal, ω is a frequency, t is a time, U'1Is the amplitude, U 'of first modulated wave S1 at the time T'2Δ θ' is the phase difference of the second modulated wave S2 at the time T, and te ∈ T, which is the amplitude of the second modulated wave S2 at the time T.
3. The control method according to claim 2, wherein the comparing the adjusted modulation wave signal with a set carrier signal to generate two sets of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and the generating a set of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit using the carrier signal comprises:
the first modulation wave S1 at the time T is compared with the carrier signal in a superposition mode, and a first group of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge-arm inverter circuit are generated according to a matching jump principle;
the second modulation wave S2 at the time T is compared with the carrier signal in a superposition mode, and a second group of on-off complementary PWM signals corresponding to a second bridge arm in the two-phase three-bridge-arm inverter circuit are generated according to a matching jump principle;
and performing superposition comparison on a third modulation wave S3 and the carrier signal, and generating a third group of on-off complementary PWM signals corresponding to a third bridge arm in the two-phase three-bridge-arm inverter circuit according to a matching and hopping principle, wherein the third modulation wave S3 is as follows:
Figure FDA0002961473340000022
in the formula, M is the amplitude of the carrier signal, and the carrier signal is a triangular carrier.
4. The control method according to claim 3, wherein the controlling the operating state of a corresponding one of the two-phase three-leg inverter circuits based on each set of on-off complementary PWM signals to output a final voltage waveform comprises:
controlling the interactive on-off of a first switch tube and a second switch tube on the first bridge arm based on the first group of on-off complementary PWM signals;
controlling the interactive on-off of a third switching tube and a fourth switching tube on the second bridge arm based on the second group of on-off complementary PWM signals;
and controlling the interactive on-off of a fifth switching tube and a sixth switching tube on the third bridge arm based on the third group of on-off complementary PWM signals.
5. A control system based on two-phase three-bridge arm inverter circuit is characterized by comprising:
the voltage detection module is used for detecting the current output voltage at the output side of the two-phase three-bridge-arm inverter circuit and carrying out difference operation on the current output voltage and a set reference voltage so as to obtain an offset difference value;
the waveform adjusting module is used for adjusting the current modulating wave signal based on the offset difference value by utilizing a proportional-integral controller;
the signal generation module is used for comparing the adjusted modulation wave signal with a set carrier signal to generate two groups of on-off complementary PWM signals corresponding to the first two bridge arms in the two-phase three-bridge arm inverter circuit, and simultaneously generating a group of on-off complementary PWM signals corresponding to the third bridge arm in the two-phase three-bridge arm inverter circuit by using the carrier signal;
the state control module is used for controlling the working state of a corresponding bridge arm in the two-phase three-bridge arm inverter circuit based on each group of on-off complementary PWM signals so as to output a final voltage waveform;
the voltage detection module comprises a first voltage detection circuit and a second voltage detection circuit;
the first voltage detection circuit is used for detecting a first output voltage U between a first phase voltage output end and a zero line output end of the output side of the two-phase three-bridge-arm inverter circuitANThrough said first output voltage UANSubtracting the set reference voltage U to obtain a first offset difference value;
the second voltage detection circuit is used for detecting a second output voltage U between a second phase voltage output end and a zero line output end of the output side of the two-phase three-bridge-arm inverter circuitBNThrough said second output voltage UBNSubtracting the set reference voltage U to obtain a second offset difference value; and based on the first output voltage UANAnd the second output voltage UBNObtaining a third output voltage U between a first phase voltage output end and a second phase voltage output end of the two-phase three-bridge arm output sideABAnd through the third output voltage UABAnd a set reference voltage
Figure FDA0002961473340000041
And subtracting to obtain a third offset.
6. The control system of claim 5, wherein the waveform adjustment module comprises a first proportional-integral controller, a second proportional-integral controller, and a third proportional-integral controller;
the first proportional integral controller is used for regulating the amplitude U of the first modulated wave S1 based on the first offset difference1Is adjusted to be U'1And the first modulated wave S1 obtained by the first multiplier at time T is:
S1＝U′1sin(ωt)
the second proportional integral controller is used for regulating the amplitude U of the second modulation wave S2 based on the second offset difference2Is adjusted to be U'2；
The third proportional-integral controller is configured to adjust the phase difference Δ θ of the second modulated wave S2 to Δ θ' based on the third offset amount, and obtain, through the phase shifter and the second multiplier, the second modulated wave S2 at time T as:
Figure FDA0002961473340000042
wherein sin (ω t) is a unit sine signal, ω is a frequency, t is a time, U'1Is the amplitude, U 'of first modulated wave S1 at the time T'2Δ θ' is the phase difference of the second modulated wave S2 at the time T, and te ∈ T, which is the amplitude of the second modulated wave S2 at the time T.
7. The control system of claim 6, wherein the signal generation module comprises a first PWM generation circuit, a second PWM generation circuit, and a third PWM generation circuit;
the first PWM generating circuit is used for performing superposition comparison on the first modulation wave S1 at the time T and the carrier signal, and generating a first group of on-off complementary PWM signals corresponding to a first bridge arm in the two-phase three-bridge-arm inverter circuit according to a matching and jumping principle;
the second PWM generating circuit is configured to compare the second modulation wave S2 at the time T with the carrier signal in a superposition manner, and generate a second set of on-off complementary PWM signals corresponding to a second bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle;
the third PWM generating circuit is configured to perform superposition comparison on a third modulated wave S3 and the carrier signal, and generate a third set of on-off complementary PWM signals corresponding to a third bridge arm in the two-phase three-bridge inverter circuit according to a matching and hopping principle, where the third modulated wave S3 is:
Figure FDA0002961473340000051
wherein M is the amplitude of the carrier signal, and the carrier signal is a triangular carrier.
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