CN111181465B - Direct torque control method and device for open-winding permanent magnet synchronous motor system - Google Patents

Direct torque control method and device for open-winding permanent magnet synchronous motor system Download PDF

Info

Publication number
CN111181465B
CN111181465B CN202010116830.6A CN202010116830A CN111181465B CN 111181465 B CN111181465 B CN 111181465B CN 202010116830 A CN202010116830 A CN 202010116830A CN 111181465 B CN111181465 B CN 111181465B
Authority
CN
China
Prior art keywords
motor
ref
vector
voltage vector
flux linkage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN202010116830.6A
Other languages
Chinese (zh)
Other versions
CN111181465A (en
Inventor
孙丹
王铭泽
郑志豪
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Zhejiang University ZJU
Original Assignee
Zhejiang University ZJU
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Zhejiang University ZJU filed Critical Zhejiang University ZJU
Priority to CN202010116830.6A priority Critical patent/CN111181465B/en
Publication of CN111181465A publication Critical patent/CN111181465A/en
Application granted granted Critical
Publication of CN111181465B publication Critical patent/CN111181465B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
    • H02P21/28—Stator flux based control
    • H02P21/30—Direct torque control [DTC] or field acceleration method [FAM]
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/05—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for damping motor oscillations, e.g. for reducing hunting
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/12—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation pulsing by guiding the flux vector, current vector or voltage vector on a circle or a closed curve, e.g. for direct torque control

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

The invention discloses a direct torque control method and a direct torque control device for an open-winding permanent magnet synchronous motor system. The method eliminates a hysteresis comparator required in the traditional control structure, simplifies a switching table by a space voltage vector plane sector division mode suitable for an open winding motor structure, realizes the one-to-one correspondence of the sectors and basic voltage vectors, improves the precision of the selected voltage vectors, and improves the static running performance of a motor system.

Description

Direct torque control method and device for open-winding permanent magnet synchronous motor system
Technical Field
The invention belongs to the technical field of motor control, and particularly relates to a direct torque control method and a direct torque control device for an open-winding permanent magnet synchronous motor system.
Background
The open-winding permanent magnet synchronous motor is a novel topological structure which opens a neutral point of a stator winding of the motor and accesses two inverters at two ends of the winding for power supply. The inverter can reduce the requirement on the capacity of a single inverter, can generate a multi-level power supply effect and reduce voltage harmonics, and is widely researched in the fields of electric automobiles, aerospace and military at present.
Direct torque control is an important control idea in the field of motor control, but for a double-independent-power-supply type open-winding permanent magnet synchronous motor, because a double-inverter structure can generate relatively abundant basic voltage vectors, the design of a hysteresis comparator in the traditional direct torque control is more difficult, and meanwhile, the complexity of a switching table is increased, so that a method suitable for direct torque control of the open-winding permanent magnet synchronous motor needs to be researched. Of course, the problem of high torque ripple and flux linkage ripple in direct torque control has been receiving wide attention from researchers.
Disclosure of Invention
The invention aims to provide a direct torque control method of a double-independent-power-supply type open-winding permanent magnet synchronous motor system based on a simplified switch table, so as to solve the problems of complex switch table, complex selected voltage vector and large motor torque ripple in the related technology.
In order to achieve the purpose, the invention adopts the technical scheme that:
in a first aspect, an embodiment of the present invention provides a direct torque control method for an open-winding permanent magnet synchronous motor system, including:
collecting three-phase stator current, line voltage and rotor position angle of the motor, and differentiating the rotor position angle to obtain the rotating speed of the motor;
calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage, and calculating a flux linkage given vector according to the rotor position angle;
respectively calculating reference voltage vectors of the motor in an alpha-beta coordinate system and an a-b-c coordinate system according to a flux linkage vector and a flux linkage given vector of the motor and a coordinate transformation principle;
calculating the area mark of the motor reference voltage vector according to the reference voltage vector of the motor in an a-b-c coordinate system, and selecting the required basic voltage vector by simplifying a switch table;
and generating a driving signal of each phase bridge arm switching device in the double inverter according to the preset switching state combination corresponding to each basic voltage vector so as to control the motor system.
Further, calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage, wherein the flux linkage vector comprises the following steps:
Figure BDA0002391750670000021
Figure BDA0002391750670000022
ψα＝∫(uα-Rsiα)dt
ψβ＝∫(uβ-Rsiβ)dt
wherein: u. ofα、uβStator voltages, u, of the motor's alpha and beta axes, respectivelyab、ubcLine voltages i between phases a and b and between phases b and c of the motor, respectivelyα、iβStator currents, i, of the motor's alpha and beta axes, respectivelya～icThree-phase stator currents of the electric machine, psiα、ΨβFlux linkage, R, of the motor's alpha and beta axes, respectivelysIs the stator resistance of the motor.
Further, calculating a flux linkage given vector according to the rotor position angle comprises:
θr＝np×θr0
θδ＝arcsin(kp(ωr_ref-ωr)+ki∫(ωr_ref-ωr)dt)
ψα_ref＝|ψs_ref|·cos(θδ+θr)
ψβ_ref＝|ψs_ref|·sin(θδ+θr)
wherein: thetarIs the rotor electrical angle of the motor, npIs the number of pole pairs, θ, of the motorr0Is the rotor position angle, θδIs the power angle, omega, of the motorr_refFor a given speed of rotation, ω, of the motorrIs the rotational speed of the motor, kpIs a proportionality coefficient, kiIs an integral coefficient, Ψα_ref、Ψβ_refFor the flux linkage of the alpha and beta axes of the motor, a vector is given, psis_refAnd setting the stator flux linkage value of the motor.
Further, calculating a reference voltage vector of the motor in an alpha-beta coordinate system, comprising:
Vα_ref＝(ψα_ref-ψα)/Ts+Rsiα
Vβ_ref＝(ψβ_ref-ψβ)/Ts+Rsiβ
wherein: vα_ref、Vβ_refReference voltages for the alpha and beta axes of the motor, Ψα_ref、Ψβ_refBy a given amount, psi, for the flux linkage of the motor's alpha and beta axesα、ΨβIs the flux linkage of the alpha axis and the beta axis of the motor, TsIs the sampling period of the system, RsIs the stator resistance of the motor, iα、iβThe stator currents of the alpha axis and the beta axis of the motor.
Further, calculating a reference voltage vector of the motor under an a-b-c coordinate system, comprising:
Figure BDA0002391750670000031
wherein: va_ref、Vb_ref、Vc_refReference voltages V of three phases of the motor in an a-b-c coordinate systemα_ref、Vβ_refReference voltages for the alpha and beta axes of the motor.
Further, calculating a zone flag of the motor reference voltage vector, comprising:
Figure BDA0002391750670000032
wherein: x represents one of three abc phases, i.e. x ═ a, b, c, VdcIs the sum of the dc voltages of the two dc voltage sources.
Further, the required basic voltage vector is selected by simplifying a switch table, and the method comprises the following steps:
the selected basic voltage vector is obtained from table 1:
TABLE 1
Figure BDA0002391750670000033
Figure BDA0002391750670000041
Wherein: v. ofm(m ═ 1,2,3,. and 19) respectively represent at Vdc1＝Vdc2In the case of open-winding permanent-magnet synchronous machines, 19 basic voltage vectors, where Vdc1、Vdc2The voltages of the two dc voltage sources, respectively, "/" indicates that the corresponding zone-mark combination is not present in the space voltage vector plane.
Further, the combination of the switch states corresponding to each preset basic voltage vector includes:
the switching state combination corresponding to the preset basic voltage vector is obtained through table 2:
TABLE 2
Figure BDA0002391750670000042
Wherein: sa1Sb1Sc1-Sa2Sb2Sc2The states of the switching devices in six bridge arms of the double-inverter are shown, if the switching device of the upper bridge arm is conducted, S is equal to 1, and if the switching device of the lower bridge arm is conducted, S is equal to 0.
In a second aspect, an embodiment of the present invention provides a direct torque control apparatus for an open-winding permanent magnet synchronous motor system, including:
the acquisition module is used for acquiring three-phase stator current, line voltage and a rotor position angle of the motor and differentiating the rotor position angle to obtain the rotating speed of the motor;
the first calculation module is used for calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage and calculating a flux linkage given vector according to the rotor position angle;
the second calculation module is used for calculating reference voltage vectors of the motor in an alpha-beta coordinate system and an a-b-c coordinate system respectively according to the flux linkage vector and the flux linkage given vector of the motor and a coordinate transformation principle;
the table look-up module is used for calculating the area mark of the motor reference voltage vector according to the reference voltage vector of the motor in the a-b-c coordinate system and selecting the required basic voltage vector by simplifying a switch table;
and the driving signal generating module is used for generating driving signals of the switching devices of the bridge arms of each phase in the double inverter according to the preset switching state combination corresponding to each basic voltage vector so as to control the motor system.
According to the embodiment of the invention, the projection of the basic voltage vector in three phases abc is used for dividing the space voltage vector plane, and the concept of the area mark is introduced, so that the selection of the basic voltage vector is realized, the switching state of each bridge arm is obtained to generate the driving signal of each switching device, the control is applied to the motor system, and the whole control structure is simpler; the control algorithm eliminates a hysteresis comparator required in the traditional structure, simplifies a switching table, improves the precision of the selected voltage vector, and has low torque ripple and flux linkage ripple of the motor, thereby improving the static running performance of a motor system.
Drawings
The accompanying drawings, which are included to provide a further understanding of the invention and are incorporated in and constitute a part of this application, illustrate embodiment(s) of the invention and together with the description serve to explain the invention without limiting the invention. In the drawings:
fig. 1 is a schematic structural diagram of a typical double-independent-power-supply type open-winding permanent magnet synchronous motor system applied to the embodiment of the invention;
FIG. 2 is a flow chart of a method of direct torque control of an open-winding permanent magnet synchronous motor system according to an embodiment of the present invention;
FIG. 3 is a control block diagram of a direct torque control method of an open-winding permanent magnet synchronous motor system according to an embodiment of the present invention;
FIG. 4 is a sector division diagram of a space voltage vector plane;
FIG. 5 is a block diagram of an experimental platform of a 1.3kw dual-independent power supply type open winding permanent magnet synchronous motor system;
FIG. 6 is a waveform diagram of an experiment during steady-state operation of the system under the control method of the present invention;
FIG. 7 is a waveform diagram of a system mutation speed setting experiment under the control method of the present invention;
fig. 8 is a schematic structural diagram of a direct torque control device of an open-winding permanent magnet synchronous motor system according to an embodiment of the invention.
Detailed Description
In order to make the technical solutions of the present invention better understood, the technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
It should be noted that the terms "comprises" and "comprising," and any variations thereof, in the description and claims of the present invention and the above-described drawings, are intended to cover a non-exclusive inclusion, such that a process, method, system, article, or apparatus that comprises a list of steps or elements is not necessarily limited to those steps or elements expressly listed, but may include other steps or elements not expressly listed or inherent to such process, method, article, or apparatus.
In accordance with an embodiment of the present invention, there is provided an embodiment of a method for direct torque control of an open-winding permanent magnet synchronous machine system, wherein the steps illustrated in the flowchart of the figure may be performed in a computer system, such as a set of computer executable instructions, and wherein, although a logical order is illustrated in the flowchart, in some cases, the steps illustrated or described may be performed in an order different than that illustrated herein.
FIG. 1 is a typical dual independent power type open-winding permanent magnet synchronous motor system structure applicable to the embodiment of the present invention, which includes an open-winding permanent magnet synchronous motor 1 and two three-phase six switchesInverters 2 and 3, in which the DC voltages of the two inverters are equal, i.e. Vdc1＝Vdc2。
FIG. 2 is a flow chart of a method of direct torque control of an open-winding permanent magnet synchronous motor system according to an embodiment of the present invention; FIG. 3 is a control block diagram of a direct torque control method of an open-winding permanent magnet synchronous motor system according to an embodiment of the present invention; as shown in fig. 2, the method comprises the steps of:
step S101, collecting three-phase stator current, line voltage and rotor position angle of a motor, and differentiating the rotor position angle to obtain the rotating speed of the motor;
step S102, calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage, and calculating a flux linkage given vector according to the rotor position angle;
step S103, respectively calculating reference voltage vectors of the motor in an alpha-beta coordinate system and an a-b-c coordinate system according to a flux linkage vector and a flux linkage given vector of the motor and a coordinate transformation principle;
step S104, calculating the area mark of the motor reference voltage vector according to the reference voltage vector of the motor in the a-b-c coordinate system, and selecting the required basic voltage vector through a simplified switch table;
and step S105, generating driving signals of the switching devices of the bridge arms of each phase in the double inverter according to the preset switching state combination corresponding to each basic voltage vector for controlling the motor system.
According to the embodiment of the invention, the projection of the basic voltage vector in three phases abc is used for dividing the space voltage vector plane, and the concept of the area mark is introduced, so that the selection of the basic voltage vector is realized, the switching state of each bridge arm is obtained to generate the driving signal of each switching device, the control is applied to the motor system, and the whole control structure is simpler; the control algorithm eliminates a hysteresis comparator required in the traditional structure, simplifies a switching table, improves the precision of the selected voltage vector, and has low torque ripple and flux linkage ripple of the motor, thereby improving the static running performance of a motor system.
As shown in fig. 3, the method comprises the steps of:
according to the embodiment of the invention, the three-phase stator current, the line voltage and the rotor position angle of the motor are collected, and the rotor position angle is differentiated to obtain the motor rotating speed, which specifically comprises the following steps:
three-phase current sensor 3-1 is used for collecting three-phase stator current signals i of open-winding permanent magnet synchronous motor 1a～icThe stator line voltage u of the open winding permanent magnet synchronous motor 1 is collected by a voltage sensor 3-2ab、ubcAnd the encoder 3-3 measures the rotor angle theta of the permanent magnet synchronous motor 1r0And obtaining the rotor electrical angular velocity omega by the rotor position angle through a d/dt differentiatorrElectric angle of rotor thetarCan be calculated by the following formula:
θr＝np×θr0
wherein: n ispIs the number of pole pairs of the motor.
According to the embodiment of the invention, the flux linkage vector of the motor is calculated according to the three-phase stator current and the line voltage, and the flux linkage given vector is calculated according to the rotor position angle, which is as follows:
to connect the stator line voltage uab、ubcAnd three-phase stator current ia～icThe voltage vector u of the motor under an alpha-beta coordinate system is obtained through coordinate transformation after the input into a Clark transformation module 4αβAnd stator current vector iαβThe calculation formula is as follows:
Figure BDA0002391750670000071
Figure BDA0002391750670000072
will voltage vector uαβAnd stator current vector iαβThe input stator flux linkage calculation module 5 obtains a flux linkage vector psi of the motorαβThe calculation formula is as follows:
ψα＝∫(uα-Rsiα)dt
ψβ＝∫(uβ-Rsiβ)dt
wherein: u. ofα、uβStator voltages, u, of the motor's alpha and beta axes, respectivelyab、ubcLine voltages i between phases a and b and between phases b and c of the motor, respectivelyα、iβStator currents, i, of the motor's alpha and beta axes, respectivelya～icThree-phase stator currents of the electric machine, psiα、ΨβFlux linkage, R, of the motor's alpha and beta axes, respectivelysIs the stator resistance of the motor.
Given speed of rotation omegar_refWith the motor speed omegarInputting the sine value sin theta of the power angle of the motor obtained by the PI regulator module 6δThen obtaining the motor power angle theta through arc tangent treatmentδThe calculation formula is as follows:
θδ＝arcsin(kp(ωr_ref-ωr)+ki∫(ωr_ref-ωr)dt)
wherein: thetaδIs the power angle, omega, of the motorr_refFor a given speed of rotation, ω, of the motorrIs the rotational speed of the motor, kpIs a proportionality coefficient, kiIs an integral coefficient.
Given value psi of magnetic flux linkages_refAngle theta of motorδAnd rotor electrical angle thetarInput into a given flux linkage calculation module 7 to obtain a given flux linkage vector psiαβ_refThe calculation formula is as follows:
ψα_ref＝|ψs_ref|·cos(θδ+θr)
ψβ_ref＝|ψs_ref|·sin(θδ+θr)
wherein: wherein: thetarIs the rotor electrical angle of the motor, npIs the number of pole pairs, θ, of the motorr0Is the rotor position angle, θδIs the power angle of the motorα_ref、Ψβ_refFor the flux linkage of the alpha and beta axes of the motor, a vector is given, psis_refAnd setting the stator flux linkage value of the motor.
According to the above embodiment of the present invention, the reference voltage vectors of the motor in the α - β coordinate system and the a-b-c coordinate system are calculated according to the flux linkage vector and the flux linkage given vector of the motor and the coordinate transformation principle, specifically as follows:
will give the flux linkage vector Ψαβ_refWith flux linkage vector ΨαβThe difference is input into a reference voltage vector calculation module 8 to obtain a reference voltage vector V of the motor under an alpha-beta coordinate systemαβ_refThe required formula is as follows:
Vα_ref＝(ψα_ref-ψα)/Ts+Rsiα
Vβ_ref＝(ψβ_ref-ψβ)/Ts+Rsiβ
wherein: vα_ref、Vβ_refReference voltages for the alpha and beta axes of the motor, Ψα_ref、Ψβ_refBy a given amount, psi, for the flux linkage of the motor's alpha and beta axesα、ΨβIs the flux linkage of the alpha axis and the beta axis of the motor, TsIs the sampling period of the system, RsIs the stator resistance of the motor, iα、iβThe stator currents of the alpha axis and the beta axis of the motor.
A reference voltage vector V under an alpha-beta coordinate systemαβ_refInputting the Clark inverse transformation module 9 to obtain a reference voltage vector V under an a-b-c coordinate systemabc_refThe required formula is as follows:
Figure BDA0002391750670000091
wherein: va_ref、Vb_ref、Vc_refReference voltages V of three phases of the motor in an a-b-c coordinate systemα_ref、Vβ_refReference voltages for the alpha and beta axes of the motor.
According to the above embodiment of the present invention, the area flag of the reference voltage vector of the motor is calculated according to the reference voltage vector of the motor in the a-b-c coordinate system, and the required basic voltage vector is selected by simplifying the switch table, specifically:
reference voltage vector Vabc_refInputting the signals into the switching signal generation module 10, fig. 4 is a sector division diagram of space voltage vector, and the region mark R of the motor reference voltage vector is obtained by calculationabcThe required formula is as follows:
Figure BDA0002391750670000092
wherein: x represents one of three abc phases, i.e. x ═ a, b, c, VdcIs the sum of the DC voltages of two DC voltage sources
According to the above embodiment of the present invention, the driving signals of the switching devices of the bridge arms in each phase in the dual inverter are generated according to the preset switching state combination corresponding to each basic voltage vector, so as to apply control to the motor system, specifically:
region index R based on motor reference voltage vectorabcThe desired basic voltage vector is selected by table 1:
TABLE 1
Figure BDA0002391750670000093
The switching state combination corresponding to the preset basic voltage vector is obtained through table 2:
TABLE 2
Figure BDA0002391750670000101
To verify the effectiveness of the control method according to the embodiment of the present invention, experimental verification studies are performed on the experimental platform shown in fig. 5, the experimental parameters are shown in table 3, and the control period of the system is set to 0.0001 s.
TABLE 3
Figure BDA0002391750670000102
Fig. 6 shows experimental waveforms of the motor in steady-state operation with a speed band of 750rpm and a load of 3Nm, where the waveforms are, from top to bottom, the motor speed, the electromagnetic torque, the flux linkage amplitude and the a-phase stator current, and it can be seen that the motor operates smoothly, the torque and flux linkage amplitude have small pulsation, and the stator current is sinusoidal.
Fig. 7 shows a sudden change in the speed setting, where the speed setting is stepped from 500rpm to 1000rpm and the motor is running without load, it can be seen that the motor speed follows the speed setting within 0.65 s.
The present invention also provides an embodiment of a direct torque control device of an open-winding permanent magnet synchronous motor system, configured to perform a direct torque control method of the open-winding permanent magnet synchronous motor system, and fig. 8 is a schematic structural diagram of the direct torque control device of the open-winding permanent magnet synchronous motor system according to the embodiment of the present invention, where the direct torque control device includes:
the acquisition module 91 is used for acquiring three-phase stator current, line voltage and rotor position angle of the motor and differentiating the rotor position angle to obtain the rotating speed of the motor;
the first calculation module 92 is used for calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage and calculating a flux linkage given vector according to the rotor position angle;
the second calculating module 93 is used for calculating reference voltage vectors of the motor in an alpha-beta coordinate system and an a-b-c coordinate system respectively according to the flux linkage vector and the flux linkage given vector of the motor and a coordinate transformation principle;
the table look-up module 94 is used for calculating the area mark of the motor reference voltage vector according to the reference voltage vector of the motor in the a-b-c coordinate system and selecting the required basic voltage vector by simplifying a switch table;
and a driving signal generating module 95, configured to generate a driving signal of each phase bridge arm switching device in the dual inverter according to a preset switching state combination corresponding to each basic voltage vector, so as to control the motor system.
The above-mentioned serial numbers of the embodiments of the present invention are merely for description and do not represent the merits of the embodiments.
In the above embodiments of the present invention, the descriptions of the respective embodiments have respective emphasis, and for parts that are not described in detail in a certain embodiment, reference may be made to related descriptions of other embodiments.
In the embodiments provided in the present application, it should be understood that the disclosed technology can be implemented in other ways. The above-described embodiments of the apparatus are merely illustrative, and for example, the division of the units may be a logical division, and in actual implementation, there may be another division, for example, multiple units or components may be combined or integrated into another system, or some features may be omitted, or not executed. In addition, the shown or discussed mutual coupling or direct coupling or communication connection may be an indirect coupling or communication connection through some interfaces, units or modules, and may be in an electrical or other form.
The units described as separate parts may or may not be physically separate, and parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of units. Some or all of the units can be selected according to actual needs to achieve the purpose of the solution of the embodiment.
In addition, functional units in the embodiments of the present invention may be integrated into one processing unit, or each unit may exist alone physically, or two or more units are integrated into one unit. The integrated unit can be realized in a form of hardware, and can also be realized in a form of a software functional unit.
The integrated unit, if implemented in the form of a software functional unit and sold or used as a stand-alone product, may be stored in a computer readable storage medium. Based on such understanding, the technical solution of the present invention may be embodied in the form of a software product, which is stored in a storage medium and includes instructions for causing a computer device (which may be a personal computer, a server, or a network device) to execute all or part of the steps of the method according to the embodiments of the present invention. And the aforementioned storage medium includes: a U-disk, a Read-Only Memory (ROM), a Random Access Memory (RAM), a removable hard disk, a magnetic or optical disk, and other various media capable of storing program codes.
The embodiments described above are presented to enable a person having ordinary skill in the art to make and use the invention. It will be readily apparent to those skilled in the art that various modifications to the above-described embodiments may be made, and the generic principles defined herein may be applied to other embodiments without the use of inventive faculty. Therefore, the present invention is not limited to the above embodiments, and those skilled in the art should make improvements and modifications to the present invention based on the disclosure of the present invention within the protection scope of the present invention.

Claims (6)

1. A direct torque control method of an open-winding permanent magnet synchronous motor system is characterized by comprising the following steps:
collecting three-phase stator current, line voltage and rotor position angle of the motor, and differentiating the rotor position angle to obtain the rotating speed of the motor;
calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage, and calculating a flux linkage given vector according to the rotor position angle;
respectively calculating reference voltage vectors of the motor in an alpha-beta coordinate system and an a-b-c coordinate system according to a flux linkage vector and a flux linkage given vector of the motor and a coordinate transformation principle;
calculating the area mark of the motor reference voltage vector according to the reference voltage vector of the motor in an a-b-c coordinate system, and selecting the required basic voltage vector by simplifying a switch table;
generating a driving signal of each phase bridge arm switching device in the double inverter according to a preset switching state combination corresponding to each basic voltage vector so as to control a motor system;
wherein calculating the zone flags for the motor reference voltage vector comprises:
Figure FDA0003091087960000011
wherein: x represents one of three abc phases, i.e. x ═ a, b, c, VdcIs the sum of the direct current voltages of two direct current voltage sources;
wherein the selection of the desired basic voltage vector by the reduced switching table comprises:
the selected basic voltage vector is obtained from table 1:
TABLE 1
Figure FDA0003091087960000012
Wherein: v. ofm(m ═ 1,2,3,. and 19) respectively represent at Vdc1＝Vdc2In the case of open-winding permanent-magnet synchronous machines, 19 basic voltage vectors, where Vdc1、Vdc2The voltages of two direct current voltage sources respectively, "/" indicates that the corresponding area sign combination does not exist in the space voltage vector plane;
the combination of the switch states corresponding to each preset basic voltage vector comprises:
the switching state combination corresponding to the preset basic voltage vector is obtained through table 2:
TABLE 2
Figure FDA0003091087960000021
Wherein: sa1Sb1Sc1-Sa2Sb2Sc2The states of the switching devices in six bridge arms of the double-inverter are shown, if the switching device of the upper bridge arm is conducted, S is equal to 1, and if the switching device of the lower bridge arm is conducted, S is equal to 0.
2. The direct torque control method of an open-winding permanent magnet synchronous motor system according to claim 1, wherein calculating a flux linkage vector of the motor from three-phase stator currents and line voltages comprises:
Figure FDA0003091087960000022
Figure FDA0003091087960000031
ψα＝∫(uα-Rsiα)dt
ψβ＝∫(uβ-Rsiβ)dt
wherein: u. ofα、uβStator voltages, u, of the motor's alpha and beta axes, respectivelyab、ubcLine voltages i between phases a and b and between phases b and c of the motor, respectivelyα、iβStator currents, i, of the motor's alpha and beta axes, respectivelya～icThree-phase stator currents of the electric machine, psiα、ΨβFlux linkage, R, of the motor's alpha and beta axes, respectivelysIs the stator resistance of the motor.
3. The direct torque control method of an open-winding permanent magnet synchronous motor system according to claim 1, wherein calculating a flux linkage given vector according to a rotor position angle comprises:
θr＝np×θr0
θδ＝arcsin(kp(ωr_ref-ωr)+ki∫(ωr_ref-ωr)dt)
ψα_ref＝|ψs_ref|·cos(θδ+θr)
ψβ_ref＝|ψs_ref|·sin(θδ+θr)
wherein: thetarIs the rotor electrical angle of the motor, npIs the number of pole pairs, θ, of the motorr0Is the rotor position angle, θδIs the power angle, omega, of the motorr_refFor a given speed of rotation, ω, of the motorrIs the rotational speed of the motor, kpIs a proportionality coefficient, kiIs an integral coefficient, Ψα_ref、Ψβ_refFor the flux linkage of the alpha and beta axes of the motor, a vector is given, psis_refAnd setting the stator flux linkage value of the motor.
4. The direct torque control method of the open-winding permanent magnet synchronous motor system according to claim 1, wherein calculating the reference voltage vector of the motor in an α - β coordinate system comprises:
Vα_ref＝(ψα_ref-ψα)/Ts+Rsiα
Vβ_ref＝(ψβ_ref-ψβ)/Ts+Rsiβ
wherein: vα_ref、Vβ_refReference voltages for the alpha and beta axes of the motor, Ψα_ref、Ψβ_refBy a given amount, psi, for the flux linkage of the motor's alpha and beta axesα、ΨβIs the flux linkage of the alpha axis and the beta axis of the motor, TsIs the sampling period of the system, RsIs the stator resistance of the motor, iα、iβThe stator currents of the alpha axis and the beta axis of the motor.
5. The direct torque control method of the open-winding permanent magnet synchronous motor system according to claim 1, wherein calculating the reference voltage vector of the motor in an a-b-c coordinate system comprises:
Figure FDA0003091087960000041
wherein: va_ref、Vb_ref、Vc_refReference voltages V of three phases of the motor in an a-b-c coordinate systemα_ref、Vβ_refReference voltages for the alpha and beta axes of the motor.
6. A direct torque control device for an open-winding permanent magnet synchronous motor system, comprising:
the acquisition module is used for acquiring three-phase stator current, line voltage and a rotor position angle of the motor and differentiating the rotor position angle to obtain the rotating speed of the motor;
the first calculation module is used for calculating a flux linkage vector of the motor according to the three-phase stator current and the line voltage and calculating a flux linkage given vector according to the rotor position angle;
the second calculation module is used for calculating reference voltage vectors of the motor in an alpha-beta coordinate system and an a-b-c coordinate system respectively according to the flux linkage vector and the flux linkage given vector of the motor and a coordinate transformation principle;
the table look-up module is used for calculating the area mark of the motor reference voltage vector according to the reference voltage vector of the motor in the a-b-c coordinate system and selecting the required basic voltage vector by simplifying a switch table;
the driving signal generating module is used for generating driving signals of the switching devices of the bridge arms of each phase in the double inverter according to the preset switching state combination corresponding to each basic voltage vector so as to control the motor system;
wherein calculating the zone flags for the motor reference voltage vector comprises:
Figure FDA0003091087960000042
wherein: x represents one of three abc phases, i.e. x ═ a, b, c, VdcIs the sum of the direct current voltages of two direct current voltage sources;
wherein the selection of the desired basic voltage vector by the reduced switching table comprises:
the selected basic voltage vector is obtained from table 1:
TABLE 1
Figure FDA0003091087960000051
Wherein: v. ofm(m ═ 1,2,3,. and 19) respectively represent at Vdc1＝Vdc2In the case of open-winding permanent-magnet synchronous machines, 19 basic voltage vectors, where Vdc1、Vdc2The voltages of two direct current voltage sources respectively, "/" indicates that the corresponding area sign combination does not exist in the space voltage vector plane;
the combination of the switch states corresponding to each preset basic voltage vector comprises:
the switching state combination corresponding to the preset basic voltage vector is obtained through table 2:
TABLE 2
Figure FDA0003091087960000052
Wherein: sa1Sb1Sc1-Sa2Sb2Sc2The states of the switching devices in six bridge arms of the double-inverter are shown, if the switching device of the upper bridge arm is conducted, S is equal to 1, and if the switching device of the lower bridge arm is conducted, S is equal to 0.
CN202010116830.6A 2020-02-25 2020-02-25 Direct torque control method and device for open-winding permanent magnet synchronous motor system Active CN111181465B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202010116830.6A CN111181465B (en) 2020-02-25 2020-02-25 Direct torque control method and device for open-winding permanent magnet synchronous motor system

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202010116830.6A CN111181465B (en) 2020-02-25 2020-02-25 Direct torque control method and device for open-winding permanent magnet synchronous motor system

Publications (2)

Publication Number Publication Date
CN111181465A CN111181465A (en) 2020-05-19
CN111181465B true CN111181465B (en) 2021-07-20

Family

ID=70654924

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202010116830.6A Active CN111181465B (en) 2020-02-25 2020-02-25 Direct torque control method and device for open-winding permanent magnet synchronous motor system

Country Status (1)

Country Link
CN (1) CN111181465B (en)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP7467301B2 (en) * 2020-09-18 2024-04-15 株式会社東芝 Open winding motor drive device and refrigeration cycle device
CN112468041A (en) * 2021-01-28 2021-03-09 四川大学 Diode clamping based double three-phase open winding permanent magnet synchronous generator system
CN115158100A (en) * 2022-06-29 2022-10-11 东风汽车集团股份有限公司 Control method of battery self-heating system

Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101383582A (en) * 2008-10-15 2009-03-11 南京航空航天大学 Electric excitation synchronous motor control method based on torque angle sine value linear control
CN101383546A (en) * 2008-10-15 2009-03-11 南京航空航天大学 Torque angle sine value linear controlled pole hidden type permanent magnet synchronous motor controlling method
CN103281026A (en) * 2013-05-22 2013-09-04 浙江大学 Control method of open winding permanent magnet synchronous motor system of hybrid inverter
CN108258967A (en) * 2018-02-27 2018-07-06 江苏大学 A kind of magneto based on novel flux observer is without position Direct Torque Control
CN109495049A (en) * 2018-11-29 2019-03-19 江苏大学 Permanent magnetism vernier motor unity power factor Direct Torque Control based on striding capacitance
CN110212839A (en) * 2019-07-01 2019-09-06 台州学院 It is a kind of to eliminate the model prediction Direct Torque Control for opening winding electric machine common-mode voltage influences
CN110350836A (en) * 2019-06-28 2019-10-18 浙江大学 Common DC bus type opens the improvement Direct Torque Control of winding permanent magnet synchronous motor system

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101383582A (en) * 2008-10-15 2009-03-11 南京航空航天大学 Electric excitation synchronous motor control method based on torque angle sine value linear control
CN101383546A (en) * 2008-10-15 2009-03-11 南京航空航天大学 Torque angle sine value linear controlled pole hidden type permanent magnet synchronous motor controlling method
CN103281026A (en) * 2013-05-22 2013-09-04 浙江大学 Control method of open winding permanent magnet synchronous motor system of hybrid inverter
CN108258967A (en) * 2018-02-27 2018-07-06 江苏大学 A kind of magneto based on novel flux observer is without position Direct Torque Control
CN109495049A (en) * 2018-11-29 2019-03-19 江苏大学 Permanent magnetism vernier motor unity power factor Direct Torque Control based on striding capacitance
CN110350836A (en) * 2019-06-28 2019-10-18 浙江大学 Common DC bus type opens the improvement Direct Torque Control of winding permanent magnet synchronous motor system
CN110212839A (en) * 2019-07-01 2019-09-06 台州学院 It is a kind of to eliminate the model prediction Direct Torque Control for opening winding electric machine common-mode voltage influences

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
Multilevel Torque Hysteresis-Band Based Direct-Torque Control Strategy for a Three-Level Open-End Winding Induction Motor Drive for Electric Vehicle Applications;Suresh Lakhimsetty等;《IEEE Journal of Emerging and Selected Topics in Power Electronics》;20190930;第7卷(第3期);第1969-1981页 *
Reduction of Torque and Flux Ripples in Space Vector Modulation-Based Direct Torque Control of Asymmetric Permanent Magnet Synchronous Machine;Atheer H等;《IEEE Transactions on Power Electronics》;20170430;第32卷(第4期);第2976-2986页 *

Also Published As

Publication number Publication date
CN111181465A (en) 2020-05-19

Similar Documents

Publication Publication Date Title
CN108306571B (en) Five-phase permanent magnet linear motor one-phase open-circuit fault-tolerant direct thrust control method
CN111181465B (en) Direct torque control method and device for open-winding permanent magnet synchronous motor system
CN108964547B (en) Fault-tolerant control method for two-phase open-circuit fault of five-phase permanent magnet synchronous motor
Xia et al. A novel direct torque and flux control method of matrix converter-fed PMSM drives
Hua et al. Multivector-based model predictive control with geometric solution of a five-phase flux-switching permanent magnet motor
CN112290859B (en) Five-phase permanent magnet motor short-circuit fault-tolerant control method adopting dead-beat current tracking
CN104184380A (en) One-phase-failure fault-tolerant torque control method of 60-degree offset six-phase permanent magnet synchronous motor
CN109347386B (en) SVPWM-based five-phase permanent magnet motor maximum torque current ratio fault-tolerant control method
Cheng et al. Model predictive current control for an open-winding PMSM system with a common DC bus in 3-D space
Sun et al. Virtual current compensation-based quasi-sinusoidal-wave excitation scheme for switched reluctance motor drives
CN108574442B (en) Six-phase motor direct torque control system and control method thereof
CN108574439B (en) Space vector control method for fault-tolerant system of permanent magnet synchronous motor
CN110829926B (en) SVPWM fault-tolerant control method and device for five-phase permanent magnet fault-tolerant motor
Wang et al. Improved fault-tolerant model predictive torque control of five-phase PMSM by using deadbeat solution
CN111654224A (en) Fault-tolerant control method for five-phase permanent magnet synchronous motor under three-phase open circuit fault
Zheng et al. Analysis and fault-tolerant control for dual-three-phase PMSM based on virtual healthy model
CN110350836B (en) Direct torque control method of common direct current bus type open winding permanent magnet synchronous motor system
CN116191982A (en) SVPWM modulation strategy of single-winding five-phase bearingless permanent magnet motor
CN112260605B (en) Direct torque control method for one-phase-lacking fault of five-phase permanent magnet synchronous motor
Zhang et al. A novel 3-D space vector modulation strategy for open-end winding PMSM
CN114400945A (en) Phase-loss fault-tolerant operation hybrid control method for double three-phase permanent magnet synchronous motor
CN108574438A (en) A kind of striding capacitance opens the inverter open circuit hybrid modulation fault tolerant control method of winding three-phase permanent magnet synchronous motor
CN116827210A (en) Three-dimensional space vector modulation method for open-winding motor
CN113141139B (en) Five-closed-loop control method and system for double three-phase permanent magnet motor
Zhou et al. Switching-Table-Based Diagnosis-Free Fault-Tolerant DTC for Five-Phase PMSM With Any Phase Open-Circuit Fault

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant