CN111181379B - Reverse winding design method for common-mode EMI suppression of Boost circuit - Google Patents

Reverse winding design method for common-mode EMI suppression of Boost circuit Download PDF

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CN111181379B
CN111181379B CN202010076538.6A CN202010076538A CN111181379B CN 111181379 B CN111181379 B CN 111181379B CN 202010076538 A CN202010076538 A CN 202010076538A CN 111181379 B CN111181379 B CN 111181379B
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winding
frequency
reverse
boost circuit
reverse phase
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CN111181379A (en
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林苏斌
周云
吴钦伟
陆文韬
陈为
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Fuzhou University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H02M1/123—Suppression of common mode voltage or current
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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Abstract

The invention provides aA method for designing an inverted winding for suppressing common-mode EMI (electro-magnetic interference) of a Boost circuit is characterized in that a Boost inductor of an additional inverted winding is regarded as a double-winding transformer, and a transformer high-frequency model is established for the double-winding transformer on the premise of considering parasitic parameters; evaluating the common-mode EMI inhibition capability of the Boost circuit by using insertion loss; in the experimental measurement of noise measurement, the total earth distributed capacitance Ca of a switching tube of a Boost circuit is solved by inserting a passive device with known impedance into a noise measurement circuit, and the key frequency point of an insertion loss curve is usedf 1 、f c 、f 2 For design basis, the total earth distributed capacitance Ca of the switching tube of the Boost circuit is solved, and the compensation capacitance C of the reverse phase winding is further obtainedBThe selection principle, the winding method of the reverse phase winding and the method for selecting the optimal turn number of the reverse phase winding; the invention provides an optimal method for reasonably designing relevant parameters of the reverse phase winding and inhibiting common mode noise of a Boost circuit.

Description

Reverse winding design method for common-mode EMI suppression of Boost circuit
Technical Field
The invention relates to the technical field of electronics, in particular to a design method of an inverted winding for suppressing common-mode EMI (electro-magnetic interference) of a Boost circuit.
Background
With the widespread use of switching power supplies in electronic devices, their high frequency switching characteristics cause serious electromagnetic interference (EMI) problems. The EMI is divided into differential mode interference and common mode interference, and the electromagnetic noise of the common mode interference is generated by forming a displacement current in a ground loop in an electric field coupling manner through a distributed capacitance between a conductor or device with potential variation and a grounding conductor with zero potential in a circuit. The EMI filter is a key component in the switching power supply, and in order to suppress common mode noise in a low frequency band, the size of the filter used is usually large, which affects improvement of power density of the switching power supply. In order to suppress harmonic interference, a Power Factor Correction (PFC) technology is widely used, a Boost PFC circuit has a simple structure and is simple and convenient to design, and is the most common PFC circuit topology, and the electromagnetic compatibility problem of the Boost PFC circuit is also widely paid attention by design researchers.
The Boost inductor is generally a customized non-standard device, is influenced by a structure and a process, has complex stray parameters, and is a key device influencing the EMI (electro-magnetic interference) characteristic of a PFC (power factor correction) circuit. The Boost inductor is designed in a targeted manner, the electromagnetic compatibility characteristic of the Boost inductor is improved, and the electromagnetic interference of the switching power supply can be effectively reduced. The construction of the balancing circuit and the construction of the inverting winding are the main schemes for suppressing the electromagnetic interference of the PFC circuit from the circuit. The method for constructing the balanced circuit adds an inductor or a capacitor into a branch of the circuit to enable a common mode noise path of the circuit to reach a balanced state, and noise current does not flow through a Linear Impedance Stabilization Network (LISN). The method is used for connecting devices in series in a power loop, and the original electrical performance can be changed. The reverse phase winding method is to introduce a reverse phase noise source to a coupled reverse phase compensation winding of a power inductor structure on the premise of not changing the basic electrical performance of a circuit, so as to realize the offset of common mode noise.
The existing design method of the reverse phase winding ignores the influence of parasitic parameters between the Boost inductor and the reverse phase winding, and the Boost inductor of the additional reverse phase winding is regarded as an ideal transformer. However, as the frequency increases, the influence of the parasitic parameters increases significantly, affecting the noise suppression effect of the inverter winding on the Boost circuit.
Disclosure of Invention
The invention provides a design method of an inverted winding for suppressing common-mode EMI of a Boost circuit, and provides an optimal method for reasonably designing relevant parameters of the inverted winding and suppressing common-mode noise of the Boost circuit.
The invention adopts the following technical scheme.
A reverse phase winding design method for common mode EMI suppression of a Boost circuit is characterized in that the reverse phase winding is wound on a PFC inductor of the Boost circuit, and in the design of the reverse phase winding, the Boost inductor with the additional reverse phase winding is regarded as a double-winding transformerEstablishing a transformer high-frequency model for the double-winding transformer under the premise of considering parasitic parameters; evaluating the common-mode EMI inhibition capability of the Boost circuit by using insertion loss; in the experimental measurement of noise measurement, the total earth distributed capacitance C of a switching tube of a Boost circuit is solved by inserting a passive device with known impedance into a noise measurement circuitAAnd at the critical frequency point f of the insertion loss curve1、fc、f2For design basis, the total earth distributed capacitance C of the switching tube of the Boost circuit is solvedAFurther obtain the compensation capacitance C of the reverse phase windingBThe selection principle, the winding method of the reverse phase winding and the method for selecting the optimal turn number of the reverse phase winding.
The total ground capacitance C of the switching tube of the Boost circuit is obtained by the experimental measurement methodAThe method comprises a step A1, wherein the step A1 is as follows:
the first step is as follows: measuring original common mode noise to obtain noise current i1；
The second step is that: inserting a passive device of known impedance, Zstd1To obtain a noise current i2；
The third step: inserting a passive device of known impedance, Zstd2To obtain a noise current i3；
……
By analogy, forming an insertion loss curve of the high-frequency model of the transformer;
the passive device of the known impedance is connected between the potential action point A of the switching tube of the Boost circuit and the ground potential.
By controlling the low frequency resonance point f of the insertion loss curve1Crossing frequency point fcHigh frequency resonance point f2The frequency value of the phase-reversing winding is designed to design the parameters of the phase-reversing winding, so that the suppression effect of the phase-reversing winding on common-mode noise is the best; the reverse phase winding parameters comprise compensation capacitance, winding mode and optimal turn number.
Selecting compensation capacitor C of reverse phase winding by low-frequency common-mode noise suppression optimal principleBEven at a low frequency resonance point f1The frequency is lower than 150kHz, so that the common mode noise suppression effect of the reverse winding on the low frequency band of the Boost circuit is ensured to be the bestIt is preferred.
By selecting the compensating capacitor CBControlling the low frequency resonance point f1Then, it is necessary to increase the crossover frequency f as much as possiblecHigh frequency resonant frequency f2And the good common mode noise suppression effect of the inverter winding on the middle and high frequency bands of the Boost circuit is ensured.
After the Boost circuit is added with the reverse phase winding, the insertion loss is as follows:
Figure GDA0002993618770000031
Lmis the exciting inductance, L, of a transformerkLeakage inductance is adopted, and n is the turn ratio of the primary and secondary turns of the transformer, namely the turn ratio between the Boost inductance and the reverse winding; cBThe compensation capacitor is used for grounding the secondary side B point of the double-winding transformer; cADistributing capacitance for the A point to the ground; rLISNIs the common mode equivalent resistance of a Linear Impedance Stabilization Network (LISN). CssEffective capacitance C for representing primary and secondary common mode ports of transformerpsConverted to secondary side and secondary side capacitor CsThe equivalent capacitance after parallel connection; the smaller the insertion loss IL is, the better the suppression effect of the reverse phase winding on the common mode noise is shown;
when the reverse winding is wound on the Boost inductor, the leakage inductance L between the reverse winding and the Boost inductor is required to be ensuredkAs small as possible, thereby increasing fc、f2；
Therefore, when selecting the optimum number of turns of the reverse phase winding, λ of the reverse phase winding is made as large as possible, so that f is increasedc、f2；
Wherein
Figure GDA0002993618770000032
The noise suppression effect is best when the number of turns of the anti-phase winding is such that λ is maximum.
In the double-winding transformer, the number of turns of the reverse winding is far less than that of the Boost inductor, so that the double-winding transformer has a larger turn ratio n, and the compensation capacitor CBFar greater than CssAccording to (formula 2)The in-loss can be further expressed as:
Figure GDA0002993618770000033
solving the total capacitance to ground C of the switch tubeAWhen the temperature of the water is higher than the set temperature,
firstly, the common mode noise current of the Boost circuit is measured to obtain the original common mode noise current i1Comprises the following steps:
Figure GDA0002993618770000034
then, a known impedance Z is inserted between a potential moving point A of a switching tube of the Boost circuit and the groundstd1To obtain a noise current i2；
Figure GDA0002993618770000041
The total capacitance C of the switch tube to ground can be further solved by formula 4 and formula 5A。
In the design of the anti-phase winding by controlling f1、fc、f2The frequency value of (2) realizes the suppression of common mode noise; from equation 3, f1、fc、f2The expression for the three key frequency points is:
Figure GDA0002993618770000042
Figure GDA0002993618770000043
Figure GDA0002993618770000044
the compensation capacitor CBThe selection principle is to make the low frequency band commonPrinciple for optimum suppression of modal noise, i.e. by compensating capacitor CBMake the low frequency resonance point f1Is less than 150kHz, i.e.
Figure GDA0002993618770000045
Due to the resonance point f of the low-frequency band1Less than 150kHz, so the formula:
Figure GDA0002993618770000046
compensation capacitor CBCan be further simplified into
CB＝n·(1+Lk/Lm)CA(equation 10).
Selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAnd after the reverse phase winding is uniformly wound, the (formula 10) can be respectively substituted into the (formula 7) and the (formula 8), so as to obtain:
fc、f2the expression of (a) is as follows:
Figure GDA0002993618770000047
from the above formula, LkThe smaller, fc、f2The higher the frequency value of the phase-reversal winding is, the larger the effective noise suppression frequency band bandwidth of the phase-reversal winding is, and the better the noise suppression effect is; therefore, when winding the reverse winding, the leakage inductance L between the reverse winding and the Boost inductance should be ensuredkAt the minimum, the winding method is uniform winding and dense winding is avoided.
In the compensation capacitor CBAfter the winding mode is determined, the number of turns of the reverse phase winding and the leakage inductance L need to be comprehensively consideredkThe influence of (c). Selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAfter the reverse phase winding is uniformly wound, the (formula 1) can be substituted into the (formula 11) and the (formula 12), and f can be further substitutedc、f2The method is simplified as follows:
Figure GDA0002993618770000051
from the above, fc、f2Proportional to λ, the noise suppression effect is best when the number of turns of the anti-phase winding is such that λ is the greatest, and λ should be made the greatest when the number of turns of the anti-phase winding is chosen.
The invention provides an optimal method for reasonably designing relevant parameters of the phase-reversing winding and inhibiting common-mode noise of the Boost circuit.
Drawings
The invention is described in further detail below with reference to the following figures and detailed description:
FIG. 1a is a schematic diagram of a Boost circuit common mode noise path;
FIG. 1b is a schematic diagram of an equivalent model of common mode noise of a Boost circuit;
FIG. 2a is a schematic diagram of a Boost circuit with additional inverting windings;
FIG. 2b is a schematic diagram of a common mode noise equivalent model of a Boost circuit reverse phase winding method;
FIG. 3 is a schematic diagram of an equivalent model of common mode noise by the inverse winding method;
FIG. 4 is a graph illustrating an insertion loss representative characteristic;
FIG. 5 is a graph comparing insertion loss curves of different compensation capacitors;
FIG. 6a is a graph showing the comparison of different compensation capacitance noise test results;
FIG. 6b is another comparative graph of different compensated capacitive noise test results;
FIG. 7 is a graph showing comparison of insertion loss between different winding types;
FIG. 8 is a diagram illustrating noise contrast in different winding modes;
FIG. 9 is a table of experimental parameters for different turns of the inverter winding;
FIG. 10 is a schematic of the common mode noise of a1 turn inverter winding;
FIG. 11 is a schematic of the common mode noise of a 4 turn inverter winding;
FIG. 12 is a schematic of common mode noise for a 6 turn inverter winding;
fig. 13 is a schematic diagram of common mode noise for a 12-turn inverter winding.
Detailed Description
As shown in fig. 1 to 13, in the design of the inverter winding, the Boost inductance with the additional inverter winding is regarded as a double-winding transformer, and a transformer high-frequency model is established for the double-winding transformer under the premise of considering parasitic parameters; evaluating the common-mode EMI inhibition capability of the Boost circuit by using insertion loss; in the experimental measurement of noise measurement, the total earth distributed capacitance C of a switching tube of a Boost circuit is solved by inserting a passive device with known impedance into a noise measurement circuitAAnd at the critical frequency point f of the insertion loss curve1、fc、f2For design basis, the total earth distributed capacitance C of the switching tube of the Boost circuit is solvedAFurther obtain the compensation capacitance C of the reverse phase windingBThe selection principle, the winding method of the reverse phase winding and the method for selecting the optimal turn number of the reverse phase winding.
The total ground capacitance C of the switching tube of the Boost circuit is obtained by the experimental measurement methodAThe method comprises a step A1, wherein the step A1 is as follows:
the first step is as follows: measuring original common mode noise to obtain noise current i1；
The second step is that: inserting a passive device of known impedance, Zstd1To obtain a noise current i2；
The third step: inserting a passive device of known impedance, Zstd2To obtain a noise current i3；
……
By analogy, forming an insertion loss curve of the high-frequency model of the transformer;
the passive device of the known impedance is connected between the potential action point A of the switching tube of the Boost circuit and the ground potential.
By controlling the low frequency resonance point f of the insertion loss curve1Crossing frequency point fcHigh frequency resonance point f2The frequency value of the phase-reversing winding is designed to design the parameters of the phase-reversing winding, so that the suppression effect of the phase-reversing winding on common-mode noise is the best; the reverse phase winding parameters comprise compensation capacitance, winding mode and optimal turn number.
Selecting compensation capacitor C of reverse phase winding by low-frequency common-mode noise suppression optimal principleBEven at a low frequency resonance point f1And the frequency is lower than 150kHz, so that the best effect of the reverse winding on the common mode noise suppression of the low-frequency band of the Boost circuit is ensured.
By selecting the compensating capacitor CBControlling the low frequency resonance point f1Then, it is necessary to increase the crossover frequency f as much as possiblecHigh frequency resonant frequency f2And the good common mode noise suppression effect of the inverter winding on the middle and high frequency bands of the Boost circuit is ensured.
After the Boost circuit is added with the reverse phase winding, the insertion loss is as follows:
Figure GDA0002993618770000071
Lmis the exciting inductance, L, of a transformerkLeakage inductance is adopted, and n is the turn ratio of the primary and secondary turns of the transformer, namely the turn ratio between the Boost inductance and the reverse winding; cBThe compensation capacitor is used for grounding the secondary side B point of the double-winding transformer; cADistributing capacitance for the A point to the ground; rLISNIs the common mode equivalent resistance of a Linear Impedance Stabilization Network (LISN). CssEffective capacitance C for representing primary and secondary common mode ports of transformerpsConverted to secondary side and secondary side capacitor CsThe equivalent capacitance after parallel connection; the smaller the insertion loss IL is, the better the suppression effect of the reverse phase winding on the common mode noise is shown;
when the reverse winding is wound on the Boost inductor, the leakage inductance L between the reverse winding and the Boost inductor is required to be ensuredkAs small as possible, thereby increasing fc、f2；
Therefore, when selecting the optimum number of turns of the inverter winding, λ of the inverter winding is made as large as possibleTo increase fc、f2；
Wherein
Figure GDA0002993618770000072
The noise suppression effect is best when the number of turns of the anti-phase winding is such that λ is maximum.
In the double-winding transformer, the number of turns of the reverse winding is far less than that of the Boost inductor, so that the double-winding transformer has a larger turn ratio n, and the compensation capacitor CBFar greater than CssThe insertion loss can be further expressed according to (equation 2) as:
Figure GDA0002993618770000073
solving the total capacitance to ground C of the switch tubeAWhen the temperature of the water is higher than the set temperature,
firstly, the common mode noise current of the Boost circuit is measured to obtain the original common mode noise current i1Comprises the following steps:
Figure GDA0002993618770000074
then, a known impedance Z is inserted between a potential moving point A of a switching tube of the Boost circuit and the groundstd1To obtain a noise current i2；
Figure GDA0002993618770000081
The total capacitance C of the switch tube to ground can be further solved by formula 4 and formula 5A。
In the design of the anti-phase winding by controlling f1、fc、f2The frequency value of (2) realizes the suppression of common mode noise;
from equation 3, f1、fc、f2The expression for the three key frequency points is:
Figure GDA0002993618770000082
Figure GDA0002993618770000083
Figure GDA0002993618770000086
the compensation capacitor CBThe selection principle is the principle of optimizing the low-frequency common-mode noise suppression effect, namely, the compensation capacitor CBMake the low frequency resonance point f1Is less than 150kHz, i.e.
Figure GDA0002993618770000084
Due to the resonance point f of the low-frequency band1Less than 150kHz, so the formula:
Figure GDA0002993618770000085
compensation capacitor CBCan be further simplified into
CB＝n·(1+Lk/Lm)CA(equation 10).
Selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAnd after the reverse phase winding is uniformly wound, the (formula 10) can be respectively substituted into the (formula 7) and the (formula 8), so as to obtain:
fc、f2the expression of (a) is as follows:
Figure GDA0002993618770000091
from the above formula, LkThe smaller, fc、f2The higher the frequency value of (A), the larger the effective noise suppression band bandwidth of the inverter winding, and the noise suppression band bandwidthThe better the inhibition effect; therefore, when winding the reverse winding, the leakage inductance L between the reverse winding and the Boost inductance should be ensuredkAt the minimum, the winding method is uniform winding and dense winding is avoided.
In the compensation capacitor CBAfter the winding mode is determined, the number of turns of the reverse phase winding and the leakage inductance L need to be comprehensively consideredkThe influence of (c). Selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAfter the reverse phase winding is uniformly wound, the (formula 1) can be substituted into the (formula 11) and the (formula 12), and f can be further substitutedc、f2The method is simplified as follows:
Figure GDA0002993618770000092
from the above, fc、f2Proportional to λ, the noise suppression effect is best when the number of turns of the anti-phase winding is such that λ is the greatest, and λ should be made the greatest when the number of turns of the anti-phase winding is chosen.
Example (b):
in this embodiment, a Boost PFC circuit of a communication power supply is taken as an example, and the whole process of the design of the inverting winding is described in detail. Wherein, the prototype input is 220VacAnd output 380VdcThe power inductor has the advantages of being/120W, the switching frequency is 115kHz, the PFC inductor is an annular iron-silicon-aluminum magnetic core, the inductance value is 1.353mH, and the number of turns of the power inductor is 115 turns.
Fig. 1a and 1b are schematic diagrams of common mode noise of a Boost circuit, and fig. 1a is a common mode noise path of the Boost circuit. Wherein the combination of elements within the dashed box represents a linear impedance network, L1Is a Boost inductor, S is a switch tube, D is a diode, C is an output filter capacitor, RLIs a load resistor, point A is the main potential trip point of the circuit, CAThe total distributed capacitance to ground (including inductance L) for point A1The outer conductor has distributed capacitance to ground and the switch tube S and diode D have distributed capacitance to ground via the heat sink). When the switching tube S is switched on and off at high frequency, the potential of the point A in the circuit jumps, displacement current is formed in a ground loop in an electric field coupling mode, and common-mode noise is formed by the displacement current flowing through the L line/N line and the LISN. In making explicitOn the basis of the common mode noise transmission path, for convenience of analysis, according to a substitution theorem, a Boost circuit common mode noise equivalent model as shown in fig. 1b is established. R in FIG. 1bLISNIs the common mode equivalent resistance of the LISN. As can be seen from fig. 1b, the common mode noise flowing through the LISN equivalent resistor is:
Figure GDA0002993618770000093
fig. 2a and 2b are schematic diagrams of common mode noise of the Boost circuit by the reverse winding method. FIG. 2a is a Boost circuit with additional inverting winding, where LAInductance corresponding to the opposite winding, CBTo compensate for capacitance. Fig. 2b is a common mode noise equivalent model of the Boost circuit inverting winding method. As can be seen from FIG. 2a, after the reverse winding is wound, point B passes through the compensation capacitor CBThe displacement current generated to ground is:
Figure GDA0002993618770000094
from fig. 2b it can be seen that the common mode current flowing through the LISN is:
Figure GDA0002993618770000101
as can be seen from the formula (17), theoretically, if the potential jumps of the points A and B are completely reversed, the compensation capacitor C is adjustedBAnd the size of the B-point to ground potential (adjusting the number of turns of the anti-phase winding) has the opportunity to greatly suppress the common mode current flowing through the LISN, ideally to minimize common mode noise to zero. In practice, complete cancellation is difficult to achieve due to the influence of circuit parasitic parameters. Therefore, it is necessary to deeply analyze the influence of the parasitic parameters on the common mode noise suppression effect to find a method for optimizing the design of the inverter winding.
FIG. 3 is an equivalent model of common mode noise by the inverse winding method, taking into account parasitic parameters. And after the reverse winding is wound, the reverse winding and the Boost inductor form a double-winding transformer. Wherein C ispDistributing capacitance C for primary side of transformersDistributing capacitance and C for secondary side of transformerpsIs the common mode port equivalent capacitance, L of the transformermIs the exciting inductance, L, of a transformerkLeakage inductance is adopted, and n is the turn ratio of the primary and secondary turns of the transformer; cBThe compensation capacitor is used for grounding the secondary side B point of the double-winding transformer; cADistributing capacitance for the A point to the ground; rLISNIs the common mode equivalent resistance of a Linear Impedance Stabilization Network (LISN). After the reverse winding is added, the insertion loss expression of the double-winding transformer is as follows:
Figure GDA0002993618770000102
compared with Boost inductor, the number of turns of reverse winding is generally less, the turn ratio n of the formed double-winding transformer is very large, and the required compensation capacitor CBAre generally large; the number of turns of the reverse phase winding is small, so that the secondary side capacitor C is causedsCapacitance C converted to secondary sidepsAlso very small, i.e. the equivalent capacitance CssIs smaller. Thus, the compensation capacitor CBFar greater than CssThe insertion loss may be further expressed as:
Figure GDA0002993618770000103
FIG. 4 shows a turn ratio n equal to 9 and a compensation capacitance equal to 130pF, CssAnd 5pF, the corresponding insertion loss is a characteristic curve with frequency as a variable in the conduction band. From the figure, the low frequency resonance point f can be clearly seen1Crossing frequency point fcHigh frequency resonance point f2。
Because the total capacitance to ground of the switch tube CAThe influence on the common mode noise is very critical, and when the reverse winding is designed, C needs to be solved firstA. The common mode noise current of the Boost circuit is measured to obtain the original common mode noise current i1。
Figure GDA0002993618770000104
A capacitor C with the capacitance value of 100pF is inserted between the potential moving point A of the switching tube of the Boost circuit and the grounddThe common mode noise current i can be obtained2。
Figure GDA0002993618770000105
The equations (20) and (21) can be further solved, and the total earth capacitance C of the Boost circuit in the embodimentaAnd 23.5 pF.
The optimization design of the reverse phase winding method is mainly controlled by f1、fc、f2Thereby achieving the rejection of common mode noise. Theoretically, in the range of the conduction band, if the resonance point f can be made1Sufficiently small, less than 150 kHz; f. ofc、f2Large enough to be larger than 30MHz, and the reverse winding has the best effect on noise suppression. However, in practice, f1、fc、f2The value of (a) is difficult to control as desired. From the insertion loss expression (19), the expressions for three key frequency points can be derived as follows:
Figure GDA0002993618770000111
Figure GDA0002993618770000112
Figure GDA0002993618770000113
in order to ensure that the low-frequency band has good common-mode noise suppression effect, the compensation capacitor C is selected according to the principle of optimal common-mode noise suppression effect of the low-frequency bandBBy making the low-frequency resonance point f1The frequency value of the compensating capacitor C is less than 150kHzBIt is possible to obtain:
Figure GDA0002993618770000114
due to the resonance point f of the low-frequency band1Less than 150kHz, so there are:
Figure GDA0002993618770000115
compensation capacitor CBCan be further simplified into:
CB＝n·(1+Lk/Lm)CAequation 26
Leakage inductance L when the reverse phase winding is 6 turns and is uniformly woundkThe compensation capacitance C is calculated to be 80.2 mu H according to the principle of optimal low-frequency band noise suppression effectBIs 477 pF. In the EMI noise test experiment, three compensation capacitors with the capacitance values of 568.6pF, 477.1pF and 315.6pF are added respectively. The insertion loss curves are plotted in comparison with fig. 5, and the EMI noise test results are shown in fig. 6. As can be seen from fig. 5, when the capacitor C is compensatedBAnd when the principle of low-frequency common mode rejection optimization is met, the effect of insertion loss is optimal. It can be seen from the noise test results of FIG. 6 that when the capacitor C is compensatedBWhen the principle of low-frequency common mode rejection is met, the rejection effect of the reverse winding on the common mode noise is the best within 5 MHz.
Selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAnd then, the insertion loss in the low frequency band is very small, and the suppression effect on common mode noise is very good. However, the different winding methods cause leakage inductance L between the Boost inductance winding and the reverse windingkVery different crossing frequency f affecting the insertion loss curvecHigh frequency resonance point f2The size of (2). By substituting formula (14) for formula (11) or (12), f can be obtainedc、f2The expression of (a) is as follows:
Figure GDA0002993618770000116
Figure GDA0002993618770000121
obtained from the formulae (15) and (16), LkThe smaller, fc、f2The higher the frequency value of (2), the larger the bandwidth of the effective noise suppression frequency band of the reverse winding, and the better the noise suppression effect. Therefore, when winding the reverse winding, the leakage inductance L between the reverse winding and the Boost inductance should be ensured as much as possiblekAnd minimum. In an actual circuit, the reverse phase winding can be uniformly wound or densely wound, and when the reverse phase winding is uniformly wound, the leakage inductance is generally small. In 6 turns of the reverse winding and compensating capacitor CBIs selected according to the condition of formula (10). Uniform winding with leakage inductance LkAt 85.94. mu.H, C was selectedB477.12 pF; leakage inductance L under close winding of the reverse windingk288.5 μ H, C was selectedB565.15 pF. The insertion loss curves are plotted in comparison with fig. 7, and the EMI noise test results are shown in fig. 8. As can be seen from fig. 7, the insertion loss is most effective when the reverse phase winding is uniformly wound. As can be seen from the noise test result in fig. 8, when the phase-inverted winding is uniformly wound, the noise improvement effect in the low frequency band is good, and the noise suppression effect in the high frequency band is more obvious.
When the reverse winding is wound on the Boost inductor, the more the number of turns of the reverse winding is, the more the leakage inductance value of the formed double-winding transformer is correspondingly reduced. Therefore, in the compensation capacitor CBAfter the winding mode is determined, the number of turns of the reverse phase winding and the leakage inductance L need to be comprehensively consideredkThe influence of (c). Selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAnd after the reverse phase winding is uniformly wound, the following can be obtained:
Figure GDA0002993618770000122
Figure GDA0002993618770000123
wherein the content of the first and second substances,
Figure GDA0002993618770000124
fc、f2proportional to λ, the noise suppression is best when the number of turns of the anti-phase winding is such that λ is the largest. Therefore, the number of turns of the inverter winding should be selected so as to maximize λ.
In the compensation capacitor CBAnd when the reverse phase winding is selected according to the low-frequency common mode noise suppression optimal principle and is uniformly wound, measuring the common mode noise current of the Boost circuit under the conditions that the reverse phase winding has 1 turn, 4 turns, 6 turns and 12 turns respectively. The parameters of the double-winding transformer with the additional reverse-phase winding under different turns are shown in figure 9; common mode noise of 1-turn reverse winding is shown in FIG. 10; 4-turn reverse winding as in FIG. 11; 6-turn reverse winding as in FIG. 11; the 12-turn anti-phase winding is as in figure 12.
As can be seen from fig. 9, λ is maximum when the reverse winding is 6 turns; with 1 turn of the anti-phase winding, λ is minimal. From the graphs (fig. 10, 11, 12 and 13) of the common mode noise test results of the opposite phase windings with different turns, it can be seen that within 5MHz, the noise suppression effect of the opposite phase winding with 6 turns is the best, and the noise suppression effect of the opposite phase winding with 1 turn is the worst. Experimental results show that the larger the lambda is, the better the suppression effect of the reverse winding on the common mode noise is.

Claims (6)

1. A method for designing an inverted winding for suppressing common-mode EMI of a Boost circuit is characterized by comprising the following steps: the reverse phase winding is wound on a PFC (power factor correction) inductor of the Boost circuit, the Boost inductor with the additional reverse phase winding is regarded as a double-winding transformer in the design of the reverse phase winding, and a transformer high-frequency model is established for the double-winding transformer under the premise of considering parasitic parameters; evaluating the common-mode EMI inhibition capability of the Boost circuit by using insertion loss; in the experimental measurement of noise measurement, the total earth distributed capacitance C of a switching tube of a Boost circuit is solved by inserting a passive device with known impedance into a noise measurement circuitAAnd a low-frequency resonance point f at a key frequency point of the insertion loss curve1Crossing frequency point fcHigh frequency resonance point f2For design basis, the total earth distributed capacitance C of the switching tube of the Boost circuit is solvedAFurther obtain the compensation capacitance C of the reverse phase windingBSelection principle of (1), reverse windingWinding method of the group and method for selecting the optimal number of turns of the reverse phase winding;
the total ground capacitance C of the switching tube of the Boost circuit is obtained by the experimental measurement methodAWhich comprises the steps of a1,
step a1 is:
the first step is as follows: measuring original common mode noise to obtain noise current i1；
The second step is that: inserting a passive device of known impedance, Zstd1To obtain a noise current i2；
The third step: inserting a passive device of known impedance, Zstd2To obtain a noise current i3；
……
By analogy, forming an insertion loss curve of the high-frequency model of the transformer;
the passive device with known impedance is connected between a potential moving point A of a switching tube of the Boost circuit and a ground potential;
by controlling the low frequency resonance point f of the insertion loss curve1Crossing frequency point fcHigh frequency resonance point f2The frequency value of the phase-reversing winding is designed to design the parameters of the phase-reversing winding, so that the suppression effect of the phase-reversing winding on common-mode noise is the best; the reverse phase winding parameters comprise compensation capacitance, a winding mode and an optimal number of turns;
selecting compensation capacitor C of reverse phase winding by low-frequency common-mode noise suppression optimal principleB＝n·(1+Lk/Lm)CAEven at a low frequency resonance point f1The frequency is lower than 150kHz, so that the best effect of the reverse winding on the common mode noise suppression of the low-frequency band of the Boost circuit is ensured;
by selecting the compensating capacitor CBControlling the low frequency resonance point f1Then, the crossing frequency point f needs to be increasedcHigh-frequency resonance frequency point f2The suppression effect of the reverse phase winding on common mode noise of the middle and high frequency bands of the Boost circuit is good;
when the reverse winding is wound on the Boost inductor, the leakage inductance L between the reverse winding and the Boost inductor is required to be ensuredkAs small as possible, thereby increasing fc、f2。
2. The method of claim 1, wherein the method comprises the steps of: after the Boost circuit is added with the reverse phase winding, the insertion loss is as follows:
Figure FDA0002993618760000021
Lmis an exciting inductance of a transformer, LkN is the turn ratio of the number of turns of the primary side and the secondary side of the transformer, namely the turn ratio between the Boost inductor and the reverse winding; cBThe compensation capacitor is used for grounding the secondary side B point of the double-winding transformer; cACapacitors are distributed for the switching tube to the ground; rLISNCommon mode equivalent resistance of the linear impedance stabilization network; cssEffective capacitance C for representing primary and secondary common mode ports of transformerpsConverted to secondary side and secondary side capacitor CsThe equivalent capacitance after parallel connection; the smaller the insertion loss IL is, the better the suppression effect of the reverse phase winding on the common mode noise is shown;
when the reverse winding is wound on the Boost inductor, the leakage inductance L between the reverse winding and the Boost inductor is required to be ensuredkAs small as possible to obtain fc、f2；
Therefore, when selecting the optimum number of turns of the reverse winding, the reverse winding is made
Figure FDA0002993618760000022
Thereby obtaining fc、f2；
The noise suppression effect is best when the number of turns of the anti-phase winding is such that λ is maximum.
3. The method of claim 2, wherein the method comprises the following steps: in the double-winding transformer, the number of turns of the reverse winding is far smaller than that of the Boost inductor, so that the turn ratio n of the double-winding transformer is obtained, and the compensation capacitor C is consideredBFor expressing insertion loss (male)Formula 2) is further represented as:
Figure FDA0002993618760000023
solving the total capacitance to ground C of the switch tubeAWhen the temperature of the water is higher than the set temperature,
firstly, the common mode noise current of the Boost circuit is measured to obtain the original common mode noise current i1Comprises the following steps:
Figure FDA0002993618760000031
then, a known impedance Z is inserted between a potential moving point A of a switching tube of the Boost circuit and the groundstd1To obtain a noise current i2；
Figure FDA0002993618760000032
Further solving the total earth capacitance C of the switch tube by (formula 4) and (formula 5)A。
4. The method of claim 3, wherein the method comprises the following steps: in the design of the anti-phase winding by controlling f1、fc、f2The frequency value of (2) realizes the suppression of common mode noise; f is obtained from (equation 3)1、fc、f2The expression for the three key frequency points is:
Figure FDA0002993618760000033
Figure FDA0002993618760000034
Figure FDA0002993618760000035
the compensation capacitor CBThe selection principle is the principle of optimizing the low-frequency common-mode noise suppression effect, namely, the compensation capacitor CBMake the low frequency resonance point f1Is less than 150kHz, i.e.
Figure FDA0002993618760000036
Due to the resonance point f of the low-frequency band1Less than 150kHz, the formula:
Figure FDA0002993618760000037
compensation capacitor CBIs further simplified into
CB＝n·(1+Lk/Lm)CA(equation 10).
5. The method of claim 4, wherein the method comprises the following steps: selecting a compensation capacitor C according to the principle of optimal low-frequency common-mode noise suppression effectBAnd after the reverse phase winding is uniformly wound, substituting (formula 10) into (formula 7) and (formula 8) respectively to obtain:
fc、f2the expression of (a) is as follows:
Figure FDA0002993618760000041
from the above formula, LkThe smaller, fc、f2The higher the frequency value of the phase-reversal winding is, the larger the effective noise suppression frequency band bandwidth of the phase-reversal winding is, and the better the noise suppression effect is; therefore, when winding the reverse winding, the leakage inductance L between the reverse winding and the Boost inductance should be ensuredkAt the minimum, the winding method is uniform winding and avoidsAnd tight winding is avoided.
6. The method of claim 5, wherein the method comprises the following steps: in the compensation capacitor CBAfter the winding mode is determined, the number of turns of the reverse phase winding and the leakage inductance L need to be comprehensively consideredkThe compensation capacitor C is selected according to the principle of optimal low-frequency common-mode noise suppression effectBAnd after the reverse phase winding is uniformly wound, substituting (formula 1) into (formula 11) and (formula 12), and further adding fc、f2The method is simplified as follows:
Figure FDA0002993618760000042
from the above, fc、f2Proportional to λ, the noise suppression effect is best when the number of turns of the anti-phase winding is such that λ is the greatest, and λ should be made the greatest when the number of turns of the anti-phase winding is chosen.
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