CN111124023B - A hybrid power supply modulator and modulation circuit - Google Patents
A hybrid power supply modulator and modulation circuit Download PDFInfo
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Abstract
本发明提供一种混合型电源调制器，包括线性模块、电源模块、数字控制模块和开关转换模块，线性模块用于向功率放大器提供与包络信号幅值对应的调制电压，数字控制模块用于将包络信号进行处理后并逻辑分析，输出第一控制信号、第二控制信号和第三控制信号，第一控制信号经过第一栅极驱动器控制第一选择开关，第二控制信号经过第二栅极驱动器控制第二选择开关，通过第一选择开关和第二选择开关对功率放大器提供与包络信号幅值对应的调制电流；即通过包络追踪技术控制功率放大器的调制电压和调制电流随包络信号的幅值而变化，提高了功率放大器的效率。本发明还提供一种混合型电源调制电路。
The invention provides a hybrid power supply modulator, comprising a linear module, a power supply module, a digital control module and a switch conversion module. The linear module is used for providing a modulation voltage corresponding to the amplitude of an envelope signal to the power amplifier, and the digital control module is used for After the envelope signal is processed and logically analyzed, the first control signal, the second control signal and the third control signal are output. The first control signal controls the first selection switch through the first gate driver, and the second control signal passes through the second control signal. The gate driver controls the second selection switch, and provides the power amplifier with a modulation current corresponding to the amplitude of the envelope signal through the first selection switch and the second selection switch; The amplitude of the envelope signal changes, improving the efficiency of the power amplifier. The invention also provides a hybrid power supply modulation circuit.
Description
Technical Field
The invention relates to the technical field of wireless communication, in particular to a hybrid power modulator and a modulation circuit.
Background
With the accelerated development of information-based construction, the service demands of wireless communication systems such as wireless communication, data link, satellite communication and the like are rapidly increased, the coverage area of network systems is continuously expanded, and the number of users in each network system is multiplied. With the background of increasingly complex environments and increasingly crowded electromagnetic spectrum, high transmission rates, high spectrum utilization, high communication reliability, low power consumption, and miniaturization have become urgent requirements for wireless communication systems.
In recent years, various sophisticated wideband efficient modulation techniques have been successively applied to wireless communication systems in order to improve transmission rate and spectrum utilization. A wideband high-efficiency modulation technique represented by Orthogonal Frequency Division Multiplexing (OFDM), in which a modulation waveform has characteristics of wideband and Peak-to-Average Power Ratio (PAPR), and puts higher requirements on efficiency, linearity and operating bandwidth of a radio Frequency Power amplifier (hereinafter referred to as radio Frequency amplifier) in a wireless communication system, and the radio Frequency Power amplifier is used for receiving an input signal RFinThereafter, the input signal RF is amplifiedinTo generate the amplifierLarge output signal RFOUT。
For wideband signals with high peak-to-average ratio (PAPR), in order to ensure the linearity of a radio frequency power amplifier, the traditional method adopts output power back, namely, the radio frequency power amplifier with higher power output capability is used to enable the radio frequency power amplifier to work in a linear state, thereby improving the linear performance. However, the conventional rf power amplifier generally adopts a constant voltage for power supply, and since the constant voltage is set according to the maximum output power of the rf power amplifier in the saturation region, the average output power of the rf power amplifier is far less than the maximum output power of the saturation region during power backoff, the loss of the rf power amplifier is increased rapidly, and the working efficiency is deteriorated rapidly. Aiming at the broadband modulation waveform with the high peak-to-average ratio (PAPR) similar to OFDM, how to simultaneously meet the requirements of high linearity, high efficiency and wide frequency band is a key research point of the current radio frequency power amplifier and a worldwide difficult problem which needs to be solved urgently.
Compared with other technologies, the Envelope Tracking (ET) technology has a wider dynamic range and a wider working frequency range, improves the linearity and efficiency more controllably, and has more advantages in technical realizability, so that the method is more suitable for a wireless communication system with a high peak-to-average power ratio (PAPR). And how to design a high-efficiency high-bandwidth power supply modulator becomes a core part in ET technology.
Disclosure of Invention
In view of the above problems, an object of the present invention is to provide a hybrid power modulator and a modulation circuit for providing a modulation voltage and a modulation current corresponding to an amplitude of an envelope signal to a drain of a power amplifier, thereby improving efficiency of the power amplifier.
In order to achieve the purpose, the invention adopts the following technical scheme:
a hybrid power modulator, comprising: linear module, power module, digital control module and switch conversion module, linear module provides the modulation voltage to power amplifier, and digital control module control switch conversion module provides the modulation current to power amplifier, wherein: the linear module comprises an operational amplifier and a voltage current generator, wherein the envelope signal is input into the operational amplifier, and then a modulation voltage corresponding to the amplitude of the envelope signal is provided for the power amplifier through the voltage current generator; the power supply module is used for converting input power supply voltage into regulated voltage and respectively supplying power to a first selection switch and a second selection switch in the switch conversion module by using the power supply voltage and the regulated voltage; the digital control module comprises a first comparison unit, a second comparison unit and a logic control unit, the digital control module processes an input envelope signal and outputs an analog-digital conversion signal, and the analog-digital conversion signal sequentially passes through the first comparison unit and the logic control unit and then outputs a first control signal and a second control signal which are used for controlling the switch conversion module to provide a modulation current corresponding to the amplitude of the envelope signal to the power amplifier; the analog-to-digital conversion signal outputs a third control signal after passing through the second comparison unit, and the third control signal is used for controlling the power supply module to provide power supply voltage corresponding to the amplitude of the envelope signal to the power supply end of the voltage current generator; the switch conversion module comprises a first grid driver, a first selection switch, a second grid driver and a second selection switch, wherein a first control signal controls the first selection switch through the first grid driver, a second control signal controls the second selection switch through the second grid driver, and modulation current corresponding to the amplitude of the envelope signal is provided for the power amplifier through the first selection switch and the second selection switch.
Preferably, the envelope signal is input from a positive input terminal of the operational amplifier, and a negative input terminal of the operational amplifier is grounded via a first resistor and connected to an output terminal of the voltage current generator via a second resistor.
Preferably, the voltage current generator is a push-pull circuit, the push-pull circuit comprises an N-type MOS transistor and a P-type MOS transistor, and a gate of the N-type MOS transistor is connected with a gate of the P-type MOS transistor and serves as an input end of the voltage current generator; the source electrode of the N-type MOS tube is connected with the source electrode of the P-type MOS tube and is used as the output end of the voltage current generator; the drain electrode of the N-type MOS tube is used as a power supply end of the voltage current generator; the drain electrode of the P-type MOS tube is grounded.
Preferably, the power supply module includes a dc-dc voltage converter and a power supply selector, the dc-dc voltage converter is configured to convert a power supply voltage into an adjusted voltage, the power supply voltage and the adjusted voltage are input into the power supply selector, and the power supply selector is controlled by a third control signal to provide a power supply voltage to the power supply terminal of the voltage generator, the power supply voltage includes the power supply voltage or the adjusted voltage.
Preferably, the digital control module further includes a low-pass filter and an analog-to-digital converter, and the envelope signal is processed by the low-pass filter and the analog-to-digital converter in sequence and then outputs an analog-to-digital conversion signal.
Preferably, the first comparing unit includes a first comparator, a first hysteresis comparator and a second comparator.
Preferably, the first selection switch includes a first switch tube and a second switch tube, a first output end of the first gate driver is connected to an input control end of the first switch tube, a second output end of the first gate driver is connected to an input control end of the second switch tube, a source electrode of the first switch tube is connected to a drain electrode of the second switch tube and serves as an output end of the first selection switch, a source electrode of the second switch tube is grounded, and a power supply voltage is used to supply power to the drain electrode of the first switch tube;
the second selection switch comprises a third switch tube and a fourth switch tube, the first output end of the second grid driver is connected with the input control end of the third switch tube, the second output end of the second grid driver is connected with the input control end of the fourth switch tube, the source electrode of the third switch tube is connected with the drain electrode of the fourth switch tube and serves as the output end of the second selection switch, the source electrode of the fourth switch tube is grounded, and the drain electrode of the third switch tube is supplied with power by using the regulated voltage.
Preferably, the output end of the first selection switch is connected with the drain electrode of the power amplifier through a first inductor; the output end of the second selection switch is connected with the drain electrode of the power amplifier through a second inductor and a first diode in sequence; the inductance values of the first inductor and the second inductor are equal.
Preferably, the power supply selector includes a second diode and a fifth switching tube, an output terminal of the dc-dc voltage converter is connected to an anode of the second diode, a cathode of the second diode is connected to a source of the fifth switching tube and a power supply terminal of the voltage current generator, the power supply voltage is input to a drain of the fifth switching tube, a third control signal is input to an input control terminal of the fifth switching tube, and switching of the supply voltage of the voltage current generator between the power supply voltage and the regulation voltage is realized by controlling on and off of the fifth switching tube.
Preferably, the push-pull circuit further comprises a dc biaser, and the dc biaser is used for providing a dc bias voltage to the input ends of the N-type MOS transistor and the P-type MOS transistor.
The invention also provides a hybrid power supply modulation circuit, which comprises the hybrid power supply modulator.
Compared with the prior art, the invention has the following beneficial effects: providing a modulation voltage corresponding to the amplitude of the envelope signal to the power amplifier through the linear module; the digital control module processes the input envelope signal and outputs an analog-digital conversion signal, and the analog-digital conversion signal sequentially passes through the first comparison unit and the logic control unit and then outputs a first control signal and a second control signal which are used for controlling the switch conversion module to provide a modulation current corresponding to the amplitude of the envelope signal to the power amplifier; the modulation voltage and the modulation current of the power amplifier are controlled to change along with the amplitude of the envelope signal through an envelope tracking technology instead of supplying fixed power supply voltage and current to the power amplifier, and when the amplitude of the input envelope signal is small, the power amplifier does not need to supply large modulation voltage and modulation current, so that the power consumption of the power amplifier can be obviously reduced; meanwhile, the analog-to-digital conversion signal outputs a third control signal after passing through the second comparison unit, the third control signal is utilized to control the power supply module to provide power supply voltage corresponding to the amplitude of the envelope signal to the power supply end of the voltage current generator, when the amplitude of the envelope signal is smaller, the linear amplification amplitude of the corresponding linear module is smaller, the voltage current generator does not need very high power supply voltage, and can provide corresponding modulation voltage for the power amplifier, so that the efficiency of the linear module is improved, and the loss of the linear module is reduced. The invention improves the efficiency of the power amplifier by reducing the power consumption of the power amplifier and reducing the loss of the linear module.
Drawings
Fig. 1 is a schematic diagram of an internal circuit of a hybrid power modulator provided by the present invention;
FIG. 2 is a schematic diagram of an internal circuit of a linear module according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of an internal circuit of a power module according to an embodiment of the invention;
FIG. 4 is a schematic diagram of an internal circuit of the digital control module according to an embodiment of the present invention;
fig. 5 is a schematic circuit diagram of an internal circuit of a switching conversion module according to an embodiment of the present invention.
Wherein: 1. the linear module 11, the operational amplifier 12, the voltage current generator 13, the first resistor 14, the second resistor 2, the power module 21, the dc-dc voltage converter 22, the power selector 221, the second diode 222, the fifth switching tube 3, the digital control module 31, the low-pass filter 32, the analog-to-digital converter 33, the first comparison unit 331, the first comparator 332, the first hysteresis comparator 333, the second comparator 34, the second comparison unit 35, the logic control unit 35, the switch conversion module 4, the first gate driver 41, the second gate driver 42, the second gate driver 43, the first selection switch 44, the second selection switch 45, the first inductor 46, the second inductor 47, the first diode 5, and the power amplifier.
Detailed Description
The following describes an embodiment according to the present invention with reference to the drawings.
In the following description, numerous specific details are set forth in order to provide a thorough understanding of the present invention, however, the present invention may be practiced in other ways than those specifically described herein, and thus the present invention is not limited to the specific embodiments disclosed below.
Since the conventional power amplifier is supplied with a constant voltage, in order to ensure the linearity of the power amplifier, a power back-off is conventionally adopted, and the power back-off causes the loss of the power amplifier to be increased sharply, and the working efficiency is deteriorated sharply.
The invention provides a hybrid power supply modulator, which tracks an input envelope signal in real time to control the modulation voltage and the modulation current of a power amplifier, thereby achieving the purpose of improving the efficiency.
In order to better understand the technical solutions and effects of the present invention, the following detailed descriptions of specific embodiments will be provided with reference to fig. 1-5.
Referring to fig. 1, the present invention provides a hybrid power modulator, including: the power amplifier comprises a linear module 1, a power supply module 2, a digital control module 3 and a switch conversion module 4, wherein the linear module 1 provides most of modulation voltage Vpa for a power amplifier 5, and the digital control module 3 controls the switch conversion module 4 to provide main modulation current Ih for the power amplifier 5, wherein: the linear module 1 comprises an operational amplifier 11 and a voltage current generator 12, wherein the envelope signal Venv is input into the operational amplifier 11, and then a modulation voltage Vpa corresponding to the amplitude of the envelope signal Venv is provided for the power amplifier 5 through the voltage current generator 12; the power supply module 2 is configured to convert an input power supply voltage Vdd into an adjustment voltage Vm, and supply power to the first selection switch 43 and the second selection switch 44 in the switch conversion module 4 by using the power supply voltage Vdd and the adjustment voltage Vm, respectively; the digital control module 3 includes a first comparing unit 33, a second comparing unit 34 and a logic control unit 35, the digital control module 3 processes the input envelope signal Venv and then outputs an analog-to-digital conversion signal AD, the analog-to-digital conversion signal AD sequentially passes through the first comparing unit 33 and the logic control unit 35 and then outputs a first control signal SW1 and a second control signal SW2, and the first control signal SW1 and the second control signal SW2 are used for controlling the switch converting module 4 to provide a modulation current Ih corresponding to the amplitude of the envelope signal Venv to the power amplifier 5; the analog-to-digital conversion signal AD passes through the second comparing unit 34 and then outputs a third control signal SW3, where the third control signal SW3 is used to control the power module 2 to provide a power supply voltage Vdd _ m corresponding to the amplitude of the envelope signal Venv to the power terminal of the voltage current generator 12; the switch converting module 4 includes a first gate driver 41, a first selection switch 43, a second gate driver 42, and a second selection switch 44, the first control signal SW1 controls the first selection switch 43 through the first gate driver 41, the second control signal SW2 controls the second selection switch 44 through the second gate driver 42, and the modulation current Ih corresponding to the magnitude of the envelope signal Venv is provided to the power amplifier 5 through the first selection switch 43 and the second selection switch 44.
By adopting the technical scheme, the linear module 1 is utilized to provide the modulation voltage Vpa corresponding to the amplitude of the envelope signal Venv to the drain electrode of the power amplifier 5; the digital control module 3 processes an input envelope signal Venv and outputs an analog-to-digital conversion signal AD, the analog-to-digital conversion signal AD is sequentially compared by the first comparison unit 33 and logically analyzed by the logic control unit 35 to output a first control signal SW1 and a second control signal SW2, the analog-to-digital conversion signal AD is compared by the second comparison unit 34 and outputs a third control signal SW3, and the first control signal SW1 and the second control signal SW2 control the switch conversion module 4 to provide a modulation current Ih corresponding to the amplitude of the envelope signal Venv to the power amplifier 5; that is, the modulation voltage Vpa and the modulation current Ih of the power amplifier 5 are controlled to vary with the amplitude of the envelope signal Venv by using an envelope tracking technique, instead of supplying a fixed voltage and current to the drain of the power amplifier 5, and when the amplitude of the input envelope signal Venv is small, the small modulation voltage Vpa and the small modulation current Ih are supplied to the drain of the power amplifier 5, so that the power consumption of the power amplifier 5 can be reduced significantly; meanwhile, the third control signal SW3 is used for controlling the power supply module 2 to provide the power supply voltage Vdd _ m corresponding to the amplitude of the envelope signal Venv to the power supply terminal of the voltage current generator 12, when the amplitude of the envelope signal Venv is smaller, the linear amplification amplitude of the corresponding linear module 1 is smaller, and the voltage current generator 12 does not need a very high power supply voltage Vdd _ m, that is, the third control signal SW3 controls the power supply module 2 to provide the smaller power supply voltage Vdd _ m to the power supply terminal of the voltage current generator 12, so that the corresponding modulation voltage can be provided for the power amplifier 5, the efficiency of the linear module 1 is improved, and the loss of the linear module 1 is reduced.
Based on the above embodiment, further, the power voltage of the operational amplifier 11 is Vdd, the envelope signal Venv is input to the positive input terminal of the operational amplifier 11, the negative input terminal of the operational amplifier 11 is grounded through the first resistor 13 and is connected to the output terminal of the voltage current generator 12 through the second resistor 14, the output terminal of the operational amplifier 11 is connected to the input terminal of the voltage current generator 12, and the output terminal of the voltage current generator 12 is connected to the drain of the power amplifier 5 (see fig. 2).
By adopting the technical scheme, the envelope signal Venv input in the forward direction is linearly amplified through the operational amplifier 11, the envelope signal Venv comprises LTE, QPSK, WCDMA, OFDM and the like, the amplification times are determined by the first resistor 13 and the second resistor 14, then the amplified envelope signal Venv is input into the voltage current generator 12, and the voltage current generator 12 provides the modulation voltage Vpa corresponding to the amplitude of the envelope signal Venv and a small part of drain driving current Im to the drain of the power amplifier 5. The drain of the conventional power amplifier is supplied with power by a constant voltage, and when the power is backed off, the average output power of the power amplifier 5 is far less than the power of the saturation region of the power amplifier 5, so that the loss of the power amplifier 5 is increased sharply, and the working efficiency is deteriorated sharply, the linear module 1 composed of the operational amplifier 11 and the voltage current generator 12 is adopted to provide the drain of the power amplifier 5 with the modulation voltage Vpa corresponding to the amplitude of the envelope signal Venv, so that the modulation voltage Vpa changes along with the amplitude of the envelope signal Venv, and when the amplitude of the envelope signal Venv is smaller, the voltage current generator 12 provides the drain of the power amplifier 5 with a smaller modulation voltage Vpa, so that the power amplification can be realized, that is, the power consumption of the power amplifier 5 is reduced, and the efficiency is improved.
On the basis of the above embodiment, further, the voltage current generator 12 is a push-pull circuit, the push-pull circuit includes an N-type MOS transistor M1 and a P-type MOS transistor M2, and a supply voltage Vdd _ M corresponding to the amplitude of the envelope signal Venv is input from the drain of the N-type MOS transistor M1; the drain electrode of the P-type MOS tube M2 is grounded; the grid electrode of the N-type MOS tube M1 is connected with the grid electrode of the P-type MOS tube M2, and is used as the input end of the voltage current generator 12 and is connected with the output end of the operational amplifier 11; the source of the N-type MOS transistor M1 is connected to the source of the P-type MOS transistor M2 as the output terminal of the voltage current generator 12 (see fig. 2).
By adopting the above technical scheme, after the envelope signal Venv is amplified by the operational amplifier 11, the envelope signal Venv is followed by the push-pull circuit in the voltage generator 12, and the drain driving current Im of the power amplifier 5 is provided while the modulation voltage Vpa corresponding to the amplitude of the envelope signal Venv is provided for the drain of the power amplifier 5, because the input impedance of the push-pull circuit is relatively large and the output impedance is relatively small, the driving current Im can be provided for the drain of the power amplifier 5, and the driving capability of the linear module 1 is improved.
Based on the above embodiment, the power module 2 further includes a dc-dc voltage converter 21 and a power selector 22, the dc-dc voltage converter 21 is configured to convert the power voltage Vdd into a regulated voltage Vm, the regulated voltage Vm may be smaller than the power voltage Vdd or larger than the power voltage Vdd, and the regulated voltage Vm in this embodiment is smaller than the power voltage Vdd. The supply voltage Vdd and the adjustment voltage Vm are input to the supply selector 22, and the supply selector 22 is controlled by the third control signal SW3 to provide a supply voltage Vdd _ m corresponding to the magnitude of the envelope signal Venv to the supply terminals of the voltage generator 12, the supply voltage Vdd _ m comprising the supply voltage Vdd or the adjustment voltage Vm, as shown in fig. 3.
By adopting the technical scheme, the third control signal SW3 is used for controlling the power supply selector 22 to provide the power supply voltage Vdd _ m corresponding to the amplitude of the envelope signal Venv for the power supply end of the push-pull circuit, when the amplitude of the envelope signal Venv is smaller, the linear amplification amplitude of the corresponding linear module 1 is smaller, the push-pull circuit does not need a very high power supply voltage Vdd _ m, the corresponding modulation voltage Vpa and partial drain drive current Im can be provided for the drain of the power amplifier 5, at the moment, the third control signal SW3 is input with a low-level signal, and the power supply selector 22 is controlled to provide the adjustment voltage Vm for the power supply end of the push-pull circuit; when the amplitude of the envelope signal Venv is relatively large, the amplitude of the corresponding linear amplification of the linear module 1 is relatively large, and at this time, the third control signal SW3 inputs a high-level signal to control the power supply selector 22 to provide the power supply voltage Vdd to the power supply terminal of the push-pull circuit. The present embodiment controls the supply voltage Vdd _ m of the push-pull circuit to vary with the amplitude of the envelope signal Venv according to the envelope tracking technique, which improves the efficiency of the linear module 1 and reduces the loss of the linear module 1.
If the adjustment voltage Vm is greater than the power supply voltage Vdd, when the amplitude of the envelope signal Venv is relatively small, the third control signal SW3 inputs a high-level signal to control the power supply selector 22 to provide the power supply voltage Vdd to the power supply terminal of the push-pull circuit; when the amplitude of the envelope signal Venv is relatively large, the third control signal SW3 inputs a low-level signal to control the power supply selector 22 to provide the adjustment Vm to the power supply terminal of the push-pull circuit.
On the basis of the above embodiment, the digital control module 3 further includes a low-pass filter 31 and an analog-to-digital converter 32, and the envelope signal Venv is processed by the low-pass filter 31 and the analog-to-digital converter 32 in sequence to output an analog-to-digital conversion signal AD.
It should be noted that, an output end of the low-pass filter 31 is connected to an input end of the analog-to-digital converter 32, the envelope signal Venv is sequentially subjected to high-frequency denoising by the low-pass filter 31, and is subjected to analog-to-digital conversion of an amplitude of the envelope signal Venv by the analog-to-digital converter 32, so that the analog signal is converted into a digital signal, and an analog-to-digital conversion signal AD is output.
By adopting the technical scheme, the envelope signal Venv is denoised at high frequency, after analog-to-digital conversion, the analog-to-digital conversion signal AD is conveniently input into the first comparison unit 33 for comparison and the logic control unit 35 for logic analysis so as to output the first control signal SW1 and the second control signal SW2, and the analog-to-digital conversion signal AD is conveniently input into the second comparison unit 34 for comparison so as to output the third control signal SW 3.
On the basis of the above embodiment, further, the first comparing unit 33 includes a first comparator 331, a first hysteresis comparator 332 and a second comparator 333, and the second comparing unit 34 is a second hysteresis comparator.
It should be noted that the analog-to-digital conversion signal AD is input to the non-inverting input terminal of the first comparator 331 and compared with the first reference voltage Vref1 at the inverting input terminal to output the first digital signal C1, the analog-to-digital conversion signal AD is input to the inverting input terminal of the first hysteresis comparator 332 and compared with the second reference voltage Vref1 at the inverting input terminal within the first hysteresis width Vh1 to output the second digital signal C2, and the analog-to-digital conversion signal AD is input to the inverting input terminal of the second comparator 333 and compared with the third reference voltage Vref3 at the inverting input terminal to output the third digital signal C3; the first digital signal C1, the second digital signal C2 and the third digital signal C3 are input to the logic control unit 35 for logic analysis, and the first control signal SW1 and the second control signal SW2 are output; the analog-to-digital converted signal AD is input to the positive input terminal of the second hysteresis comparator and compared with the reference voltage Vref4 of the negative input terminal within the second hysteresis width Vh2 to output the third control signal SW3 (described with reference to fig. 4).
Specifically, the logic control unit 35 performs a logic analysis as follows: when the first digital signal C1, the second digital signal C2 and the third digital signal C3 are respectively 1, the first control signal SW1 is at a high level, and the second control signal SW2 is at a high level; when the first digital signal C1, the second digital signal C2 and the third digital signal C3 are respectively 1, 1 and 0, the first control signal SW1 is at a high level, and the second control signal SW2 is at a low level; when the first digital signal C1, the second digital signal C2 and the third digital signal C3 have logic 1, 0 and 0, respectively, the first control signal SW1 is at a low level and the second control signal SW2 is at a high level; when the first, second and third digital signals C1, C2 and C3 are respectively 0, 0 and 0, the first control signal SW1 is at low level and the second control signal SW2 is at low level.
By adopting the technical scheme, according to the tracking of the envelope signal Venv, the first control signal SW1 and the second control signal SW2 corresponding to the amplitude of the envelope signal Venv are output and are used for controlling the switch conversion module 4 to provide the modulation current Ih for the drain electrode of the power amplifier 5; meanwhile, the analog-to-digital conversion signal AD is input into the positive input end of the second hysteresis comparator and is compared with the reference voltage Vref4 of the negative input end within the second hysteresis width Vh2, and then a third control signal SW3 corresponding to the amplitude of the envelope signal Venv is output, so that the power supply terminal power supply voltage Vdd _ m of the push-pull circuit is controlled to be switched between the power supply voltage Vdd and the regulation voltage Vm. When the amplitude of the input envelope signal Venv is relatively small, the third control signal SW3 outputs a low level to control the power supply selector 22 to provide the adjustment voltage Vm to the power supply terminal of the push-pull circuit; when the amplitude of the envelope signal Venv is relatively large, the third control signal SW3 outputs a high level signal to control the power supply selector 22 to supply the power supply voltage Vdd to the power supply terminal of the push-pull circuit.
On the basis of the above embodiment, further, the first selection switch 43 includes a first switch tube S1 and a second switch tube S2, the first output terminal SD11 of the first gate driver 41 is connected to the input control terminal of the first switch tube S1, the second output terminal SD12 of the first gate driver 41 is connected to the input control terminal of the second switch tube S2, the source of the first switch tube S1 is connected to the drain of the second switch tube S2 and serves as the output terminal of the first selection switch 43, the source of the second switch tube S2 is grounded, and the drain of the first switch tube S1 is powered by the power voltage Vdd;
the second selection switch 44 includes a third switch tube S3 and a fourth switch tube S4, the first output terminal SD21 of the second gate driver 42 is connected to the input control terminal of the third switch tube S3, the second output terminal SD22 of the second gate driver 42 is connected to the input control terminal of the fourth switch tube S4, the source of the third switch tube S3 is connected to the drain of the fourth switch tube S4 and serves as the output terminal of the second selection switch 44, the source of the fourth switch tube S4 is grounded, and the drain of the third switch tube S3 is powered by the adjustment voltage Vm (see fig. 5).
By adopting the above technical solution, the power supply voltage Vdd is inputted to the drain of the first switch tube S1 to supply power to the first selection switch 43, the adjustment voltage Vm is inputted to the drain of the third switch tube S3 to supply power to the second selection switch 44, the first control signal SW1 controls the first switch tube S1 and the second switch tube S2 to be turned on and off through the first gate driver 41, the second control signal SW2 controls the third switch tube S3 and the fourth switch tube S4 to be turned on and off through the second gate driver 42, and the operation of the first selection switch 43 and the second selection switch 44 is as follows:
1) when the first control signal SW1 and the second control signal SW2 are both at a high level, the first switch tube S1 of the first selection switch 43 is turned on, the second switch tube S2 is turned off, and the third switch tube S3 of the second selection switch 44 is turned on, and the fourth switch tube S4 is turned off.
2) When the first control signal SW1 and the second control signal SW2 are both at a low level, the first switch tube S1 of the first selection switch 43 is turned off, the second switch tube S2 is turned on, the third switch tube S3 of the second selection switch 44 is turned off, and the fourth switch tube S4 is turned on.
3) When the first control signal SW1 is at a high level and the second control signal SW2 is at a low level, the first switch tube S1 of the first selection switch 43 is turned on, the second switch tube S2 is turned off, the third switch tube S3 of the second selection switch 44 is turned off, and the fourth switch tube S4 is turned on.
4) When the first control signal SW1 is at a low level and the second control signal SW2 is at a high level, the first switch tube S1 of the first selection switch 43 is turned off, the second switch tube S2 is turned on, the third switch tube S3 of the second selection switch 44 is turned on, and the fourth switch tube S4 is turned off.
On the basis of the above embodiment, further, the output terminal of the first selection switch 43 is connected to the drain of the power amplifier 5 through the first inductor 45; the output end of the second selection switch 44 is connected with the drain of the power amplifier 5 through a second inductor 46 and a first diode 47 in sequence; the inductance values of the first inductor 45 and the second inductor 46 are equal.
By adopting the above technical scheme, the switching conversion module 4 outputs the modulation current corresponding to the amplitude of the envelope signal Venv through the first inductor 45 and the second inductor 46, and the switching conversion module 4 specifically works as follows:
1) when the first control signal SW1 and the second control signal SW2 are both at a high level, the first switch tube S1 of the first selection switch 43 is turned on, the second switch tube S2 is turned off, the third switch tube S3 of the second selection switch 44 is turned on, the fourth switch tube S4 is turned off, the power supply voltage Vdd of the first selection switch 43 charges the first inductor 45, the power supply voltage Vm of the second selection switch 44 charges the second inductor 46, and the switch conversion module 4 rapidly increases the modulation current Ih, which is provided by the drain of the power amplifier 5 and corresponds to the amplitude of the envelope signal Venv.
2) When the first control signal SW1 and the second control signal SW2 are both at a low level, the first switch tube S1 of the first selection switch 43 is turned off, the second switch tube S2 is turned on, the third switch tube S3 of the second selection switch 44 is turned off, the fourth switch tube S4 is turned on, the first inductor 45 and the second inductor 46 are discharged through the second switch tube S2 and the fourth switch tube S4, respectively, and the modulation current Ih, which is provided by the switch conversion module 4 to the drain of the power amplifier 5 and corresponds to the amplitude of the envelope signal Venv, is rapidly reduced.
3) When the first control signal SW1 is at a high level and the second control signal SW2 is at a low level, the first switch tube S1 of the first selection switch 43 is turned on, the second switch tube S2 is turned off, the third switch tube S3 of the second selection switch 44 is turned off, the fourth switch tube S4 is turned on, the power voltage Vdd of the first selection switch 43 charges the first inductor 45, the second inductor 46 is discharged through the fourth switch tube S4, and the modulation current Ih, which is provided by the switch conversion module 4 to the drain of the power amplifier 5 and corresponds to the amplitude of the envelope signal Venv, is slowly increased.
4) When the first control signal SW1 is at a low level and the second control signal SW2 is at a high level, the first switch tube S1 of the first selection switch 43 is turned off, the second switch tube S2 is turned on, the third switch tube S3 of the second selection switch 44 is turned on, the fourth switch tube S4 is turned off, the first inductor 45 is discharged through the second switch tube S2, the power voltage Vm of the second selection switch 44 charges the second inductor 46, and the modulation current Ih, which is provided by the drain of the power amplifier 5 and corresponds to the amplitude of the envelope signal Venv, is slowly reduced by the switch conversion module 4.
Based on the above embodiment, further, the power selector 22 includes a second diode 221 and a fifth switching tube 222, the output terminal of the dc-dc voltage converter 21 is connected to the anode of the second diode 221, the cathode of the second diode 221 is connected to the source of the fifth switching tube 222 and the power supply terminal of the voltage current generator 12, the power supply voltage Vdd is input to the drain of the fifth switching tube 222, a third control signal SW3 is input to the input control terminal of the fifth switching tube 222, and the supply voltage Vdd _ m of the voltage current generator 12 is switched between the power supply voltage Vdd and the adjustment voltage Vm by controlling the on and off of the fifth switching tube 222 (see fig. 3).
With the above technical solution, the third control signal SW3 is utilized to control the power supply voltage Vdd _ m at the power end of the push-pull circuit by controlling the on/off of the fifth switching tube 222. When the SW3 outputs a high level, the fifth switching tube 222 is turned on, and due to the unidirectional conduction of the second diode 221, the supply voltage Vdd _ m of the push-pull circuit is Vdd, and when the SW3 outputs a low level, the fifth switching tube 222 is turned off, and the supply voltage Vdd _ m of the push-pull circuit is Vm.
On the basis of the above embodiment, further, the push-pull circuit further includes a dc bias BT for providing a dc bias voltage Vbias to the input terminals of the N-type MOS transistor M1 and the P-type MOS transistor M2.
By adopting the technical scheme, the direct-current bias voltage Vbias is provided for the input ends of the N-type MOS transistor M1 and the P-type MOS transistor M2, so that the signal cross-over distortion input into the push-pull circuit is prevented.
The invention also provides a hybrid power supply modulation circuit, which comprises the hybrid power supply modulator.
The above description is only a preferred embodiment of the present invention and is not intended to limit the present invention, and various modifications and changes may be made by those skilled in the art. Any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the protection scope of the present invention.
Claims (11)
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102629854A (en) * | 2011-02-01 | 2012-08-08 | 联发科技（新加坡）私人有限公司 | Integrated circuit, wireless communication unit and method for providing a power supply |
| CN104521137A (en) * | 2012-03-30 | 2015-04-15 | 努吉拉有限公司 | Determination of envelope shaping and signal path predistortion of an ET amplification stage using device characterisation data |
| CN107565910A (en) * | 2017-08-31 | 2018-01-09 | 东南大学 | A kind of envelop modulator and envelope tracking power amplifier |
| CN109478870A (en) * | 2016-07-29 | 2019-03-15 | 高通股份有限公司 | It is tracked with the envelope for carrying out selection between booster power and battery supply |
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| GB2482738B (en) * | 2010-08-13 | 2015-05-13 | Nujira Ltd | Switch mode power supply for envelope tracking |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102629854A (en) * | 2011-02-01 | 2012-08-08 | 联发科技（新加坡）私人有限公司 | Integrated circuit, wireless communication unit and method for providing a power supply |
| CN104521137A (en) * | 2012-03-30 | 2015-04-15 | 努吉拉有限公司 | Determination of envelope shaping and signal path predistortion of an ET amplification stage using device characterisation data |
| CN109478870A (en) * | 2016-07-29 | 2019-03-15 | 高通股份有限公司 | It is tracked with the envelope for carrying out selection between booster power and battery supply |
| CN107565910A (en) * | 2017-08-31 | 2018-01-09 | 东南大学 | A kind of envelop modulator and envelope tracking power amplifier |
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