CN110867651A - Zero-order resonance patch antenna and transmission type low-cost monopulse phased array antenna device - Google Patents
Zero-order resonance patch antenna and transmission type low-cost monopulse phased array antenna device Download PDFInfo
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- CN110867651A CN110867651A CN201911157233.1A CN201911157233A CN110867651A CN 110867651 A CN110867651 A CN 110867651A CN 201911157233 A CN201911157233 A CN 201911157233A CN 110867651 A CN110867651 A CN 110867651A
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
- H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/48—Earthing means; Earth screens; Counterpoises
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
- H01Q21/061—Two dimensional planar arrays
- H01Q21/065—Patch antenna array
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
Abstract
The invention relates to a zero-order resonance patch antenna and a transmission type low-cost monopulse phased-array antenna device, which are characterized in that a circular microstrip patch antenna is arranged in the center of a dielectric substrate, four rectangular patches are symmetrically arranged around the circular microstrip patch antenna to form a zero-order resonance structure, the rectangular patches are connected with a ground plate through metal through holes, the gap width between the circular patches and the rectangular patches is g, the circular patches are fed by a coaxial probe to excite TM (transverse magnetic) phase01The mold, rectangular patch and circular patch form a mushroom-type structure, wherein CgIs a slot capacitor, rectangularThe capacitor C and the inductor L are respectively induced by the patch and the metal through hole, and the capacitor of the circular patch to the ground is CfSurface parasitic current constitutes inductance Lf2The coaxial probe has an inductive inductance of Lf1(ii) a By
Description
The technical field is as follows:
the invention relates to the technical field of array antenna sensor devices, in particular to a zero-order resonance patch antenna with simple structure, low cost and full polarization sensing and a transmission type low-cost monopulse phased array antenna device.
Background art:
the phased array radar breaks through a plurality of limitations of the original mechanical scanning radar as a new field of radar development, and has the advantages of flexible beam pointing, variable beam shape, controllable space power distribution, large power, small volume, light weight, high reliability and the like. Due to the characteristics of the phased array, the phased array radar has performance advantages, high reliability and high cost performance which cannot be compared with the traditional seeker, and also has wide application prospect and development potential. Phased array technology has emerged in the 30's of the 20 th century. Currently, the development and testing of phased array radars has begun in military developed countries such as the united states, russia, united kingdom and germany. In recent years, low cost, intelligent, wide angle coverage is an inevitable trend in future radar technology. The antenna, as an important front-end component of an electronic system, is also continuously developed and advanced in the aspects of wide-angle scanning, low sidelobe, small size, high efficiency, interference resistance, low cost and the like. In recent years, in the field of microwave technology, phased array radar and metamaterial technology appear, and new design theory and technical means are brought for effectively improving the electrical performance and the integrated structural performance of the traditional antenna.
Approximately 70% to 80% of the cost of two-dimensional scanning phased array radar is concentrated on antenna systems. In the traditional method, M multiplied by N phase shifters and corresponding radiation units are needed for realizing the two-dimensional scanning phased radar with M rows and N columns, and the cost of the phase shift units is high, so that the manufacturing cost of a phased array is quite high, and the wide application of the phased array radar in tactics is greatly limited. Therefore, the high cost is often one of the important reasons for limiting the wide use of the two-dimensional scanning phased array radar. One approach to solve the problem of high cost of two-dimensional scanning phased array radar is to reduce the manufacturing cost of the phase shift unit or the T/R assembly. With the development of electronic technology. The price of the phase-shifting unit or the T/R assembly is also reduced, but the number of the units is huge, so that the price of the whole radar is still at a higher level; another approach is to reduce the number of phase shifting elements or T/R modules, such as by using a sparse array, a circular grid array, etc., but the reduction in the number of elements is limited and it is difficult to achieve a substantial cost reduction.
The invention content is as follows:
aiming at the defects and shortcomings in the prior art, the invention provides a zero-order resonance patch antenna and a transmission type low-cost monopulse phased array antenna device which have the advantages of simple structure, low cost and full polarization sensing.
The invention is achieved by the following measures:
a zero-order resonance patch antenna is characterized in that a circular microstrip patch antenna is arranged in the center of a dielectric substrate, four rectangular patches are symmetrically arranged around the circular microstrip patch antenna to form a zero-order resonance structure, the rectangular patches are connected with a ground plate through metal through holes, the width of a gap between the circular patches and the rectangular patches is g, the circular patches are fed by a coaxial probe to excite a TM (transverse magnetic) mode01The mold, rectangular patch and circular patch form a mushroom-shaped structure, which constructs a composite left-right hand transmission line structure, and excites zero-order resonant mode by gap coupling to convert TM into linear mode01The mode directional diagram and the ZOR mode directional diagram are superposed to achieve the purpose of widening the wave beam, wherein CgThe rectangular patch and the metal through hole respectively induce a capacitor C and an inductor L for the gap capacitor, and the capacitor of the circular patch to the ground is CfSurface parasitic current constitutes inductance Lf2The coaxial probe has an inductive inductance of Lf1(ii) a By
It can be known that when equivalent inductance and equivalent capacitance increase, resonance frequency point reduces to the miniaturization of antenna can be realized to the parameter of accessible change gap width, paster size and through-hole.
The parameters of the zero-order resonance patch antenna can adopt the following indexes: radius of circular patch: 5.1 mm; rectangular patch length: 5.2 mm; width of rectangular patch: 5 mm; gap width between circular patch and rectangular patch: 0.4 mm; thickness of the lower dielectric substrate: 2 mm; thickness of the upper dielectric substrate: 1 mm.
The invention also provides a zero-order resonance patch antenna unit array which is characterized in that the zero-order resonance patch antenna is adopted as an antenna unit, and a separated circular wave scrambler is loaded above the antenna array.
The invention also provides a transmission type low-cost monopulse phased antenna device which is characterized by being provided with a microstrip antenna array, wherein the microstrip antenna array is provided with more than two sub-arrays, and the sub-arrays are provided with more than two zero-order resonant patch antenna units; the micro-strip antenna array adopts a single-pulse feed network for feeding, and a Radant phase shifter for scanning on a pitching surface is arranged in front of the micro-strip antenna array; the RADAR lens completes one-dimensional beam scanning through one group of phase shifters, then scans the beam in the other direction through the other group of phase shifters, and realizes two-dimensional beam scanning through the two groups of phase shifters.
The microstrip antenna array of the present invention is preferably provided with four sub-arrays, which are respectively marked as sub-array a, sub-array B, sub-array C, and sub-array D, and each sub-array is provided with 6 × 6 antenna units, so that the first-stage beam forming network:
Σ1＝A+B (1)
Δ1＝A-B (2)
Σ2＝C+D (3)
Δ2＝C-D (4)
second stage beam forming network:
Σ＝A+B+C+D (5)
Δe＝A+B-C-D (6)
Δa＝A-B+C-D (7)
the invention is based on the miniaturized microstrip antenna array of zero-refraction metamaterial wide beam, uses the high-power phase shifter and can scan on the azimuth plane; the Radant lens is arranged in front of the microstrip antenna array, scanning is carried out on a pitching surface, and due to the introduction of the Radant lens phase shifter, the cost of the phased array antenna is obviously reduced.
Description of the drawings:
fig. 1 is a schematic structural diagram of a transmission type low-cost monopulse phased array antenna device according to the present invention.
Fig. 2 is a schematic diagram of the phased array antenna of the present invention.
Fig. 3 is an equivalent circuit diagram of a zero-order resonant patch antenna according to the present invention.
Fig. 4 is a model of a zero-order resonant patch antenna and an antenna array in the present invention, in which fig. 4(a) is a model of an antenna unit that hides an upper dielectric substrate, fig. 4(b) is a model of an antenna unit that loads a spoiler, fig. 4(c) is a model of an antenna array, and fig. 4(d) is a model of an antenna structure.
Fig. 5 is a schematic diagram of a radon lens phase shifter and a plate structure thereof in the present invention, wherein fig. 5(a) is a model diagram of the radon lens phase shifter, and fig. 5(b) is a diagram of a structure between plates. FIG. 6 is a phase shifter for a displaced Radant lens of the present invention.
FIG. 7 is a six-shift Radant lens phase shifter of the present invention.
Fig. 8 is a simulation graph of an antenna unit in an embodiment of the present invention.
Fig. 9 is a simulated standing wave curve of an antenna unit in an embodiment of the present invention.
Fig. 10 is a simulated pattern of an antenna element in an embodiment of the invention.
Fig. 11 is a return loss simulation result curve of the microstrip antenna array loaded with the scrambler in the embodiment of the present invention.
Fig. 12 is a simulation result curve of the voltage standing wave ratio of the microstrip antenna array loaded with the scrambler in the embodiment of the present invention.
Figure 13 is a radiation pattern of a loaded spoiler microstrip antenna array in an embodiment of the present invention,
fig. 14 is a simulation result of a three-dimensional directional diagram of a loading spoiler microstrip antenna array in an embodiment of the present invention.
Reference numerals: microstrip line 1, diode 2, parallel metal plate 3, diode circuit 4.
The specific implementation mode is as follows:
in the prior art, about 70% -80% of the cost of the two-dimensional scanning phased array radar is concentrated on an antenna system. In the traditional method, M multiplied by N phase shifters and corresponding radiation units are needed for realizing the two-dimensional scanning phased radar with M rows and N columns, and the cost of the phase shift units is high, so that the manufacturing cost of a phased array is quite high, and the wide application of the phased array radar in tactics is greatly limited. Therefore, the high cost is often one of the important reasons for limiting the wide use of the two-dimensional scanning phased array radar. One approach to solve the problem of high cost of two-dimensional scanning phased array radar is to reduce the manufacturing cost of the phase shift unit or the T/R assembly. With the development of electronic technology. The price of the phase-shifting unit or the T/R assembly is also reduced, but the number of the units is huge, so that the price of the whole radar is still at a higher level; another approach is to reduce the number of phase shifting elements or T/R modules, such as by using a sparse array, a circular grid array, etc., but the reduction in the number of elements is limited and it is difficult to achieve a substantial cost reduction.
The invention provides a polarization sensitive array antenna system device based on active-passive combination based on the technical requirements of a radar guidance and electronic reconnaissance system, wherein the polarization sensitive antenna system is formed by combining a broadband passive antenna array and a dual-polarization active antenna array; a metal grid structure is introduced to realize good isolation between the active and passive antennas, and meanwhile, the radiation pattern of the broadband passive antenna unit is restrained, and the beam width performance of the antenna is improved; the passive antenna realizes the polarization sensitivity to incident electromagnetic waves on the basis of an anisotropic unit along with the carrier; the active antenna adopts an orthogonal dual-polarized antenna unit to realize the sensing and receiving of two orthogonal polarization components of incident electromagnetic waves, and the whole active and passive composite antenna system is a polarization-sensitive radio frequency system and has the advantages of simple structure, low cost and full-polarization sensing. The active and passive composite polarization sensitive antenna system can be applied to electronic reconnaissance and guidance systems of satellite-borne, airborne and missile-borne platforms and the like, and has important application value.
The invention is based on the miniaturized microstrip antenna array of zero-refraction metamaterial wide beam, and can scan on the azimuth plane by using the high-power phase shifter and the single-pulse feed network; the Radant lens is arranged in front of the microstrip antenna array, scanning is carried out on a pitching surface, and due to the introduction of the Radant lens phase shifter, the cost of the phased array antenna is obviously reduced. The phase shifter is a key microwave element of the feed system, and the corresponding circuit for controlling the phase shift of the phase shifter is also an important circuit. Phased array radars have thousands of elements, each with a phase shifter, and the performance and cost of the phase shifters greatly affect the performance and cost of the radar. The RADAR lens completes one-dimensional beam scanning through one group of phase shifters, and then scans the beam in the other direction through the other group of phase shifters, so that the two groups of phase shifters realize two-dimensional beam scanning. If the number of the phase shifter groups for completing the row scanning is M and the number of the phase shifter groups for column scanning is N, the number of the phase shifters for realizing the two-dimensional scanning function of the phased array antenna can be reduced from M multiplied by N to M + N. In order to improve the wide-angle scanning performance of the phased array antenna, a project proposes a micro-strip antenna array scheme adopting a metamaterial technology; based on the principle of zero-refraction metamaterial and electromagnetic band gap structure, the zero-order resonant patch antenna covered by the miniaturized wide beam is designed. According to the antenna, the mushroom-type zero-order resonance structure is loaded in the central symmetry around the circular microstrip patch antenna, the TM01 mode excited by the circular patch and the ZOR mode excited by the mushroom-type patch are superposed, the antenna is miniaturized, the wave beam coverage range of the antenna is widened, the coupling between antenna array elements is reduced remarkably, surface waves are inhibited, and the radiation efficiency of the antenna is improved. Furthermore, the invention provides a realization scheme of the wide-angle scanning high-efficiency phased array antenna based on the comprehensive loading of the metamaterial and the wave disturbing structure, and the phased array monopulse antenna with low cost, miniaturization and high performance is realized.
The invention is based on the miniaturized microstrip antenna array of zero-refraction metamaterial wide beam, and can scan on the azimuth plane by using the high-power phase shifter and the single-pulse feed network; the Radant lens is arranged in front of the microstrip antenna array, scanning is carried out on a pitching surface, and due to the introduction of the Radant lens phase shifter, the cost of the phased array antenna is obviously reduced. The radon lens is composed of a diode-controlled medium. Within the lens, the propagation of the electric field is confined between parallel metal plates. The medium between the metal plates is made up of metal strips, between which a number of diodes are mounted via dielectric linings, the control principle being that the phase is changed by controlling the diodes to be on or off, while the phase shift of each diode strip is controlled by the degree of metallization. Its maximum phase lag is 360 modulo. The radon lens can realize the control of one-dimensional electric scanning in the E plane. The number of diodes at each radon lens level depends on the corresponding number of binary code bits. Radon lens antennas are less costly than phased array antennas constructed of discrete elements, and do not require separate cards, connectors, components, and radiating elements. The lens itself, i.e. the antenna, is formed by long strips, which are only two or three in total. In production, the diodes can be soldered to these strips using automated equipment. The control circuitry for a radon lens antenna is simpler than for a discrete phased array antenna. For a hybrid array formed by N rows of Radant lenses and M columns of microstrip antenna arrays, only N + M row-column phases need to be controlled. Meanwhile, because the microstrip antenna is also in a low-cost antenna form, the high-power phase shifter adopts a 6-bit unidirectional double-ring closed ferrite phase shifter which can at least process the peak power of 450W and the average power of 60W, and the cost of the ferrite phase shifter is lower; the single-pulse power distribution network of the microstrip antenna array is also realized by adopting a microstrip circuit, and the processing cost and the material cost are both controllable. The basic block diagram of the low-cost transmission type composite structure monopulse phased array antenna structure designed by the invention is shown in figure 1.
First stage beam forming network: sigma1＝A+B (1)，Δ1＝A-B (2)；Σ2＝C+D (3)； Δ2＝C-D(4)；
Second stage beam forming network:
Σ＝A+B+C+D (5)，Δe＝A+B-C-D (6)，Δa＝A-B+C-D (7)；
in a phased array implementation scheme based on a Radant lens and a metamaterial technology, a structural block diagram of a principle prototype is shown in FIG. 2, and in the one-dimensional direction of scanning beam control, the phased array antenna can be divided into an active phased array antenna and a passive phased array antenna according to the type of the phased array antenna; the azimuth control of the active phased array antenna is realized by adopting a microwave transceiving component (T/R); the passive phased array antenna is controlled by a phase shifter. According to the working mode and the technical requirements of the radar, the invention adopts a phase shifter combination mode to realize a one-dimensional azimuth beam control mode.
Microstrip patch antennas are widely used due to their low profile, light weight, and ease of processing. The half-power lobe widths of the radiation patterns of the E plane and the H plane of the conventional rectangular microstrip patch antenna are relatively narrow, so that the search and design of a microstrip antenna with a relatively wide beam and relatively high low elevation gain is a hot spot of current research. The small-sized wide-beam zero-order resonant patch antenna is designed based on the zero-refraction metamaterial principle.
According to the antenna, the mushroom-type zero-order resonance structure is loaded symmetrically around the circular microstrip patch antenna, the TM01 mode excited by the circular patch and the ZOR mode excited by the mushroom-type patch are superposed, and the wave beam of the antenna is widened while the miniaturization of the antenna is realized. The equivalent circuit diagram of the antenna is shown in fig. 3.
The rectangular patch is connected with the grounding plate through the metal through hole, the width of a gap between the rectangular patch and the rectangular patch is g, the circular patch is fed by a coaxial probe, a TM01 mode is excited, the rectangular patch and the circular patch form a mushroom-shaped structure, the structure constructs a composite left-hand and right-hand transmission line structure, a zero-order resonant mode is excited through gap coupling, a directional diagram of the TM01 mode and a directional diagram of a ZOR mode are superposed, the purpose of widening a beam is achieved, Cg is a gap capacitor, the rectangular patch and the metal through hole respectively induce a capacitor C and an inductor L, and the circular patch has a capacitance to ground of CfThe surface parasitic current of which constitutes an inductance Lf2The coaxial probe has an inductive inductance of Lf1。
The resonance frequency of the resonator conforming to the structure of the left-right hand transmission line occurs when the physical length of the resonator is an integral multiple of a half wavelength, as shown in the following formula, and is zero order when the electrical length is 0.
For a maximum operating frequency, according to the theory of microstrip antennas, the thickness of the dielectric plate preferably satisfies:
the resonant frequency of a circular patch can generally be calculated by the following equation
To take into account the influence of a dielectric plate or the like, an equivalent radius a is introducede
The radius thus calculated is about 4 mm.
The resonance mode is exactly the same as the electric field distribution at various locations of the resonator and is independent of the physical length of the resonator.
When the equivalent inductance and the equivalent capacitance are increased, the resonance frequency point is reduced, and therefore the miniaturization of the antenna can be achieved by changing the width of the gap, the size of the patch and the parameters of the through hole.
In order to further expand the coverage range of wave beams and improve the scanning angle of the phased array antenna, the wave disturbing technology is introduced on the basis of loading the metamaterial, a separated circular wave disturbing device structure is loaded above the microstrip antenna array, the structure is also realized by adopting a printed circuit, and the cost is not increased obviously. The new antenna element and array model designed is shown in fig. 4.
Example (b):
the invention designs a specific low-cost single-pulse phased array antenna array device with a transmission type composite structure, performs scheme design and simulation optimization in an X wave band, and comprises a wide-beam antenna radiation array design based on metamaterial loading, a Radant lens performs performance simulation and optimization design on the antenna array by adopting full-wave electromagnetic simulation software, and the feasibility and the effectiveness of the array antenna device provided by the invention are verified by a simulation experiment result.
The Radant lens phase shifter is formed by a plurality of parallel metal plates along the electric field
Are arranged in sequence at certain intervals. A plurality of parallel dielectric slabs are arranged between the parallel metal slabs, the loss of the dielectric slabs is small, the dielectric constant of the dielectric slabs is close to that of air, two parallel metal microstrip lines are printed on the dielectric slabs, and a diode circuit consisting of the microstrip lines, the inductors and the diodes is arranged between the metal microstrip lines. The radon lens phase shifter structure is shown in fig. 5.
In the parallel metal plates, each dielectric layer has many diodes arranged, these diodes and dielectric layers form basic phase shifter units, different phase shifter units are placed in the parallel metal plates for combination, and different phase shifter units in each parallel plate are combined together to produce different phase shifts, so that a phase shifter block is formed, and under the condition of electric field, the phase shifter block can be used for shifting the phase of the phase-shifted signal
In the direction, the value of the phase shift block in each parallel plate can be set, and the adjacent phase shift blocks form a phase gradient difference capable of generating an electric field when an electromagnetic wave passes through the phase shifter
The direction changes the propagation direction. Bias voltage is loaded on two parallel microstrip lines of the dielectric slab, and the conduction and the cut-off of the diode in the microstrip line are controlled by controlling the positive and negative bias voltage input to the microstrip line, so that the size of the phase shifter between the parallel metal plates is changed. Therefore, some driving devices can be used for loading a phase control program to control the microstrip lines between the flat metal plates, and phase gradients are generated in the direction of the electric fieldThe phase of the electromagnetic wave entering the parallel metal plates is changed, so that the scanning of the pattern can be formed.
The designed phase shifter blocks are combined among the parallel metal plates to form a one-bit Radant lens phase shifter capable of shifting the phase of electromagnetic waves incident between the parallel metal plates by 0-360 degrees, and gradient change of phase shift is formed between different parallel metal plates along the direction of an electric field, so that the electromagnetic waves radiated by the antenna array are incident between different parallel metal plates, and the gradient difference of phase change is formed along the direction of the electric field, thereby changing the transmission direction of the incident electromagnetic waves. A one-bit radon lens phase shifter model is shown in fig. 6.
15 layers of phase shifter units are placed in each pair of parallel metal plates, the 15 layers of phase shifter units form 5 phase shifter blocks, and one-bit Radant lens phase shifter capable of shifting the phase at 0-360 degrees is formed by opening or closing different phase shifter blocks in each pair of parallel metal plates. In order to form sum and difference beams to carry out direction finding and distance measuring on a target, a front surface of a phased array antenna is divided into 4 sub-arrays, each sub-array is formed by 6 multiplied by 6 antenna units, a Radant lens phase shifter is loaded on an antenna array, and after electromagnetic waves radiated by the antenna pass through a lens, beam scanning of a directional pattern is formed in the pitching direction. According to the design requirement of the phased array antenna, a phase shifter is arranged along the direction of an electric field to form a six-displacement Radant lens phase shifter, and the phase shifter model is shown in figure 7.
Based on the principle of zero-refraction metamaterial, the miniaturized wide-beam zero-order resonant patch antenna is designed. In order to further expand the beam coverage range and improve the scanning angle of the phased array antenna, a wave disturbing technology is introduced. And finally forming the wide-beam microstrip antenna array loaded with the wave scrambler. The RogersR03003 dielectric substrate with the dielectric constant of 3, the loss tangent of 0.0013 and the thickness of 1mm is selected for the experiment, and an HFSS simulation antenna model is used. And finally obtaining main parameters of the loaded zero-order resonant patch antenna unit at the resonant frequency by optimizing the position of the feed point, the size of the loaded rectangular patch, the radius of the circular patch and other parameters. It can be seen from fig. 8 and 9 that the resonant frequency of the antenna is 11.3GHz, the standing-wave ratio at the resonant frequency is about 1.22, the matching is good, and the bandwidth of the antenna is about 160 MHz. It can be seen from fig. 10 that the E-plane is 110 deg., the H-plane is 110 deg., and there are wider beams.
The analysis result of the loaded scrambler microstrip antenna array is as follows
Fig. 11 and 12 are graphs of simulation results of return loss and voltage standing wave ratio of the loaded spoiler microstrip antenna array, respectively, and it can be seen that the resonant frequency of the antenna is at 11.3GHz, the standing wave ratio at the resonant frequency is 1.19, and better matching is achieved. Fig. 13 is a radiation pattern of the loading scrambler microstrip antenna array, and it can be seen that the antenna gain reaches 25dB, and the main-side lobe ratio is about 13 dB. Fig. 14 is a simulation result of a three-dimensional directional diagram of a loading spoiler microstrip antenna array.
Claims (5)
1. A zero-order resonance patch antenna is characterized in that a circular microstrip patch antenna is arranged in the center of a dielectric substrate, four rectangular patches are symmetrically arranged around the circular microstrip patch antenna to form a zero-order resonance structure, the rectangular patches are connected with a ground plate through metal through holes, the width of a gap between the circular patches and the rectangular patches is g, the circular patches are fed by a coaxial probe to excite a TM (transverse magnetic) mode01The mold, rectangular patch and circular patch form a mushroom-shaped structure, which constructs a composite left-right hand transmission line structure, and excites zero-order resonant mode by gap coupling to convert TM into linear mode01The mode directional diagram and the ZOR mode directional diagram are superposed to achieve the purpose of widening the wave beam, wherein CgThe rectangular patch and the metal through hole respectively induce a capacitor C and an inductor L for the gap capacitor, and the capacitor of the circular patch to the ground is CfSurface parasitic current constitutes inductance Lf2The coaxial probe has an inductive inductance of Lf1(ii) a By
It can be known that when equivalent inductance and equivalent capacitance increase, resonance frequency point reduces to the miniaturization of antenna can be realized to the parameter of accessible change gap width, paster size and through-hole.
2. A zero-order resonant patch antenna according to claim 1, wherein the parameters of the zero-order resonant patch antenna are as follows: radius of circular patch: 5.1 mm; rectangular patch length: 5.2 mm; width of rectangular patch: 5 mm; gap width between circular patch and rectangular patch: 0.4 mm; thickness of the lower dielectric substrate: 2 mm; thickness of the upper dielectric substrate: 1 mm.
3. A zero-order resonant patch antenna element array, characterized in that the zero-order resonant patch antenna according to claim 1 or 2 is used as an antenna element, and a separate circular-ring-shaped wave-spoiler is loaded above the antenna array.
4. A transmission type low-cost monopulse phased antenna device, characterized by that to have microstrip antenna array, there are more than two sub-arrays in the microstrip antenna array, set up more than two zero order resonance patch antenna units as stated in claim 1 or 2 in the sub-array; the micro-strip antenna array adopts a single-pulse feed network for feeding, and a Radant phase shifter for scanning on a pitching surface is arranged in front of the micro-strip antenna array; the RADAR lens completes one-dimensional beam scanning through one group of phase shifters, then scans the beam in the other direction through the other group of phase shifters, and realizes two-dimensional beam scanning through the two groups of phase shifters.
5. A transmissive low-cost monopulse phased antenna device according to claim 4, wherein said microstrip antenna array preferably has four sub-arrays, denoted as sub-array A, sub-array B, sub-array C, sub-array D, and 6 x 6 antenna elements are provided in each sub-array, then the first stage beam forming network:
Σ1＝A+B (1)，Δ1＝A-B (2)，Σ2＝C+D (3)，Δ2＝C-D (4)；
second stage beam forming network:
Σ＝A+B+C+D (5)，Δe＝A+B-C-D (6)，Δa＝A-B+C-D (7)。
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| CN111969335A (en) * | 2020-08-16 | 2020-11-20 | 西安电子科技大学 | Conformal dual-polarized two-dimensional single-pulse end-fire array antenna |
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| CN105552538A (en) * | 2015-12-17 | 2016-05-04 | 电子科技大学 | Planar phased-array antenna capable of two-dimensional scanning at wide angle |
| CN107275805A (en) * | 2017-04-27 | 2017-10-20 | 北京华镁钛科技有限公司 | A kind of phased array antenna based on Meta Materials electromagnetic property |
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Application publication date: 20200306 |