CN110828989A - Double-frequency antenna - Google Patents
Double-frequency antenna Download PDFInfo
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- CN110828989A CN110828989A CN201911055426.6A CN201911055426A CN110828989A CN 110828989 A CN110828989 A CN 110828989A CN 201911055426 A CN201911055426 A CN 201911055426A CN 110828989 A CN110828989 A CN 110828989A
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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Abstract
The utility model belongs to the technical field of the antenna, a dual-band antenna is provided, including antenna main part, microstrip combiner, first feed port and second feed port, the antenna main part includes first radiating element and second radiating element, the feed point of antenna main part is located first radiating element with the tie point of second radiating element, first feed port with second feed port passes through respectively the microstrip combiner connect in the feed point of antenna main part altogether to reduced antenna quantity in limited product space, and made each frequency channel of antenna have better isolation, but solved the not enough antenna isolation that leads to of overall arrangement space of antenna, influenced wireless antenna's communication quality's problem.
Description
Technical Field
The application relates to the technical field of antennas, in particular to a dual-frequency antenna.
Background
In recent years, in wireless communication, a radio frequency transceiver front end, which is an important component of a whole communication system, is continuously developed along with the update of the whole communication field, and in the development process, the problems of high product cost and increased hardware design difficulty are faced. For example, with the continuous development and completeness of communication systems, the MIMO system in WIFI products has a problem that the number of antennas is increasing.
However, due to the limited space of the antenna layout of the WIFI product, the insufficient space of the antenna layout may result in the insufficient isolation of the antenna, and the problem of affecting the communication quality of the wireless antenna exists.
Disclosure of Invention
An object of the application is to provide a dual-band antenna, but the not enough antenna isolation that can lead to of overall arrangement space that aims at solving the antenna exists the problem that influences wireless antenna's communication quality.
The embodiment of the application provides a dual-band antenna, including antenna main part, microstrip combiner, first feed port and second feed port, the antenna main part includes first radiating element and second radiating element, the feed point of antenna main part is located first radiating element with the junction of second radiating element, first feed port with the second feed port passes through respectively the microstrip combiner meets in the feed point of antenna main part.
Optionally, the microstrip combiner includes a first filtering unit, a second filtering unit, a ground terminal, and a combining network for connecting the first filtering unit, the second filtering unit, and the feeding point, where the first filtering unit is connected to a first branch of the combining network, the second filtering unit is connected to a second branch of the combining network, and the combining branch of the combining network is connected to the feeding point.
Optionally, the first filtering unit is a high-pass filtering unit, and the second filtering unit is a low-pass filtering unit.
Optionally, the microstrip combiner further includes a first port matching section and a second port matching section, the first port matching section is disposed between the first feed port and the first branch of the combiner network, and the second port matching section is disposed between the second feed port and the second branch of the combiner network.
Optionally, the first port matching section and the second port matching section are both impedance transformers.
Optionally, the dual-band antenna further includes a microstrip line, and a feed point of the antenna main body is connected to a combining branch of the combining network through the microstrip line.
Optionally, the impedance of the microstrip line is 50 ohms.
Optionally, the shape of the combining network is a "T" shape.
Optionally, the first radiation unit is connected to the radiation section in the second radiation unit, and forms a concave structure.
Optionally, the combiner network is a stepped impedance transformation structure.
In the dual-band antenna provided by the application, including antenna subject, microstrip combiner, first feed port and second feed port, antenna subject includes first radiating element and second radiating element, antenna subject's feed point is located first radiating element with the tie point of second radiating element, first feed port with second feed port passes through respectively the microstrip combiner connect in antenna subject's feed point altogether to reduced the antenna quantity in limited product space, and made each frequency channel of antenna have better isolation, but solved the not enough antenna isolation that leads to of antenna overall arrangement space, influenced wireless antenna's communication quality's problem.
Drawings
Fig. 1 is a schematic structural diagram of a dual-band antenna according to an embodiment of the present application;
fig. 2 is a schematic rear view of a dual-band antenna according to an embodiment of the present application;
fig. 3 is a schematic diagram of a dual-frequency combiner architecture according to an embodiment of the present application;
fig. 4 is a schematic diagram of an SIR resonator provided in an embodiment of the present application;
fig. 5 is an equivalent circuit diagram of a low-pass filter with open-circuit stubs loaded according to an embodiment of the present application;
fig. 6 is an S parameter of a dual-band antenna according to an embodiment of the present application;
fig. 7 is a schematic diagram of distributed current and field patterns according to an embodiment of the present application.
Detailed Description
In order to make the objects, technical solutions and advantages of the present application more apparent, the present application is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the present application and are not intended to limit the present application.
In the description of the present application, it is to be understood that the terms "first", "second" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implying any number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more of that feature.
Referring to fig. 1, the dual-band antenna in this embodiment includes an antenna main body 100, a microstrip combiner 200, a first feeding port 301, and a second feeding port 302, where the antenna main body 100 includes a first radiating element 101 and a second radiating element 102, a feeding point of the antenna main body 100 is located at a connection point of the first radiating element 101 and the second radiating element 102, and the first feeding port 301 and the second feeding port 302 are respectively connected to the feeding point of the antenna main body 100 through the microstrip combiner 200 in common.
In this embodiment, the antenna main body 100 and the microstrip combiner 200 are both disposed on the first surface of the substrate, wherein the antenna main body 100 adopts the first radiation unit 101 and the second radiation unit 102 to respectively work on different frequency bands to form dual resonance, and the first radiation unit 101 and the second radiation unit 102 share a feeding point, so that each radiation unit can be independently adjusted according to the working frequency band thereof. For example, in a specific application, the first radiation unit 101 can radiate signals in a low frequency band, and the current effective electrical length is about 1/4 wavelengths of the low frequency 2400MHz frequency. The second radiating element 102 can radiate signals in a high frequency band, with an effective electrical length of current of about 1/4 wavelengths at a high frequency of 5500 MHz.
Further, in the present embodiment, the first radiation element 101 and the second radiation element 102 are both composed of radiation segments having a bending structure, and at this time, the radiation segments in the first radiation element 101 and the second radiation element 102 are coupled and connected, and form a feeding point of the antenna body 100 at the connection point.
Further, in this embodiment, reasonable network connection is performed through the microstrip combiner 200, so that a higher isolation between the first feeding port 301 and the second feeding port 302 is achieved, and meanwhile, the currents in the first radiating element 101 and the second radiating element 102 are distributed orthogonally, so that mutual coupling between the radiating elements can be effectively reduced.
In one embodiment, referring to fig. 1 and 2, the microstrip combiner 200 includes a first filtering unit 201, a second filtering unit 202, a ground 205, and a combining network for connecting the first filtering unit 201, the second filtering unit 202, and the feeding point, where the first filtering unit 201 is connected to a first branch 2031 of the combining network, the second filtering unit is connected to a second branch 2032 of the combining network, and a combining branch 2033 of the combining network is connected to the feeding point.
In this embodiment, the first branch 2031 of the combining network is connected to the first feeding port 301, the second branch 2032 of the combining network is connected to the second feeding port 302, and the ground terminal 205 is disposed on the second surface of the substrate, for example, if the substrate is a PCB, the dual-band antenna shown in fig. 1 is formed on the first surface of the PCB by etching, the ground terminal 205 is formed on the second surface of the PCB, and the ground terminal 205 is connected to the first feeding port 301 and the second feeding port 302.
In one embodiment, the first filtering unit 201 is a high-pass filtering unit, and the second filtering unit 202 is a low-pass filtering unit.
In this embodiment, the first filtering unit 201 is a high-pass filtering unit, the second filtering unit 202 is a low-pass filtering unit, and a dual-frequency combiner structure is formed by a combining network structure, as shown in fig. 3, wherein the port 1 and the port 2 may be respectively used as feeding ports, and are connected to the antenna main body 100 through a combining end, so as to implement dual-band radiation, thereby avoiding the problem of low isolation caused by the increase of the number of antennas.
In one embodiment, the first filtering unit 201 may be a Step Impedance Resonator (SIR) open stub loaded high pass filter, which does not need to have a strict high pass response, but only requires sufficiently small insertion loss in a given pass band and sufficient rejection in a stop band at frequencies below the pass band. Specifically, the high-pass filter loaded by the open-circuit branch generates a transmission zero at the frequency of the quarter wavelength f1, and then a transmission zero is also generated at the odd frequency doubling f (2N-1), so that in order to prevent the transmission zero of the odd frequency doubling from falling in the useful range of the 5G frequency band, the SIR open-circuit branch is adopted, and the structure can enable the odd frequency doubling transmission zero to shift to a higher frequency.
Referring to the schematic diagram of SIR open stub loaded high pass filter shown in FIG. 4, when Z isiC2When 0, the resulting frequency is the position of the transmission zero.
The following can be obtained: zc1-Zc2tanθ1tanθ2＝0
Order to
The zero point position depends on θ 1, θ 2 and the impedance ratio Rz.
Assuming θ 2 is θ 1 is θ, it can be obtained
When Rz >1, there are
In which the SIR resonator is formed of two sections of different characteristic impedance (Z)c1、Zc2) Of the transmission line, Zin1、Zin2The input impedance of the SIR resonator is respectively, and theta 1 and theta 2 are respectively the electrical lengths of two sections of transmission lines with different characteristic impedances in the SIR resonator, so that the SIR branch node loading is used, the high-order zero point can be transferred to a higher frequency band, and the influence on a pass band is avoided.
In this embodiment, the second filtering unit 201 may be a low-pass filter loaded with open stubs, similar to an elliptic function filter, and obtains transmission zeros at finite frequencies through quarter-wavelength open lines, and its lumped parameter equivalent circuit is shown in fig. 5, where L1, L3, and L5 may be replaced by high-impedance lines, and the series resonators L2C2 and L4C4 are replaced by quarter-wavelength open lines. The resulting circuit produces two transmission zeroes at the L2C2, L4C4 resonance. The selectivity of the transmission zero point is related to the thickness of the open-circuit branches, and generally, the thinner the open-circuit branches are, the better the selectivity is.
Further, in the present embodiment, the use of a limited number of orders enables the low-pass filter with the loaded open-circuit branches to achieve good selectivity.
In one embodiment, the microstrip combiner 20 further includes a first port matching section 2041 and a second port matching section 2042, the first port matching section 2041 is disposed between the first feeding port 301 and the first branch 2031 of the combining network, and the second port matching section 2042 is disposed between the second feeding port 302 and the second branch 2032 of the combining network.
In one embodiment, the first port matching section 2041 and the second port matching section 2042 are both impedance transformers. In this embodiment, by setting the first port matching section 2041 and the second port matching section 2042 as impedance transformers, good matching of the feeding ports can be ensured.
In one embodiment, the dual-band antenna further includes a microstrip line 400, and the feeding point of the antenna body 100 is connected to the combining branch 2033 of the combining network through the microstrip line 400.
In one embodiment, the resistance of the microstrip line 400 is 50 ohms. In this embodiment, the 50-ohm microstrip line 400 connects the antenna body 100 and the microstrip combiner 200, so as to ensure effective transmission of signals therebetween.
In one embodiment, the combining network is shaped as a "T". In this embodiment, referring to fig. 1, the combining network of the T-junction is formed by connecting a first branch 2031, a second branch 2032 and a combining branch 2033, wherein, the first branch 2031 and the second branch 2032 are coupled and connected in parallel, the combining branch 2033 is perpendicular to the first branch 2031 and the second branch 2032, and is coupled and connected with the first branch 2031 and the second branch 2032, meanwhile, the first branch 2031 and the second branch 2032 of the T-type combining network are respectively connected in series with the filter ports, and thus are respectively connected to the corresponding filtering units, the length and width of the T-shaped junction are reasonably selected according to the port impedance value presented by the filter in the non-working frequency band and the transmission line impedance equation, so that the impedance value of the connecting section of the T-shaped junction is used for offsetting the reactance of the filter end, in the smith chart, it appears that the impedance value at the filter end is rotated along the iso-electric impedance circle to make the reactance 0, i.e. the open circuit point. Therefore, the combining branch 2033 is in an open circuit state when looking at the filter end of the non-operating frequency band, so as to prevent the current from flowing, ensure good isolation between the two filters, and achieve high isolation between the first feeding port 301 and the second feeding port 302, and meanwhile, as shown in fig. 6, the first radiating element 101 and the second radiating element 102 are orthogonal in current distribution, which can effectively reduce mutual coupling between the radiating elements.
In one embodiment, the first radiating element 101 is connected to the radiating section of the second radiating element 102, and forms a concave structure. In this embodiment, the first radiating element 101 is connected to the radiating section of the second radiating element 102 to form an antenna with a concave structure, and when the concave structure is fed at a reasonably sized midpoint, the concave structure can excite the orthogonally distributed currents at the two operating frequencies, and the distributed currents appear to be orthogonal to the radiation pattern when viewed in the far field, so as to effectively reduce the mutual coupling between the radiating elements, and the distributed currents and the pattern are shown in fig. 7.
In one embodiment, the first radiation unit 101 is formed by rotating 90 ° counterclockwise after being formed into an "L" shaped mirror image, the second radiation unit 102 is formed into an "L" shaped mirror image, and the first radiation unit 101 and the second radiation unit 102 are connected to form a spoon shape.
In one embodiment, the combining network is a stepped impedance transformation structure. In this embodiment, a step impedance transformation structure is adopted to form a combiner network, so as to ensure good matching performance of the combiner network, and the combiner network can be divided into multiple sections by the step impedance transformation structure, and each section of impedance is designed to form step impedance, so that impedance matching is performed in combination with the feed port in this embodiment, and the antenna port keeps good isolation.
In the dual-band antenna provided by the application, including antenna subject, microstrip combiner, first feed port and second feed port, antenna subject includes first radiating element and second radiating element, antenna subject's feed point is located first radiating element with the tie point of second radiating element, first feed port with second feed port passes through respectively the microstrip combiner connect in antenna subject's feed point altogether to reduced the antenna quantity in limited product space, and made each frequency channel of antenna have better isolation, but solved the not enough antenna isolation that leads to of antenna overall arrangement space, there is the problem that influences wireless antenna's communication quality.
The above description is only exemplary of the present application and should not be taken as limiting the present application, as any modification, equivalent replacement, or improvement made within the spirit and principle of the present application should be included in the protection scope of the present application.
Claims (10)
1. A dual-band antenna is characterized by comprising an antenna body, a microstrip combiner, a first feed port and a second feed port, wherein the antenna body comprises a first radiation unit and a second radiation unit, a feed point of the antenna body is located at the joint of the first radiation unit and the second radiation unit, and the first feed port and the second feed port are respectively connected to the feed point of the antenna body in a shared mode through the microstrip combiner.
2. The dual-band antenna of claim 1, wherein the microstrip combiner comprises a first filtering unit, a second filtering unit, a ground terminal, and a combining network for connecting the first filtering unit, the second filtering unit, and the feeding point, the first filtering unit and the second filtering unit are respectively located at two opposite sides of the feeding point, the first filtering unit is connected to a first branch of the combining network, the second filtering unit is connected to a second branch of the combining network, and the combining branch of the combining network is connected to the feeding point.
3. The dual-band antenna of claim 2, wherein said first filtering unit is a high-pass filtering unit and said second filtering unit is a low-pass filtering unit.
4. The dual-band antenna of claim 2, wherein the microstrip combiner further comprises a first port matching section disposed between the first feed port and a first branch of the combining network and a second port matching section disposed between the second feed port and a second branch of the combining network.
5. The dual-band antenna of claim 4, wherein said first port matching section and said second port matching section are impedance transformers.
6. The dual-band antenna of claim 2, wherein the dual-band antenna further comprises a microstrip line, and a feeding point of the antenna body is connected to the combining branch of the combining network through the microstrip line.
7. The dual-band antenna of claim 6, wherein the microstrip line has an impedance of 50 ohms.
8. The dual-band antenna of claim 2, wherein said combining network is "T" shaped.
9. The dual-band antenna of claim 1, wherein said first radiating element is connected to a radiating segment in said second radiating element and forms a concave structure.
10. The dual-band antenna of claim 2, wherein said combining network is a stepped impedance transformation structure.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201911055426.6A CN110828989A (en) | 2019-10-31 | 2019-10-31 | Double-frequency antenna |
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| CN201911055426.6A CN110828989A (en) | 2019-10-31 | 2019-10-31 | Double-frequency antenna |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112201951A (en) * | 2020-09-28 | 2021-01-08 | 上海摩勤智能技术有限公司 | Multi-antenna layout structure of antenna bracket and mobile terminal |
| CN112490661A (en) * | 2020-11-23 | 2021-03-12 | 上海海积信息科技股份有限公司 | Impedance matching device and antenna |
| WO2023231752A1 (en) * | 2022-05-30 | 2023-12-07 | 华为技术有限公司 | Antenna and base station |
-
2019
- 2019-10-31 CN CN201911055426.6A patent/CN110828989A/en active Pending
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112201951A (en) * | 2020-09-28 | 2021-01-08 | 上海摩勤智能技术有限公司 | Multi-antenna layout structure of antenna bracket and mobile terminal |
| CN112201951B (en) * | 2020-09-28 | 2023-03-10 | 上海摩勤智能技术有限公司 | Multi-antenna layout structure of antenna bracket and mobile terminal |
| CN112490661A (en) * | 2020-11-23 | 2021-03-12 | 上海海积信息科技股份有限公司 | Impedance matching device and antenna |
| WO2023231752A1 (en) * | 2022-05-30 | 2023-12-07 | 华为技术有限公司 | Antenna and base station |
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