CN110795901B - Design method of 5G microwave full-equal-width parallel line coupling filter - Google Patents
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Abstract
The invention relates to a design method of a 5G microwave full-width parallel line coupling filter for industrial Internet. The invention adopts N coupling line segments to form a parallel line coupling band-pass filter, and the correction center frequency is determined according to the center working frequency and the relative bandwidth of the filter; according to the type of the filter and the in-band ripple, determining the inductance of each stage of series coil and the capacitance of the parallel capacitor, determining the value of the impedance converter parameter by adopting a parity mode impedance method, and determining the parity mode impedance of the filter; determining the length and the precision of each stage of coupling line segments according to the chemical corrosion precision of the circuit board, so that the lengths and the widths of all parallel lines are equal; and simulating the lengths and widths of all stages of the obtained parallel line coupling band-pass filter through ADS and outputting the simulated lengths and widths as layout files of the layout, and rounding the open ends of the parallel line coupling band-pass filter according to the layout files of the layout files.
Description
Technical Field
The invention relates to the technical field of full-equal-width parallel line coupling filters, in particular to a design method of a 5G microwave full-equal-width parallel line coupling filter.
Background
In circuit designs for wireless signal transmission, filters are one of the most common approaches to avoid the generation of harmonics and image signals.
A filter is an important place in front-end circuit design as a widely used microwave device. With the development of microwave circuit integration, microstrip parallel line coupled filters are widely used with the advantages of easy integration, easy design, easy manufacture (printed circuit), large bandwidth, planar structure, large aspect ratio, easy rotation for adapting to receiver channels, and the like.
The invention relates to the technical field of radio frequency/microwave/millimeter wave, industrial Internet and 5G, in particular to a full-equal-width parallel line coupling filter, which can accurately design the frequency response of the filter and improve the accuracy and consistency of the filter design.
The filter of the planar microstrip structure is the most commonly used band-pass filter. In the process of designing a filter, in addition to requirements of bandwidth, out-of-band rejection, insertion loss and the like, the filter is usually considered to be easy to design, thermally reliable, consistent and the like. The phenomena of discontinuous line width and filleting of right angles of parallel lines of each level can be caused in the corrosion processing technology, processing errors and frequency offset are caused, the inconsistency of design and processing results is found, the high-frequency filter is difficult to realize the high consistency of design and detection, and the design difficulty of the filter is high and the research and development cost is high.
Disclosure of Invention
The invention provides a design method of a 5G microwave full-width parallel line coupling filter for industrial Internet, which aims to improve the accuracy and consistency of the filter and solve the problem of discontinuity among parallel line coupling filters, and provides the following technical scheme:
a design method of a 5G microwave full-width parallel line coupling filter for industrial Internet comprises the following steps:
step 1: n coupling line segments are connected to form a parallel line coupling band-pass filter, numbering is carried out from left to right, and the center working frequency and the relative bandwidth of the filter are determined according to the wireless transmission system index of the filter;
step 2: according to the filter center working frequency and the relative bandwidth, determining a correction center frequency;
step 3: determining inductance of each stage of series coil and capacitance g of parallel capacitor according to filter type and in-band ripple 1 ,g 2 …g N ；
Step 4: determining the impedance converter parameter Z by odd-even mode impedance method 0 J 1 ,Z 0 J 2 …Z 0 J N Is a value of (2);
step 5: determining the odd-even mode impedance Z of the filter by adopting an odd-even mode impedance method 0e ,Z 0o ；
Step 6: determining the length and the precision of each stage of coupling line segments according to the chemical corrosion precision of the circuit board, so that the lengths and the widths of all parallel lines are equal;
step 7: and simulating the lengths and widths of all stages of the obtained parallel line coupling band-pass filter through ADS and outputting the simulated lengths and widths as layout files of the layout, and rounding the open ends of the parallel line coupling band-pass filter according to the layout files of the layout files.
Preferably, the step 2 specifically includes:
step 2.1: according to the filter center working frequency and the relative bandwidth, determining a correction center frequency, and determining the correction center frequency by the following formula:
wherein Δf is the corrected center frequency, N is the order, n=1, 2, … n+1, f 0 And the center working frequency of the filter.
Preferably, the step 4 is specifically
The value of the impedance converter parameter is determined by the odd-even mode impedance method by:
wherein Z is 0 50 ohm impedance, delta is the relative bandwidth, J is the admittance inverter constant, Z 0 J 1 Z is the first stage impedance converter parameter value 0 J 2 Z is the second stage impedance converter parameter value 0 J N Is the value of the nth stage impedance converter parameter.
Preferably, the step 5 specifically includes:
determining the odd-even mode impedance Z of the filter by adopting an odd-even mode impedance method 0e ,Z 0o The odd-even mode impedance Z of the filter is determined by 0e ,Z 0o ：
Z 0e ＝Z 0 [1+JZ 0 +(JZ 0 ) 2 ]
Z 0o ＝Z 0 [1-JZ 0 +(JZ 0 ) 2 ]
Wherein Z is 0e And Z 0o Are all odd-even mode impedances of the filter.
Preferably, the step 6 specifically includes:
step 6.1: according to the chemical corrosion precision of the circuit board, determining the length, the phase and the frequency offset of each stage of coupling line segments, so that the lengths and the widths of all parallel lines are equal, and determining the lengths of each stage of coupling line segments by the following formula:
wherein L is a L is the length of the microstrip line after the rounded corners with equal area, W is the width of the microstrip line;
step 6.2: according to the lengths of the coupling line segments of each level, the phases of the coupling line segments of each level are determined, and the phases of the coupling line segments of each level are represented by the following formula:
wherein f 0 Calculating the center working frequency f of the filter for theory 0 ' is the center working frequency of the actual measured filter after actual corrosion;
step 6.3: determining a frequency offset according to the phases of the coupling line segments of each stage, wherein the frequency offset is represented by the following formula:
wherein Δf 0 For frequency offset lambda g Is a waveguide wavelength.
The invention has the following beneficial effects:
the parallel line coupling filter designed by the invention adopts a round corner design scheme to replace the traditional length compensation scheme for the open end of the parallel line coupling filter, and in order to avoid discontinuity caused by different widths of adjacent parallel lines of each step, particularly small width difference, parallel lines with very similar lengths and widths of each step are required to be set to be identical in length and width.
The method solves the problems that the linewidth of each level of parallel lines of the existing parallel line coupling filter is discontinuous, and the processing error is easy to cause, so that the frequency deviation is caused, and the design and the processing are inconsistent. The filter is easy to accurately design due to the design of the full equal width, so that the whole design flow is simple and smooth. The rounded design avoids frequency offset caused by machining corrosion.
(1) At the open-circuit port of each level of parallel line, the frequency is offset due to the rounding phenomenon caused by the corrosion processing technology, and the higher the frequency is, the narrower the line width is, the more serious the rounding corrosion phenomenon is, so that the accurate design and processing of the high-frequency filter are difficult.
(2) The invention of the filleted parallel line coupling filter with the full equal width provides good performance guarantee for a radio frequency/microwave/millimeter wave multichannel radiometer system.
(3) The derivation of the correlation equation gives an accurate design of the filter, which ensures that consistent performance is provided for the multichannel receiver radiometer system.
(4) The invention of the rounded full-width filter provides a set of related design flow, and reduces the design difficulty of the precise high-frequency filter.
Drawings
Fig. 1 is a structure of N coupled line bandpass filters;
FIG. 2 is an equivalent circuit of one coupling segment;
FIG. 3 is an overall equivalent circuit diagram of a filter;
FIG. 4 is an open-end rounded full-width parallel line coupled filter design layout;
FIG. 5 is a single parallel line structure diagram, FIG. 5- (a) is a single rounded parallel line, and FIG. 5- (b) is an equal area right angle parallel line;
FIG. 6 shows the frequency shift of the corresponding fillet for different center frequencies for the order of n 4, FIG. 6- (a) for frequency 5GHz, FIG. 6- (b) for 12GHz, and FIG. 6- (c) for 20.2GHz; FIG. 6- (d) is 26GHz and FIG. 6- (e) is 34GHz;
FIG. 7 shows the frequency shift of the corresponding fillet for different center frequencies for the order of 5 for n, FIG. 7- (a) for frequency 8GHz, FIG. 7- (b) for 12GHz, and FIG. 7- (c) for 20GHz; FIG. 7- (d) is 26GHz and FIG. 7- (e) is 34GHz;
FIG. 8 shows the frequency shift of the corresponding fillet for different center frequencies for the order of 6 for n, FIG. 8- (a) for frequency 8GHz, FIG. 8- (b) for 12GHz, and FIG. 8- (c) for 20GHz; FIG. 8- (d) is 26GHz and FIG. 8- (e) is 34GHz;
FIG. 9 is a graph of center frequency, bandwidth and frequency shift, FIG. 9- (a) is a graph of center frequency and frequency shift, and FIG. 9- (b) is a graph of bandwidth and frequency shift;
FIG. 10 is a sample plot of a full-width equal-length fillet parallel line coupled filter, FIG. 10- (a) a single sample plot, and FIG. 10- (b) a plurality of test samples;
FIG. 11 is a chart of three different center frequency full equal width equal length filter sample tests, FIG. 11- (a) is a center frequency 12GHz sample test, FIG. 11- (b) is a center frequency 26.2GHz sample test, and FIG. 11- (c) is a center frequency 34GHz sample test.
Detailed Description
The present invention will be described in detail with reference to specific examples.
First embodiment:
according to the invention, as shown in fig. 1, the invention provides a design method of a 5G microwave full-width parallel line coupling filter for industrial Internet, which comprises the following steps:
step 1: n coupling line segments are connected to form a parallel line coupling band-pass filter, numbering is carried out from left to right, and the center working frequency and the relative bandwidth of the filter are determined according to the wireless transmission system index of the filter;
consider N coupled linesThe band-pass filter formed by the segment strings is numbered 1-N from left to right as shown in figure 1. Each coupling line segment can be represented by the equivalent circuit of fig. 2, wherein J represents the inverter, i.e., the inverter constant, and then the overall equivalent circuit diagram of the bandpass filter represented in fig. 1 can be represented by the equivalent circuit diagram of fig. 3, wherein the line of length θ at each end of the filter is the same as Z 0 Matching, negligible, J 1 ～J N Representing the coupled line inverter constants of each stage.
Step 2: according to the filter center working frequency and the relative bandwidth, determining a correction center frequency;
to verify the shift in frequency, EM simulations were performed on four filters having center frequencies of 8GHz, 12GHz, 20GHz, 26GHz, and 34GHz, respectively, and having a relative bandwidth of 12%. In consideration of processing precision, the first-order coupling parallel line distance of the parallel line coupling filter is set to be 0.1mm, a specific size calculation formula can refer to related data and books, and the widths and lengths of all the other parallel microstrip lines are consistent with those of the first-order coupling parallel line distance, so that the full-equal-width equal-length design is realized. The simulation results of the parallel line filters having right-angle and rounded-angle parallel line tops were compared, respectively, as shown in fig. 6, 7, and 8 (a) to (e). Comparing (a) to (e) in fig. 7 and 8 alone, it can be seen that the fillet frequency shift increases with increasing center frequency. Comparing fig. 6, 7 and 8 longitudinally, it can be obtained that the rounded frequency shift decreases with increasing order. The detailed parameters are shown in Table 1, and the detailed comparison parameters are given.
Plotting the parameters compared in Table 1 against different orders and different center frequencies yields FIG. 9, from FIG. 9- (a) the frequency shift increases with increasing center frequency, substantially satisfying the linear relationship; the frequency shift decreases with increasing order. As can be seen from fig. 9- (b), the frequency shift varies only slightly with bandwidth and decreases with increasing order n.
TABLE 1 round-corner frequency shifts for different orders and center frequencies
From the above data, the correction center frequency is determined by:
step 3: determining inductance of each stage of series coil and capacitance g of parallel capacitor according to filter type and in-band ripple 1 ,g 2 …g N ；
Step 4: determining the impedance converter parameter Z by odd-even mode impedance method 0 J 1 ,Z 0 J 2 …Z 0 J N Is a value of (2);
wherein Z is 0 For a 50 ohm impedance, n=1, 2,3 … n+1, N is the order, g is the cutoff frequency ω c Chebyshev low-pass prototype filter parameters at=1, i.e. g i (i=1 to n) is the inductance of each series coil and the capacitance of the parallel capacitor, Z 0o ,Z 0e The odd-even mode characteristic impedance, respectively, delta is the relative bandwidth and J is the admittance inverter constant. For parallel line coupled filters, additional capacitive effects are created due to the fact that the electric field energy exceeds the open ends of the parallel lines. This phenomenon results in parallel lines having an electrical dimension that is one third greater than the actual design value of the substrate thickness. To compensate for this effect, a parallel line length pre-shortening process is typically employed. Z is Z 0 J 1 Z is the first stage impedance converter parameter value 0 J 2 Z is the second stage impedance converter parameter value 0 J N Is the value of the nth stage impedance converter parameter.
Step (a)5: determining the odd-even mode impedance Z of the filter by adopting an odd-even mode impedance method 0e ,Z 0o ；
Z 0e ＝Z 0 [1+JZ 0 +(JZ 0 ) 2 ]
Z 0o ＝Z 0 [1-JZ 0 +(JZ 0 ) 2 ]
The parallel line coupling filter designed by the invention adopts a round corner design scheme to replace the traditional length compensation scheme for the open end of the parallel line coupling filter, and in order to avoid discontinuity caused by different widths of adjacent parallel lines of each step, particularly small width difference, parallel lines with very similar lengths and widths of each step are required to be set to be identical in length and width. Based on this method we change the right angles of the designed filter level parallel lines to rounded corners to conform to the actual situation after etching, as shown in fig. 4.
Step 6: determining the length and the precision of each stage of coupling line segments according to the chemical corrosion precision of the circuit board, so that the lengths and the widths of all parallel lines are equal;
the single parallel lines were rounded as shown in fig. 5- (a), and the right-angle parallel lines with equal areas were as shown in fig. 5- (b). The microstrip line has a width of W and a length of La, and after the microstrip line has an equal area of rounded corners, the microstrip line has a length of L, and right-angle ends at two ends of the microstrip line are rounded with a W/2 rounded corner radius, as shown in FIG. 5- (a). Since FIG. 5- (b) and FIG. 5- (a) have the same area, the microstrip line length after the rounded corner can be determined by the formula (6), and the phase and frequency shifts caused by the microstrip line length are the formulas (7) and (8)
Wherein f 0 Calculating a filter for theoryCenter working frequency f 0 ' is the center working frequency of the actual measured filter after actual corrosion, lambda g Is a waveguide wavelength;
step 7: and simulating the lengths and widths of all stages of the obtained parallel line coupling band-pass filter through ADS and outputting the simulated lengths and widths as layout files of the layout, and rounding the open ends of the parallel line coupling band-pass filter according to the layout files of the layout files.
Actual measurement results:
according to the steps, three chebyshev filters are designed, the center frequencies are respectively 12GHz, 26GHz and 34GHz, and the relative bandwidths are respectively 11.8%, 15.8% and 12%. The assembly diagram is shown in fig. 10. The parallel line coupling filter is sensitive to the width and the height of the metal cavity, and the height width is set to be 8mm and 3.5mm, so that the waveguide cut-off frequency of the cavity is smaller than 38GHz. The two ends of the cavity are connected by using a K head. The edge-coupled filter is sensitive to both width and height of the metal cavity, and this method is called de-embedding effect process in order to ensure that the cavity pair is frequency-responsive in the cavity by measuring the corresponding K-head and calibration line (TRL), and removing in the frequency response of the final filter, resulting in an accurate frequency response of the filter itself. Fig. 11 (a) to (c) are the above three filter sample measurement curves, the numbers of which are 2,3, and 3, respectively. From the graph, it can be found that the three filter measurement results are well matched with the simulation result, and the consistency between the same sample is also good. The detailed parameters are shown in Table 2.
Table 2 sample measurement results
One possible rounded design proposed by the present invention. The parallel lines of each step are set to be the same in length and width, and the curve of the frequency offset after the rounding of the open ends of the parallel lines is obtained through simulation, so that an empirical formula of the frequency offset after the rounding of the open ends of the parallel line coupling filter is obtained. Finally, parameters such as frequency response, insertion loss and the like of a plurality of parallel line coupling filters manufactured by using a rounded design flow are measured, simulation and measurement results are well matched, and the same filters have good consistency.
The above description is only a preferred implementation manner of the design method of the 5G microwave full-width parallel line coupling filter, and the protection scope of the design method of the 5G microwave full-width parallel line coupling filter is not limited to the above embodiments, and all technical solutions under the concept belong to the protection scope of the invention. It should be noted that modifications and variations can be made by those skilled in the art without departing from the principles of the present invention, which is also considered to be within the scope of the present invention.
Claims (5)
1. A design method of a 5G microwave full-width parallel line coupling filter for industrial Internet is characterized by comprising the following steps: the method comprises the following steps:
step 1: n coupling line segments are connected to form a parallel line coupling band-pass filter, numbering is carried out from left to right, and the center working frequency and the relative bandwidth of the filter are determined according to the wireless transmission system index of the filter;
step 2: according to the filter center working frequency and the relative bandwidth, determining a correction center frequency;
step 3: determining inductance of each stage of series coil and capacitance g of parallel capacitor according to filter type and in-band ripple 1 ,g 2 …g N ；
Step 4: determining the impedance converter parameter Z by odd-even mode impedance method 0 J 1 ,Z 0 J 2 …Z 0 J N Is a value of (2);
step 5: determining the odd-even mode impedance Z of the filter by adopting an odd-even mode impedance method 0e ,Z 0o ；
Step 6: determining the length and the precision of each stage of coupling line segments according to the chemical corrosion precision of the circuit board, so that the lengths and the widths of all parallel lines are equal;
step 7: and simulating and outputting the lengths and widths of all stages of the obtained parallel line coupling band-pass filter into layout files of layout by ADS, and rounding the open-circuit ends of the parallel line coupling band-pass filter according to the layout files of layout, wherein the right-angle ends of the open-circuit ends are rounded by taking half of the widths of the parallel lines as rounding radii.
2. The method for designing the 5G microwave full-width parallel line coupling filter for the industrial Internet according to claim 1, wherein the method comprises the following steps: the step 2 specifically comprises the following steps:
step 2.1: according to the filter center working frequency and the relative bandwidth, determining a correction center frequency, and determining the correction center frequency by the following formula:
wherein Δf is the corrected center frequency, N is the order, n=1, 2, … n+1, f 0 And the center working frequency of the filter.
3. The method for designing the 5G microwave full-width parallel line coupling filter for the industrial Internet according to claim 1, wherein the method comprises the following steps: the step 4 is specifically that
The value of the impedance converter parameter is determined by the odd-even mode impedance method by:
wherein Z is 0 For 50 ohm impedance, delta is the relative bandwidth, Z 0 J 1 Z is the first stage impedance converter parameter value 0 J 2 Z is the second stage impedance converter parameter value 0 J N Is the value of the nth stage impedance converter parameter.
4. The method for designing the 5G microwave full-width parallel line coupling filter for the industrial Internet according to claim 1, wherein the method comprises the following steps: the step 5 specifically comprises the following steps:
determining the odd-even mode impedance Z of the filter by adopting an odd-even mode impedance method 0e ,Z 0o The odd-even mode impedance Z of the filter is determined by 0e ,Z 0o ：
Z 0e ＝Z 0 [1+JZ 0 +(JZ 0 ) 2 ]
Z 0o ＝Z 0 [1-JZ 0 +(JZ 0 ) 2 ]
Wherein Z is 0e And Z 0o J is the admittance inverter constant, Z, is the odd-even mode impedance of the filter 0 Is a 50 ohm impedance.
5. The method for designing the 5G microwave full-width parallel line coupling filter for the industrial Internet according to claim 1, wherein the method comprises the following steps: the step 6 specifically comprises the following steps:
step 6.1: according to the chemical corrosion precision of the circuit board, determining the length, the phase and the frequency offset of each stage of coupling line segments, so that the lengths and the widths of all parallel lines are equal, and determining the lengths of each stage of coupling line segments by the following formula:
wherein L is a L is the length of the microstrip line after the rounded corners with equal area, W is the width of the microstrip line;
step 6.2: according to the lengths of the coupling line segments of each level, the phases of the coupling line segments of each level are determined, and the phases of the coupling line segments of each level are represented by the following formula:
wherein f 0 Calculating the center working frequency f of the filter for theory 0 ' is the center working frequency of the actual measured filter after actual corrosion;
step 6.3: determining a frequency offset according to the phases of the coupling line segments of each stage, wherein the frequency offset is represented by the following formula:
wherein Δf 0 For frequency offset lambda g Is a waveguide wavelength.
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| JP2010041330A (en) * | 2008-08-04 | 2010-02-18 | Toshiba Corp | Wiring substrate and electric device |
| KR101536706B1 (en) * | 2014-05-02 | 2015-07-16 | 연세대학교 산학협력단 | Filter and method for manufacturing the same |
| CN105552493A (en) * | 2016-01-26 | 2016-05-04 | 电子科技大学 | Direct design method for parallel coupling microstrip band-pass filter |
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| JP2010041330A (en) * | 2008-08-04 | 2010-02-18 | Toshiba Corp | Wiring substrate and electric device |
| KR101536706B1 (en) * | 2014-05-02 | 2015-07-16 | 연세대학교 산학협력단 | Filter and method for manufacturing the same |
| CN105552493A (en) * | 2016-01-26 | 2016-05-04 | 电子科技大学 | Direct design method for parallel coupling microstrip band-pass filter |
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