CN110784144A - Improved control method of built-in permanent magnet synchronous motor - Google Patents

Improved control method of built-in permanent magnet synchronous motor Download PDF

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Publication number
CN110784144A
CN110784144A CN201911036325.4A CN201911036325A CN110784144A CN 110784144 A CN110784144 A CN 110784144A CN 201911036325 A CN201911036325 A CN 201911036325A CN 110784144 A CN110784144 A CN 110784144A
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current
axis
motor
calculation module
value
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CN110784144B (en
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杨高兴
张瑞峰
柴璐军
路瑶
贺志学
张吉斌
丁志勇
梁海刚
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CRRC Yongji Electric Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/22—Current control, e.g. using a current control loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
    • H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation

Abstract

The invention relates to a control method of a permanent magnet synchronous motor, in particular to an improved control method of a built-in permanent magnet synchronous motor. The method solves the problems that the existing permanent magnet synchronous motor control method using parameter online identification has defects and is not ideal in use. The invention carries out on-line calculation on the torque current, carries out real-time correction according to the dynamic parameters of the motor, obtains a current calculation model containing more accurate motor parameter information, further calculates to obtain the torque current by utilizing the model, and can carry out real-time correction on the torque current at low speed and high speed so as to realize accurate torque current control. The algorithm can enable the motor to operate at a more accurate working point, and has good parameter robustness and dynamic response characteristics. The change condition of the motor parameter is estimated on line in the feed-forward voltage calculation module, so that the accurate calculation control of the reference voltage is realized, and the control accuracy of the motor is improved.

Description

Improved control method of built-in permanent magnet synchronous motor
Technical Field
The invention relates to a control method of a permanent magnet synchronous motor, in particular to an improved control method of a built-in permanent magnet synchronous motor.
Background
The traditional Maximum Torque current ratio (MTPA) control method of the built-in permanent magnet synchronous motor obtains D-axis current given value by carrying out derivation operation on a motor Torque model
Figure BDA0002251609040000011
Then passing through the given torque T *And calculating motor parameters to obtain Q-axis current
Figure BDA0002251609040000012
Under the condition of constant torque, the D-Q axis current satisfies the following formula:
Figure BDA0002251609040000013
because the current calculation formula in the maximum torque current ratio (MTPA) control method comprises parameters such as a permanent magnet flux linkage and a D-Q axis inductor, the parameters can change nonlinearly along with factors such as load disturbance, temperature change and magnetic circuit saturation in actual operation, and great fluctuation is brought to the current calculation of the maximum torque current ratio (MTPA) control method. Therefore, improving the calculation accuracy of the given current and the given voltage becomes one of the keys of the permanent magnet synchronous motor control.
In order to improve the accuracy of permanent magnet synchronous motor control, most scholars generally use a parameter online identification method; in recent years, researchers have proposed a maximum torque current ratio control method based on virtual signal injection, which includes analyzing the relationship between motor torque and power, using a detected value instead of a motor parameter, injecting a high frequency current signal into a torque formula, passing the torque signal including the high frequency signal through a band pass filter and a low pass filter according to a taylor series expansion formula to obtain a torque versus current angle change rate required for a maximum torque current ratio, and passing the torque versus current angle change rate through an integrator to be controlled to be zero, thereby realizing the maximum torque current ratio control. The calculation method for obtaining the MTPA angle by the method has the advantages of low convergence speed, long dynamic response time, complex algorithm, complex signal analysis process, poor dynamic response and poor practical application.
Disclosure of Invention
The invention solves the problems that the existing permanent magnet synchronous motor control method using parameter online identification has defects and is not ideal to use, and provides an improved control method of a built-in permanent magnet synchronous motor. The control method accurately distributes the motor current controlled by the motor by accurately determining the motor parameters in real time, so as to accurately control the motor, and the motor has good steady-state control precision and dynamic response speed; and the method is simple and has no complicated calculation process.
The invention is realized by adopting the following technical scheme: the control method of the built-in permanent magnet synchronous motor comprises the following steps of dividing the control method into 4 modules which are respectively a sampling calculation module 1, a motor parameter calculation module 2, a torque current calculation module 3 and a current feedforward decoupling calculation module 4;
1) sampling calculation module
Collecting DC bus voltage U of inverter dcAnd motor stator current i a、i b(ii) a For stator current i a、i bPerforming Clarke transformation and Park transformation to obtain a stator current D axis component i in a synchronous rotation coordinate system DAnd stator current Q axis component i Q；
The position angle theta of the motor rotor is collected through a position sensor (a rotary transformer), and the electrical angular velocity omega of the motor rotor is obtained through calculation r；
2) Motor parameter calculation module
The input variables of the motor parameter calculation module are as follows:
i Qthe actual value of the Q-axis current of the motor stator is obtained;
i Q0the component of Q-axis current when the change rate of the inductance is turned;
L Q0the inductance component of the Q axis under the normal temperature state (or rated temperature) is generally a measured value or a motor design given value under the normal temperature;
L D0the inductance component of the D axis under the normal temperature state (or rated temperature) is generally a measured value or a motor design given value under the normal temperature;
ψ f0the flux linkage value is a flux linkage value under a normal temperature state (or a rated temperature), and is generally a measured value or a motor design given value under the normal temperature;
t is the temperature of the magnetic steel;
rho is a curve coefficient, and is generally 0.1-0.3%;
γ tthe magnetic steel temperature coefficient can be searched from a magnetic steel handbook;
the output variables are:
L Q(i Qt) is Q-axis inductance along with i QAnd the value of the change in the temperature t,
Figure BDA0002251609040000031
L D(t) is the value of D-axis inductance as a function of temperature t, L D(t)＝L D0γ tt；
ψ f(t) is the value of the flux linkage as a function of temperature t,. phi f(t)＝ψ f0γ tt；
ΔL err0Is a Q-axis inductor L at normal temperature Q0And D-axis inductance L D0Difference of (d), Δ L err0＝L Q0-L D0；
Δi Q0Is Q-axis actual current i QAnd i Q0Difference between, Δ i Q0＝i Q-i Q0；
3) Torque current calculation module
The torque current calculation module input variables are as follows:
T *setting torque for the motor;
ψ f0the flux linkage value of the motor is in a normal temperature state;
ΔL err0is an initial value L of the Q-axis inductance Q0And D-axis inductance initial value L D0The difference between the two;
Δi Q0is Q-axis actual current i QAnd i Q0The difference between them;
t is the temperature of the magnetic steel;
rho is a curve coefficient;
γ tmagnetic steel temperature coefficient;
Figure BDA0002251609040000032
and
Figure BDA0002251609040000033
respectively giving reference voltages to a D axis and a Q axis fed back by the current feedforward decoupling calculation module;
U Smaxin order to allow maximum amplitude of phase voltage for inverter, the control method
Figure BDA0002251609040000034
The output variables are as follows:
Figure BDA0002251609040000035
setting current for the D axis;
Figure BDA0002251609040000036
setting current for the Q axis;
the torque current calculation module is used for setting the torque T according to the input motor *Obtaining the D-axis current under the maximum torque current ratio (MTPA) calculation method through the maximum torque current ratio (MTPA) calculation method
Figure BDA0002251609040000037
D-axis gives current:
Figure BDA0002251609040000038
wherein the content of the first and second substances,
Figure BDA0002251609040000041
as
Figure BDA0002251609040000042
The compensation quantity corrects the D-axis given current in the weak magnetic region to obtain the final D-axis expected value given current
Figure BDA0002251609040000043
When the motor operates in a weak magnetic region (generally, a non-weak magnetic region below a rated rotating speed and a weak magnetic region above the rated rotating speed), firstly, a D-axis and a Q-axis given reference voltage fed back by a current feedforward decoupling calculation module are utilized to calculate the amplitude U of the given reference voltage S，U SAnd the maximum allowable phase voltage amplitude U of the inverter SmaxIs subjected to PI regulation, the regulator output is
Figure BDA0002251609040000044
When U is turned S＜U SmaxWhen the temperature of the water is higher than the set temperature,
Figure BDA0002251609040000045
equal to 0, indicating no current to the D-axis
Figure BDA0002251609040000046
Carrying out adjustment;
q-axis set current
Figure BDA0002251609040000047
When i is Q＜i Q0When the temperature of the water is higher than the set temperature,
Figure BDA0002251609040000048
when i is Q≥i Q0When the temperature of the water is higher than the set temperature,
4) current feedforward decoupling calculation module
The input parameters of the current feedforward decoupling calculation module are as follows:
Figure BDA00022516090400000410
i D、i Q、L Q(i Q,t)、L D(t)、ψ f(t); the output parameters are: given reference voltage
Figure BDA00022516090400000411
And
Figure BDA00022516090400000412
Figure BDA00022516090400000413
Figure BDA00022516090400000414
Δu Dgiven value for D-axis current
Figure BDA00022516090400000415
And D-axis current feedback value i DThe difference value is output through the result output by the PI regulator, namely D-axis current closed-loop regulation output;
similarly, Δ u QGiven value for Q-axis current
Figure BDA00022516090400000416
And Q-axis current feedback value i QThe difference value is output through a result output by a PI regulator, namely Q-axis current closed-loop regulation output;
given reference voltage output by current feedforward decoupling calculation module
Figure BDA00022516090400000417
And
Figure BDA00022516090400000418
the pulse modulation module is used for generating modulation pulses to control the motor to run.
The control method of the built-in permanent magnet synchronous motor solves the problems that the existing motor control algorithm is easily influenced by parameter change, has poor dynamic performance, is complex in algorithm and the like; the method can ensure the stable operation of the built-in permanent magnet synchronous motor, and the control method is simple and effective, high in precision and strong in usability.
1) The invention carries out on-line calculation on the torque current, carries out real-time correction according to the dynamic parameters of the motor, obtains a current calculation model containing more accurate motor parameter information, further calculates to obtain the torque current by utilizing the model, and can carry out real-time correction on the torque current at low speed and high speed so as to realize accurate torque current control. The algorithm can enable the motor to operate at a more accurate working point, and has good parameter robustness and dynamic response characteristics.
2) On the basis of a traditional permanent magnet synchronous motor vector control algorithm, motor parameters are fitted, torque current is accurately calculated and distributed, and the accurate control of the built-in permanent magnet synchronous motor is realized by utilizing the calculated torque current.
3) The precise calculation control of the reference voltage is realized in the current feedforward decoupling calculation module according to the change condition of the motor parameters (permanent magnet flux linkage, D-axis inductance and Q-axis inductance), and the motor control precision is improved.
4) Compared with the existing method, the method has the functions of dynamically adjusting the motor parameters and accurately calculating the torque current, improves the accuracy of the given voltage of the motor, has good parameter robustness, does not need complicated steps of signal injection, signal extraction and the like, simplifies the method for controlling the torque current, does not need to consider the influence of system bandwidth, and has simple algorithm, high calculation speed and good dynamic performance.
Drawings
Fig. 1 is a control block diagram of an improved method of an interior permanent magnet synchronous motor according to the present invention.
Detailed Description
The control method of the built-in permanent magnet synchronous motor comprises the following steps of dividing the control method into 4 modules (shown in figure 1) which are respectively a sampling calculation module 1, a motor parameter calculation module 2, a torque current calculation module 3 and a current feedforward decoupling calculation module 4;
1) sampling calculation module
Collecting DC bus voltage U of inverter dcAnd motor stator current i a、i b(ii) a For stator current i a、i bPerforming Clarke transformation and Park transformation to obtain a stator current D axis component i in a synchronous rotation coordinate system DAnd stator current Q axis component i Q；
The position angle theta of the motor rotor is collected through a position sensor (a rotary transformer), and the electrical angular velocity omega of the motor rotor is obtained through calculation r；
2) Motor parameter calculation module
The motor parameter calculation module is mainly a functional module for calculating parameters such as motor flux linkage, inductance and the like in real time;
the motor parameter calculation module is specifically shown in fig. 1, and input variables thereof are:
i Qthe actual value of the Q-axis current of the motor stator is obtained;
i Q0the component of Q-axis current when the change rate of the inductance is turned;
L Q0the inductance component of the Q axis under the normal temperature state (or rated working condition) is generally a measured value or a motor design given value under the normal temperature;
L D0the inductance component of the D axis under the normal temperature state (or rated working condition) is generally a measured value or a motor design given value under the normal temperature;
ψ f0the flux linkage value is a flux linkage value under a normal temperature state (or a rated working condition), and is generally a measured value or a motor design given value under the normal temperature;
t is the magnetic steel temperature, which is a value obtained by embedding a temperature sensor in the motor stator at present; the temperature change of the motor magnetic steel is relatively smooth, so that the motor magnetic steel can be regarded as a fixed value in a short time;
rho is a curve coefficient, and an approximate value is obtained by fitting a curve by adopting a finite element analysis method under the Ansoft environment, wherein the approximate value is generally 0.1-0.3%;
γ tthe magnetic steel temperature coefficient can be searched from a magnetic steel handbook;
the output variables are:
L Q(i Qt) is Q-axis inductance along with i QAnd the value of the temperature t change;
L D(t) is the value of the D-axis inductance as a function of temperature t;
ψ f(t) is the value of the flux linkage as a function of temperature t;
ΔL err0is a Q-axis inductor L at normal temperature Q0And D-axis inductance L D0A difference of (d);
Δi Q0is Q-axis actual current i QAnd i Q0The difference between them;
the three motor parameters needed in the control of the permanent magnet synchronous motor are a permanent magnet flux linkage, a quadrature axis inductance and a direct axis inductance respectively.
The permanent magnet is embedded in the D-axis magnetic circuit in the permanent magnet synchronous motor, so that the D-axis magnetic flux needs to penetrate through the iron core and the air gap as well as the permanent magnet, the Q-axis magnetic flux only needs to penetrate through the iron core and the air gap, and the magnetic permeability of the permanent magnet is close to that of air due to the fact that the magnetic permeability of the iron core is high, the magnetic resistance of the D-axis magnetic circuit is larger than that of the Q-axis magnetic circuit, and therefore Q-axis inductance L is caused QInductance L greater than D axis D. In addition, the Q-axis magnetic circuit is more easily saturated than the D-axis magnetic circuit, and therefore, with the Q-axis current i QIncrease of L QWill be significantly reduced, and L DCurrent i along D axis DThe variation of (c) is relatively small.
Acquiring a motor flux linkage and a quadrature-direct axis inductance by adopting a finite element analysis method in an Ansoft environment;
wherein the direct axis inductance and the flux linkage are approximately constant; the quadrature axis inductance is greatly influenced by the quadrature axis current and has a nonlinear relation, and an approximate fitting curve is as follows:
in the above formula, when the Q-axis current is i QWhen the temperature is small, the Q-axis magnetic circuit does not enter a saturation state, so the quadrature axis inductance is basically a constant and is a constant which slowly changes along with the temperature change; with i being QIncreasing the Q-axis magnetic circuit to saturation, decreasing the quadrature axis inductance, and increasing the turning point i QThe value is denoted as i Q0；
The permanent magnet flux linkage is influenced by the temperature of the magnetic steel, and the AC-DC axis inductance is also influenced by the temperature of the magnetic steel and the AC-DC axis current. The dynamic parameters of the motor adopting a finite element analysis method in an Ansoft environment can be expressed as follows:
for D axis inductance L DCurrent i along D axis DHas small change, is obvious only along with the change of the temperature, and has specific D-axis inductance L DThe curve with temperature is given by:
L D(t)＝L D0γ tt
magnetic linkage psi fThe curve with temperature is given by:
ψ f(t)＝ψ f0γ tt
q-axis inductor L QThe curves are expressed as follows:
Figure BDA0002251609040000072
delta L for inductance difference between Q axis and D axis errExpressed, the expression formula is as follows:
Figure BDA0002251609040000081
Δi Q0representing Q-axis current i QAnd i Q0The difference between them, the expression is as follows:
Δi Q0＝i Q-i Q0
ΔL err0represents the initial value L of the Q-axis inductance Q0And D-axis inductance initial value L D0The difference, the expression is as follows:
ΔL err0＝L Q0-L D0
3) torque current calculation module
The torque current calculation module is mainly a module for calculating the D-axis given current and the Q-axis given current in real time according to the given torque;
the input variables are as follows:
T *setting torque for the motor;
ψ f0the flux linkage value of the motor is under the normal temperature state (or rated working condition);
ΔL err0is an initial value L of the Q-axis inductance Q0And D-axis inductance initial value L D0The difference between the two;
Δi Q0is Q-axis actual current i QAnd i Q0The difference between them;
t is the temperature of the magnetic steel;
rho is a curve coefficient;
γ tis the temperature coefficient of the magnetic steel;
Figure BDA0002251609040000082
and
Figure BDA0002251609040000083
respectively setting reference voltages for a D axis and a Q axis output by the current feedforward decoupling calculation module;
U Smaxin order to allow maximum amplitude of phase voltage for inverter, the control method
Figure BDA0002251609040000084
The output variables are as follows:
Figure BDA0002251609040000085
setting current for the D axis;
Figure BDA0002251609040000086
setting current for the Q axis;
the torque current calculation module is used for setting the torque T according to the input motor *Obtaining the D-axis current under the maximum torque current ratio (MTPA) calculation method through the maximum torque current ratio (MTPA) calculation method
Figure BDA0002251609040000087
D-axis given current
Figure BDA0002251609040000091
The expression of (a) is as follows:
Figure BDA0002251609040000092
wherein the content of the first and second substances,
Figure BDA0002251609040000093
as
Figure BDA0002251609040000094
The compensation quantity corrects the D-axis given current in the weak magnetic region to obtain the final D-axis expected value given current
Figure BDA0002251609040000095
When the motor operates in a weak magnetic region (generally, a non-weak magnetic region below a rated rotating speed and a weak magnetic region above the rated rotating speed), firstly, a D-axis and a Q-axis given reference voltage fed back by a current feedforward decoupling calculation module are utilized to calculate the amplitude U of the given reference voltage S，U SAnd the maximum allowable phase voltage amplitude U of the inverter SmaxIs subjected to PI regulation, the regulator output is
Figure BDA0002251609040000096
When U is turned S＜U SmaxWhen the temperature of the water is higher than the set temperature,
Figure BDA0002251609040000097
equal to 0, indicating no current to the D-axis
Figure BDA0002251609040000098
Carrying out adjustment;
the D-axis and Q-axis given reference voltage amplitude expression fed back by the current feedforward decoupling calculation module is as follows:
Figure BDA0002251609040000099
current of Q axis
Figure BDA00022516090400000910
The calculation steps are as follows:
for a given electromagnetic torque T of the machine *And motor stator D-axis current
Figure BDA00022516090400000911
Can calculate the Q-axis current
Figure BDA00022516090400000912
Figure BDA00022516090400000913
In the above formula fIs a permanent magnet flux linkage; l is D，L QActual values of D-axis and Q-axis inductors are respectively obtained; p is the number of pole pairs;
if a more accurate Q-axis current is to be obtained
Figure BDA00022516090400000914
The quantitative motor parameter psi in the above formula is required f、L D、L QRespectively carrying out dynamic adjustment; the output of the motor parameter calculation module 2 corresponds to the variable flux linkage psi f(t) and D-axis inductance parameter L D(t) Q-axis inductance parameter L Q(i QT) substituting into the above formula, the arrangement can be given by:
simplifying the above formula, the expression can be obtained as follows:
when i is Q＜i Q0And then, the given value expression of the stator Q-axis current is as follows:
Figure BDA0002251609040000101
when i is Q≥i Q0And then, the given value expression of the stator Q-axis current is as follows:
Figure BDA0002251609040000102
in the above formula, the parameter psi f0、ΔL err0、Δi Q0、γ tT can be obtained from module 2;
as can be seen from the above formula, the temperature t of the magnetic steel is generally a slow variation, and the current is in the Q axis
Figure BDA0002251609040000103
In the process of finding, will
Figure BDA0002251609040000104
And the variation relation between magnetic linkage and inductance
Figure BDA0002251609040000105
And Q-axis feedback current i QAnd the temperature t of the magnetic steel, and the state quantity can be measured, so that the motor can be accurately controlled.
4) Current feedforward decoupling calculation module
The input parameters of the current feedforward decoupling calculation module are as follows:
Figure BDA0002251609040000106
i D、i Q、L Q(i Q,t)、L D(t)、ψ f(t); the output parameters are: given reference voltage And
Figure BDA0002251609040000108
the expression of the current feedforward decoupling calculation module is as follows:
Figure BDA00022516090400001010
Δu Dgiven value for D-axis current
Figure BDA00022516090400001011
And D-axis current feedback value i DThe difference value is output through the result output by the PI regulator, namely D-axis current closed-loop regulation output;
similarly, Δ u QGiven value for Q-axis current And Q-axis current feedback value i QThe difference value is output through a result output by a PI regulator, namely Q-axis current closed-loop regulation output;
substituting the module input variables into the expression to obtain the expression as follows:
Figure BDA00022516090400001013
Figure BDA00022516090400001014
given reference voltage output by current feedforward decoupling calculation module
Figure BDA00022516090400001015
And
Figure BDA00022516090400001016
the pulse modulation module is used for generating modulation pulses to control the motor to run.

Claims (3)

1. A control method for a built-in permanent magnet synchronous motor is characterized in that 4 modules are divided into a sampling calculation module (1), a motor parameter calculation module (2), a torque current calculation module (3) and a current feedforward decoupling calculation module (4);
1) sampling calculation module
Collecting DC bus voltage U of inverter dcAnd motor stator current i a、i b(ii) a For stator current i a、i bPerforming Clarke transformation and Park transformation to obtain a stator current D axis component i in a synchronous rotation coordinate system DAnd stator current Q axis component i Q；
The position sensor is used for acquiring the position angle theta of the motor rotor and calculating to obtain the electrical angular velocity omega of the motor rotor r；
2) Motor parameter calculation module
The input variables of the motor parameter calculation module are as follows:
i Qthe actual value of the Q-axis current of the motor stator is obtained;
i Q0the component of Q-axis current when the change rate of the inductance is turned;
L Q0setting values for inductance components of the Q shaft at normal temperature for measured values or motor design values at normal temperature;
L D0setting values for inductance components of the D shaft at normal temperature for measured values or motor design values at normal temperature;
ψ f0a flux linkage value at normal temperature, a measured value at normal temperature or a motor design set value;
t is the temperature of the magnetic steel;
rho is a curve coefficient and is 0.1-0.3%;
γ tthe magnetic steel temperature coefficient can be searched from a magnetic steel handbook;
the output variables are:
L Q(i Qt) is Q-axis inductance along with i QAnd the value of the change in the temperature t,
Figure FDA0002251609030000011
L D(t) is the value of D-axis inductance as a function of temperature t, L D(t)＝L D0γ tt；
ψ f(t) is the value of the flux linkage as a function of temperature t,. phi f(t)＝ψ f0γ tt；
ΔL err0Is a Q-axis inductor L at normal temperature Q0And D-axis inductance L D0Difference of (d), Δ L err0＝L Q0-L D0；
Δi Q0Is Q-axis actual current i QAnd i Q0Difference between, Δ i Q0＝i Q-i Q0；
3) Torque current calculation module
The torque current calculation module input variables are as follows:
T *setting torque for the motor;
ψ f0the flux linkage value of the motor is in a normal temperature state;
ΔL err0is an initial value L of the Q-axis inductance Q0And D-axis inductance initial value L D0The difference between the two;
Δi Q0is Q-axis actual current i QAnd i Q0The difference between them;
t is the temperature of the magnetic steel;
rho is a curve coefficient;
γ tmagnetic steel temperature coefficient;
Figure FDA0002251609030000021
and
Figure FDA0002251609030000022
respectively giving reference voltages to a D axis and a Q axis fed back by the current feedforward decoupling calculation module;
U Smaxallowing a maximum phase voltage amplitude for the inverter;
the output variables are as follows:
Figure FDA0002251609030000023
setting current for the D axis;
Figure FDA0002251609030000024
setting current for the Q axis;
the torque current calculation module is used for setting the torque T according to the input motor *Obtaining the D-axis current under the maximum torque current ratio calculation method through the maximum torque current ratio calculation method
Figure FDA0002251609030000025
Figure FDA0002251609030000026
Wherein the content of the first and second substances,
Figure FDA0002251609030000027
as
Figure FDA0002251609030000028
The compensation quantity of the D-axis current compensation device corrects the D-axis given current in the weak magnetic region;
when the motor runs in a weak magnetic field, firstly, the amplitude U of the given reference voltage is calculated by using the D-axis and Q-axis given reference voltages fed back by the current feedforward decoupling calculation module S，U SAnd the maximum allowable phase voltage amplitude U of the inverter SmaxIs subjected to PI regulation, the regulator output is
Figure FDA0002251609030000029
When U is turned S＜U SmaxWhen the temperature of the water is higher than the set temperature,
Figure FDA00022516090300000210
equal to 0, indicating no current to the D-axis
Figure FDA00022516090300000211
Carrying out adjustment;
q-axis set current
Figure FDA0002251609030000031
When i is Q＜i Q0When the temperature of the water is higher than the set temperature,
Figure FDA0002251609030000032
when i is Q≥i Q0When the temperature of the water is higher than the set temperature,
Figure FDA0002251609030000033
4) current feedforward decoupling calculation module
The input parameters of the current feedforward decoupling calculation module are as follows:
Figure FDA0002251609030000034
i D、i Q、L Q(i Q,t)、L D(t)、ψ f(t); the output parameters are: given reference voltage
Figure FDA0002251609030000035
And
Figure FDA0002251609030000036
Δu Dgiven value for D-axis current
Figure FDA0002251609030000039
And D-axis current feedback value i DThe difference value is output through the result output by the PI regulator, namely D-axis current closed-loop regulation output;
similarly, Δ u QGiven value for Q-axis current
Figure FDA00022516090300000310
And D-axis current feedback value i QThe difference value is output through a result output by a PI regulator, namely Q-axis current closed-loop regulation output;
given reference voltage output by current feedforward decoupling calculation module
Figure FDA00022516090300000311
And the pulse modulation module is used for generating modulation pulses to control the motor to run.
2. The improved control method of interior permanent magnet synchronous motor according to claim 1, characterized in that, in 3) the torque current calculation module,
Figure FDA00022516090300000313
3. the improved control method of interior permanent magnet synchronous motor according to claim 1 or 2, characterized in that, in 3) the torque current calculation module,
Figure FDA00022516090300000314
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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112398399A (en) * 2020-12-09 2021-02-23 中国船舶工业系统工程研究院 Active suppression method for vibration noise of permanent magnet synchronous motor
CN112589832A (en) * 2020-12-04 2021-04-02 成都卡诺普自动化控制技术有限公司 Method for determining maximum working torque of robot joint
CN117439474A (en) * 2023-12-20 2024-01-23 深圳市科沃电气技术有限公司 Industrial ceiling fan permanent magnet synchronous motor control method and device

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20090251096A1 (en) * 2008-04-04 2009-10-08 Gm Global Technology Operations, Inc. Method and apparatus for torque ripple reduction
US20180219503A1 (en) * 2015-07-21 2018-08-02 Denso Corporation Control apparatus for rotary electric machines
CN109150042A (en) * 2018-07-23 2019-01-04 同济大学 A kind of surface permanent magnetic synchronous motor Feedforward Decoupling field weakening control method
CN109217766A (en) * 2018-09-26 2019-01-15 河南科技大学 The independent reversed decoupling control system of induction-type bearingless motor
CN109428525A (en) * 2018-10-31 2019-03-05 天津工业大学 Permanent magnet synchronous motor maximum torque per ampere control method based on parameter self modification
DE102018105672A1 (en) * 2017-12-15 2019-06-19 Schaeffler Technologies AG & Co. KG Method and device for online adaptation of magnetic flux linkage characteristics of permanent magnet synchronous machines by combining recursive least squares algorithm and self-organizing map

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20090251096A1 (en) * 2008-04-04 2009-10-08 Gm Global Technology Operations, Inc. Method and apparatus for torque ripple reduction
US20180219503A1 (en) * 2015-07-21 2018-08-02 Denso Corporation Control apparatus for rotary electric machines
DE102018105672A1 (en) * 2017-12-15 2019-06-19 Schaeffler Technologies AG & Co. KG Method and device for online adaptation of magnetic flux linkage characteristics of permanent magnet synchronous machines by combining recursive least squares algorithm and self-organizing map
CN109150042A (en) * 2018-07-23 2019-01-04 同济大学 A kind of surface permanent magnetic synchronous motor Feedforward Decoupling field weakening control method
CN109217766A (en) * 2018-09-26 2019-01-15 河南科技大学 The independent reversed decoupling control system of induction-type bearingless motor
CN109428525A (en) * 2018-10-31 2019-03-05 天津工业大学 Permanent magnet synchronous motor maximum torque per ampere control method based on parameter self modification

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112589832A (en) * 2020-12-04 2021-04-02 成都卡诺普自动化控制技术有限公司 Method for determining maximum working torque of robot joint
CN112589832B (en) * 2020-12-04 2022-04-29 成都卡诺普机器人技术股份有限公司 Method for determining maximum working torque of robot joint
CN112398399A (en) * 2020-12-09 2021-02-23 中国船舶工业系统工程研究院 Active suppression method for vibration noise of permanent magnet synchronous motor
CN117439474A (en) * 2023-12-20 2024-01-23 深圳市科沃电气技术有限公司 Industrial ceiling fan permanent magnet synchronous motor control method and device
CN117439474B (en) * 2023-12-20 2024-02-20 深圳市科沃电气技术有限公司 Industrial ceiling fan permanent magnet synchronous motor control method and device

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