CN110362890A - A kind of calculation method of meter and the variable-frequency motor iron loss resistance under PWM harmonic condition - Google Patents
A kind of calculation method of meter and the variable-frequency motor iron loss resistance under PWM harmonic condition Download PDFInfo
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R27/00—Arrangements for measuring resistance, reactance, impedance, or electric characteristics derived therefrom
- G01R27/02—Measuring real or complex resistance, reactance, impedance, or other two-pole characteristics derived therefrom, e.g. time constant
- G01R27/26—Measuring inductance or capacitance; Measuring quality factor, e.g. by using the resonance method; Measuring loss factor; Measuring dielectric constants ; Measuring impedance or related variables
- G01R27/2688—Measuring quality factor or dielectric loss, e.g. loss angle, or power factor
- G01R27/2694—Measuring dielectric loss, e.g. loss angle, loss factor or power factor
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- G—PHYSICS
- G06—COMPUTING; CALCULATING OR COUNTING
- G06F—ELECTRIC DIGITAL DATA PROCESSING
- G06F30/00—Computer-aided design [CAD]
- G06F30/30—Circuit design
- G06F30/36—Circuit design at the analogue level
- G06F30/367—Design verification, e.g. using simulation, simulation program with integrated circuit emphasis [SPICE], direct methods or relaxation methods
Abstract
The invention discloses a kind of calculation methods of the variable-frequency motor iron loss resistance under meter and PWM harmonic condition, belong to alternating current generator loss analysis and calculating field, induction machine iron loss resistance is expressed as the function of induced potential and revolving speed based on being segmented variable coefficient iron loss model by this method.This method meter and the additional iron loss generated by PWM harmonics of inverter and the surface generated by motor space harmonics and pulsation loss.Using the method for the present invention, the accurate variable-frequency motor equivalent circuit under the conditions of meter and iron loss can be obtained.Finally, obtaining their iron loss resistance changing law by taking 5.5kW and 30kW variable frequency induction motor as an example.And effectiveness of the invention is verified using this two induction machines.
Description
Technical field
The invention belongs to alternating current generator loss analysis and calculating fields, and in particular to it is a kind of meter and PWM harmonic condition under
The calculation method of variable-frequency motor iron loss resistance.
Background technique
PWM frequency changing driving system and induction machine are highly integrated at this stage.PWM frequency conversion drive contain a large amount of harmonic wave at
Point, these harmonic components have a great impact to induction machine loss.It, first should be able to be fast and accurately to reduce motor iron loss
Calculate the iron loss of PWM conversion power supply induction machine.Induction machine iron loss generally can calculate (Analytic Calculation Method) or field by road
It calculates (finite element method).Due to considering the complicated geometry and material property of motor, the iron calculated based on finite element method
It consumes more accurate.But the iron loss model calculation amount based on finite element method be it is very big, this give iron loss real-time acquisition band
Very big difficulty is carried out.In addition, parameter required for motor control is that parameter (calculates ginseng in road in induction machine equivalent circuit
Number).It therefore, is to need accurately to count in induction machine equivalent circuit from the efficiency of the orientation optimization induction machine of motor control
And iron loss substitutional resistance.The equivalent iron loss substitutional resistance is required to be calculated using parameter in induction machine equivalent circuit and (be utilized
Analytic Calculation Method obtains).
In order in the Induction motor design initial stage, obtain accurate motor iron loss, many scholars are from difference
Angle propose many iron losses computation models.Wherein, widely applied classical iron loss model is by Steinmetz equation
It optimizes and obtains；Classical iron loss model is different according to the factor that iron loss generates, and iron loss is divided into magnetic hysteresis and eddy-current loss,
The coefficient of model is constant.Due to the complex nonlinear characteristic of ferromagnetic material, when induction machine works in revolving speed and voltage amplitude
When value variation range is larger, classical iron loss model will be no longer applicable in.In order to consider harmonic field to induction machine stator-rotor iron core
The influence of loss, document " segmentation variable coefficient iron losses computation mould of the such as Zhang Dongdong, Zhao Haisen for loss of electric machine fining analysis
Type [J] electrotechnics journal, 2016,31 (15): 16-24. " and " such as Zhang Dongdong, Guo Xinzhi induction machine based on DFT turn
Sub- harmonic flux density efficient separation method and loading condition down coversion rotor iron loss characteristic [J] electrotechnics journal,
2019,34 (01): 75-83. " proposes a kind of segmentation variable coefficient iron loss model, the calculating variable-frequency electric which can accurately calculate
Machine iron loss.But the model is based on finite element method, therefore calculating speed is still very slow.
Summary of the invention
In order to overcome the disadvantages of the above prior art, the purpose of the present invention is to provide under a kind of meter and PWM harmonic condition
Variable-frequency motor iron loss resistance calculation method, this method is based on being segmented variable coefficient iron loss model, by induction machine iron loss
Resistance is expressed as the function of induced potential and revolving speed, and counts and the additional iron loss that is generated by PWM harmonics of inverter and by electricity
The surface and pulsation loss that machine space harmonics generates, processing accuracy are high.
In order to achieve the above object, the present invention is achieved by the following scheme:
The calculation method of a kind of meter and PWM harmonic condition down coversion motor iron loss resistance disclosed by the invention,
Based on being segmented Varying-Coefficient Models, the flux density being segmented in Varying-Coefficient Models and frequency variable are used into induced electricity respectively
Gesture and speed variable replacement；By way of being segmented variable coefficient meter and the basic iron loss of motor with supply frequency variation, to ask
Solution obtains the basic iron loss of PWM harmonic condition down coversion motor.
Preferably, the specific method is as follows for foundation meter and the basic iron loss of PWM harmonic condition down coversion motor:
The magnetic hystersis loss P indicated with revolving speed and induced potentialH_sin, as shown in formula (8):
In formula,BmFor fundamental wave flux density amplitude；khIt is classical magnetic hystersis loss with α
Term coefficient；F is supply voltage fundamental frequency；k1And β1To add magnetic hystersis loss flux density term coefficient, k1And β1Become with flux density and frequency
Change；N*It is that stator is often connected in series equivalent the number of turns, S is the equivalent iron core cross-sectional area of motor；Em1For the amplitude of fundamental wave induced potential；Together
Walk revolving speed Ω1；P is the number of pole-pairs of motor；
The eddy-current loss P indicated with revolving speed and induced potentialE_sin, as shown in formula (9)
In formula,keFor classical eddy-current loss term coefficient；k2And β2Flux density item is lost for extraneous turbulence
Coefficient, k2And β2Change with flux density and frequency.
Preferably, the flux density for being segmented Varying-Coefficient Models and frequency variable induced potential and speed variable are replaced same
When, also counted by introducing relevant to PWM frequency converter output voltage coefficient and PWM harmonics of inverter to the basic iron loss of motor with
Influence.
It is further preferred that the magnetic hysteresis as caused by supply voltage harmonic wave and eddy-current loss, with induction machine supply voltage
Related coefficient compensates, compensated magnetic hystersis loss PH_PWMWith eddy-current loss PE_PWMIt is respectively as follows:
PE_PWM=χ2PE_sin (11)
In formula, EavFor the average value of induced potential；Eav1For the average value of fundamental wave induced potential；ErmsFor having for induced potential
Valid value；Erms1For the virtual value of fundamental wave induced potential；E (t) is the function that induced potential changes over time；T is induced electromotive force
Primitive period.
Preferably, the flux density for being segmented Varying-Coefficient Models and frequency variable induced potential and speed variable are replaced same
When, it is also contemplated that influence of the motor tooth socket to variable-frequency motor iron loss.
It is further preferred that specifically solving as follows:
Since the surface that motor fluting generates adds iron loss PsurfL, as shown in formula (16):
PsurfL=CsurfLEm1 2Ω1.5 (16)
CsurfL=KL1Csurf0 (18)
In formula,Z1For number of stator teeth；α'pFor the effective pole arc coefficients, the coefficient
It is related with iron core degree of saturation；lmFor motor axial length；D2For rotor diameter；lδFor motor gas-gap width；Ω is motor speed；
Csurf0For unloaded surface added losses coefficient；k0It is coefficient relevant to silicon steel sheet material and processing factors；Kδ1For stator teeth notching,
Carter's coefficient when rotor surface is smooth；β01For the function of stator rabbet width, specific value can table look-up acquisition；KL1It is fixed
Sub- slot ripples load factor, the relevant coefficients such as value and motor load, rotor slot size；t1For stator tooth away from；t2To turn
Sub- tooth pitch；b02For rotor width of rebate b02；
Since what motor fluting generated causes induction machine stator pulsation loss PpsLWith rotor pulsation loss PprLIt is respectively as follows:
PpsL=CpsLEm1 2Ω2 (19)
PprL=CprLEm1 2Ω2 (20)
Wherein,
In formula, Z2For number of rotor teeth；Gt1And Gt2The respectively weight of electric machine rotor tooth；KL1And KL2Respectively stator and
Rotor tooth harmonic load coefficient；γ1And γ2Coefficient respectively relevant to stator, rotor width of rebate, is shown below:
The total pulsation loss P of variable-frequency motor rotorpLAre as follows:
The loss that motor iron loss is equal to by the model and the iron loss resistance on induced potential generates, the total iron loss of variable-frequency motor
As shown in formula (25):
Iron loss equivalent resistance RFeAs shown in formula (26), formula (26) feed back out the iron loss resistance with the change of induced potential and revolving speed
Change and change:
Compared with prior art, the invention has the following advantages:
1) variable-frequency motor iron loss resistance preparation method disclosed by the invention becomes the flux density for being segmented Varying-Coefficient Models and frequency
Amount is replaced with induced potential and speed variable, by way of being segmented variable coefficient meter and the basic iron loss of motor with supply frequency change
Change, and introduce relevant to PWM frequency converter output voltage coefficient come count and PWM harmonics of inverter to the basic iron loss of motor with shadow
It rings.It therefore is that motor basic iron loss when meter and PWM harmonics of inverter condition is inhibited to bring greatly from the angle of motor control
It is convenient；
2) variable-frequency motor iron loss resistance preparation method disclosed by the invention, it is contemplated that motor tooth socket is to variable-frequency motor iron loss
It influences, and by the equation of the partition losses induced potential fundamental voltage amplitude and revolving speed.Therefore for from the angle of motor control inhibit by
The loss that motor tooth socket generates brings great convenience；
3) preparation method of iron loss resistance disclosed by the invention is applicable not only to common variable frequency induction motor iron loss resistance and asks
Solution, can be used for magneto, switched reluctance machines and other type motors；
4) the accurate variable-frequency motor equivalent circuit under the conditions of meter and iron loss can be obtained using the present invention.Specifically, with one
For platform 5.5kW and a 30kW variable frequency induction motor, their iron loss resistance changing law is obtained.And utilize this two senses
Motor is answered to verify the validity of the method for the present invention.
Detailed description of the invention
Fig. 1 is the induction machine equivalent circuit diagram under the conditions of meter and motor iron loss；
When Fig. 2 is rated power supply, 5.5kW variable-frequency motor surveys line voltage and electric current；
When Fig. 3 is rated power supply, 30kW variable-frequency motor surveys line voltage and electric current；
Fig. 4 is 5.5kW induction machine iron loss resistance changing law；
Fig. 5 is 30kW induction machine iron loss resistance changing law；
When Fig. 6 a is sinusoidal power supply, 5.5kW induction machine iron losses computation and actual measurement are compared；
When Fig. 6 b is conversion power supply, 5.5kW induction machine iron losses computation and actual measurement are compared；
When Fig. 7 a is sinusoidal power supply, 30kW induction machine iron losses computation and actual measurement are compared；
When Fig. 7 b is conversion power supply, 30kW induction machine iron losses computation and actual measurement are compared.
Specific embodiment
In order to enable those skilled in the art to better understand the solution of the present invention, below in conjunction in the embodiment of the present invention
Attached drawing, technical scheme in the embodiment of the invention is clearly and completely described, it is clear that described embodiment is only
The embodiment of a part of the invention, instead of all the embodiments.Based on the embodiments of the present invention, ordinary skill people
The model that the present invention protects all should belong in member's every other embodiment obtained without making creative work
It encloses.
It should be noted that description and claims of this specification and term " first " in above-mentioned attached drawing, "
Two " etc. be to be used to distinguish similar objects, without being used to describe a particular order or precedence order.It should be understood that using in this way
Data be interchangeable under appropriate circumstances, so as to the embodiment of the present invention described herein can in addition to illustrating herein or
Sequence other than those of description is implemented.In addition, term " includes " and " having " and their any deformation, it is intended that cover
Cover it is non-exclusive include, for example, the process, method, system, product or equipment for containing a series of steps or units are not necessarily limited to
Step or unit those of is clearly listed, but may include be not clearly listed or for these process, methods, product
Or other step or units that equipment is intrinsic.
The invention will be described in further detail with reference to the accompanying drawing:
A kind of meter proposed by the present invention and PWM harmonic condition down coversion motor iron loss resistance calculations method, become system with segmentation
Based on number iron loss model, induction machine iron loss resistance is expressed as to the function of induced potential and revolving speed.This method meter and by
The additional iron loss and the surface generated by motor space harmonics and pulsation loss that PWM harmonics of inverter generates.It is specific to establish meter
And PWM harmonic condition down coversion motor iron loss resistive method is as follows:
The limitation of classical iron loss model is, when flux density is greater than 1.2T or frequency is more than 400Hz, is calculated by classical model
Iron loss value it is less than normal compared with measured value；All coefficients in classical model are constant coefficient, therefore can not be suitable for electric machine iron core magnetic
The larger situation of close amplitude or frequency range.
In order to obtain more accurate predicted value, induction machine magnetic in induction machine supply voltage and larger rotation speed change
Stagnant loss can be found out by following formula:
In formula, k1And β1To add magnetic hystersis loss flux density term coefficient, they change with flux density and frequency.
Induction machine eddy-current loss can be found out by following formula:
In formula, k2And β2Flux density term coefficient is lost for extraneous turbulence, they change with flux density and frequency.
Since induction machine core tooth part and the distribution of yoke portion flux density are not that uniformly, this gives solution motor stator teeth portion, yoke
The equivalent cross-sectional area of portion and rotor teeth portion, yoke portion brings difficulty.When solving electric machine iron core equivalent area, ignore induction machine
The inhomogeneities of core tooth part and the distribution of yoke portion flux density.Ignoring the sky generated by induction machine tooth socket etc. by self structure factor
Under conditions of m-Acetyl chlorophosphonazo and leakage magnetic flux, it is believed that motor yoke flux density is only walked tangentially, and teeth portion flux density only walks radial direction.And due to induction
Motor slip frequency is generally very low, therefore, ignores the basic iron loss of rotor-side.At this point, induced potential e (t) and flux density change
The relationship of rate is
In formula, N*It is that stator is often connected in series equivalent the number of turns, S is the equivalent iron core cross-sectional area of motor, and t is time, B (t) magnetic
Flux density.
It can be obtained by formula (3):
Then fundamental wave potential is in the relationship of fundamental wave flux density are as follows:
Wherein, Em1For the amplitude of fundamental wave induced potential.
The synchronous rotational speed Ω of induction machine is used below1To replace supply voltage fundamental frequency f.Relationship between them are as follows:
In formula, p is the number of pole-pairs of motor.
It brings formula (6) into formula (5), can obtain:
The magnetic hystersis loss indicated with revolving speed and induced potential can be found out by bringing formula (7) into formula (1), as shown in formula (8):
Similarly, the eddy-current loss indicated with revolving speed and induced potential can be found out by bringing formula (7) into formula (2), such as formula (9) institute
Show:
Since present induction machine is typically all to apply frequency control, so its supply voltage is not the sine of standard
Wave.The magnetic hysteresis as caused by supply voltage harmonic wave and eddy-current loss can be mended with coefficient related with induction machine supply voltage
It repays, compensated magnetic hysteresis and eddy-current loss are respectively as follows:
PE_PWM=χ2PE_sin (11)
In formula,
Present induction machine uses Distributed Winding structure generally to eliminate since 5,7,11 and 13 grade space harmonics magnetic are dynamic
The air-gap field that gesture generates, even if motor stator uses integral pitch winding, compared to the iron loss generated by a harmony wave, by
5, the iron loss that 7,11 and 13 grade space harmonics magnetomotive force generate is negligible.Therefore, the present invention only counts and by one
The iron loss that secondary slot ripples generates.When ignoring voltage harmonic, air gap flux density BδIt can be found out by following formula:
In formula, BδFor air gap flux density；α'pFor the effective pole arc coefficients, iron core degree of saturation is related；lδFor motor gas-gap width.
The harmony wave as caused by stator teeth notching generates surface loss and stator tooth away from t in rotor surface1, rotor slot-pitch
t2, motor speed Ω and rotor width of rebate b02Equal relating to parameters.When unloaded, surface added losses can be found out by formula (15)
Psurf0=Csurf0Em1 2Ω1.5 (15)
In formula, Csurf0For unloaded surface added losses coefficient.
Surface loss when load can be found out by formula (16):
PsurfL=CsurfLEm1 2Ω1.5 (16)
CsurfL=KL1Csurf0 (18)
In formula, k0It is coefficient relevant to silicon steel sheet material and processing factors；Kδ1For stator teeth notching, when rotor surface is smooth
Carter's coefficient；β01For the function of stator rabbet width, specific value can table look-up acquisition；KL1For stator tooth harmonic load system
Number, the relevant coefficients such as value and motor load, rotor slot size.
Due to the slot effect of motor, motor will turn tooth socket corresponding relationship surely constantly to be changed.Surely turning tooth socket corresponding relationship will
Constantly variation will cause the variation of iron core magnetic conductance, and then rotor teeth portion flux density is caused to generate fluctuation.By rotor teeth portion flux density
Fluctuation induction machine rotor pulsation loss will be caused to be respectively as follows:
PpsL=CpsLEm1 2Ω2 (19)
PprL=CprLEm1 2Ω2 (20)
In formula,
In formula, KL2For rotor tooth harmonic load coefficient；γ1And γ2System respectively relevant to stator, rotor width of rebate
Number, is shown below:
So the pulsation loss that induction machine rotor is total are as follows:
The loss that motor iron loss is equal to by the model and the iron loss resistance on induced potential generates.The total iron loss of variable-frequency motor
As shown in formula (25).
Wherein, iron loss equivalent resistance RFeAs shown in formula (26):
From formula (26) as can be seen that the iron loss resistance changes with the variation of induced potential and revolving speed.And expression formula will become
Frequency motor iron loss resistance is expressed as the function of induced potential fundamental wave potential and revolving speed, is very easy to obtain.
Embodiment 1
With a 5.5kW variable frequency induction motor, parameter difference is as shown in table 1.Under rated condition, the voltage of two motors
It is as shown in Fig. 2 with current waveform.Using the method for solving of iron loss resistance proposed by the present invention, calculate its iron loss resistance with turn
The situation of change such as attached drawing 4 of the index of modulation of speed and PWM frequency converter.Wherein, the switching frequency of frequency converter is 5kHz, when revolving speed is low
When specified synchronous rotational speed, guarantee that the ratio of induced potential and frequency is constant；When synchronous rotational speed is more than specified synchronous rotational speed, take
Induced potential is steady state value.As can be seen that the index of modulation of PWM inverter is higher, the equivalent electricity of the higher iron loss of induction machine revolving speed
It hinders bigger.
Embodiment 2
With a 30kW variable frequency induction motor, parameter difference is as shown in table 2.Under rated condition, the voltage of two motors
It is as shown in Fig. 3 with current waveform.Using the method for solving of iron loss resistance proposed by the present invention, calculate its iron loss resistance with turn
The situation of change such as attached drawing 5 of the index of modulation of speed and PWM frequency converter.Wherein, the switching frequency of frequency converter is 5kHz, when revolving speed is low
When specified synchronous rotational speed, guarantee that the ratio of induced potential and frequency is constant；When synchronous rotational speed is more than specified synchronous rotational speed, take
Induced potential is steady state value.As can be seen that the index of modulation of PWM inverter is higher, the equivalent electricity of the higher iron loss of induction machine revolving speed
It hinders bigger.
Embodiment 3
It is utilized respectively the method for the present invention based on analytic method and the classical model based on time-stepping FEM and segmentation becomes
Modulus Model calculates the variable frequency induction motor of a specification 5.5kW as shown in Table 1 in different power voltage sine power supply item
Iron loss under part.Actual measurement and simulation comparison are as shown in figures 6 a and 6b.As can be seen that and the method for the present invention and segmentation variable coefficient mould
Type calculated value is then very close to measured value.
Embodiment 4
It is utilized respectively the method for the present invention based on analytic method and the classical model based on time-stepping FEM and segmentation becomes
Modulus Model calculates the variable frequency induction motor of a specification 30kW as shown in Table 2 in different power voltage sine condition of power supply
Under iron loss.Actual measurement and simulation comparison are as shown in figs. 7 a and 7b.As can be seen that the method for the present invention and segmentation Varying-Coefficient Models meter
Calculation value is very close to measured value.
The rule parameter of 1 5.5kW induction machine of table
The specifications parameter of 2 30kW induction machine of table
In conclusion a kind of meter disclosed by the invention and PWM harmonic condition down coversion motor iron loss resistance preparation method, with
It is segmented based on variable coefficient iron loss model, induction machine iron loss is expressed as to the function of induced potential and revolving speed.This method meter and
The additional iron loss that is generated by PWM harmonics of inverter, and consider motor space-harmonic component to rotor teeth portion surface and
The influence of pulsation loss.Based on the Analytic Calculation Method of the PWM conversion power supply induction machine iron loss in text, present invention obtains meters
And the variable frequency induction motor equivalent-circuit model under the conditions of iron loss.Finally, with 5.5kW and 30kW variable frequency induction motor
For, the substitutional resistance changing rule for obtaining them is solved using the method for the present invention.And it is utilized respectively the method for the present invention, is based on
The classical model of time-stepping FEM and segmentation Varying-Coefficient Models based on time-stepping FEM calculate above-mentioned two variable frequency induction electricity
Machine different rotating speeds iron loss, and with actual measurement compare, comparing result show context of methods precision it is higher.
The above content is merely illustrative of the invention's technical idea, and this does not limit the scope of protection of the present invention, all to press
According to technical idea proposed by the present invention, any changes made on the basis of the technical scheme each falls within claims of the present invention
Protection scope within.
Claims (6)
1. the calculation method of a kind of meter and PWM harmonic condition down coversion motor iron loss resistance, it is characterised in that:
Based on being segmented Varying-Coefficient Models, by be segmented Varying-Coefficient Models in flux density and frequency variable use respectively induced potential and
Speed variable replacement；By way of being segmented variable coefficient meter and the basic iron loss of motor with supply frequency variation, to solve
To the basic iron loss of PWM harmonic condition down coversion motor.
2. the calculation method of meter according to claim 1 and PWM harmonic condition down coversion motor iron loss resistance, feature exist
In the specific method is as follows for foundation meter and the basic iron loss of PWM harmonic condition down coversion motor:
The magnetic hystersis loss P indicated with revolving speed and induced potentialH_sin, as shown in formula (8):
In formula,BmFor fundamental wave flux density amplitude；khIt is classical magnetic hystersis loss term system with α
Number；F is supply voltage fundamental frequency；k1And β1To add magnetic hystersis loss flux density term coefficient, k1And β1Change with flux density and frequency；N*
It is that stator is often connected in series equivalent the number of turns, S is the equivalent iron core cross-sectional area of motor；Em1For the amplitude of fundamental wave induced potential；It is synchronous to turn
Fast Ω1；P is the number of pole-pairs of motor；
The eddy-current loss P indicated with revolving speed and induced potentialE_sin, as shown in formula (9)
In formula,keFor classical eddy-current loss term coefficient；k2And β2Flux density term system is lost for extraneous turbulence
Number, k2And β2Change with flux density and frequency.
3. the calculation method of meter according to claim 1 and PWM harmonic condition down coversion motor iron loss resistance, feature exist
In also passing through introducing while replacing the flux density for being segmented Varying-Coefficient Models and frequency variable induced potential and speed variable
Coefficient relevant to PWM frequency converter output voltage come count and PWM harmonics of inverter to the basic iron loss of motor with influence.
4. the calculation method of meter according to claim 3 and PWM harmonic condition down coversion motor iron loss resistance, feature exist
In the magnetic hysteresis as caused by supply voltage harmonic wave and eddy-current loss are compensated with coefficient related with induction machine supply voltage, are mended
Magnetic hystersis loss P after repayingH_PWMWith eddy-current loss PE_PWMIt is respectively as follows:
PE_PWM=χ2PE_sin (11)
In formula, EavFor the average value of induced potential；Eav1For the average value of fundamental wave induced potential；ErmsFor the effective of induced potential
Value；Erms1For the virtual value of fundamental wave induced potential；E (t) is the function that induced potential changes over time；T is induced electromotive force base
Wave period.
5. the calculation method of meter according to claim 1 and PWM harmonic condition down coversion motor iron loss resistance, feature exist
In while the flux density for being segmented Varying-Coefficient Models and frequency variable induced potential and speed variable are replaced, it is also contemplated that motor
Influence of the tooth socket to variable-frequency motor iron loss.
6. the calculation method of meter according to claim 5 and PWM harmonic condition down coversion motor iron loss resistance, feature exist
In specific solution is as follows:
Since the surface that motor fluting generates adds iron loss PsurfL, as shown in formula (16):
PsurfL=CsurfLEm1 2Ω1.5 (16)
CsurfL=KL1Csurf0 (18)
In formula,Z1For number of stator teeth；α'pFor the effective pole arc coefficients, the coefficient and iron
Heart degree of saturation is related；lmFor motor axial length；D2For rotor diameter；lδFor motor gas-gap width；Ω is motor speed；Csurf0For
Unloaded surface added losses coefficient；k0It is coefficient relevant to silicon steel sheet material and processing factors；Kδ1For stator teeth notching, rotor table
Carter's coefficient when face is smooth；β01For the function of stator rabbet width, specific value can table look-up acquisition；KL1It is humorous for stator tooth
Carrier load coefficient, the relevant coefficients such as value and motor load, rotor slot size；t1For stator tooth away from；t2For rotor tooth
Away from；b02For rotor width of rebate b02；
Since what motor fluting generated causes induction machine stator pulsation loss PpsLWith rotor pulsation loss PprLIt is respectively as follows:
PpsL=CpsLEm1 2Ω2 (19)
PprL=CprLEm1 2Ω2 (20)
Wherein,
In formula, Z2For number of rotor teeth；Gt1And Gt2The respectively weight of electric machine rotor tooth；KL1And KL2Respectively stator and rotor
Slot ripples load factor；γ1And γ2Coefficient respectively relevant to stator, rotor width of rebate, is shown below:
The total pulsation loss P of variable-frequency motor rotorpLAre as follows:
The loss that motor iron loss is equal to by the model and the iron loss resistance on induced potential generates, the total iron loss of variable-frequency motor such as formula
(25) shown in:
Iron loss equivalent resistance RFeAs shown in formula (26), formula (26) feed back out the iron loss resistance with the variation of induced potential and revolving speed and
Variation:
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| PCT/CN2019/128886 WO2020258802A1 (en) | 2019-06-28 | 2019-12-26 | Method for calculating iron loss resistance of variable frequency motor while considering pwm harmonic waves |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN113049998B (en) * | 2021-02-08 | 2021-11-02 | 华北电力大学（保定） | Ferromagnetic material loss prediction method under multi-harmonic excitation effect |
| CN113328674A (en) * | 2021-06-07 | 2021-08-31 | 广西大学 | High-speed permanent magnet motor permanent magnet loss compensation method and system considering time-space harmonic conditions |
| CN113361167A (en) * | 2021-06-07 | 2021-09-07 | 哈尔滨理工大学 | High-speed motor iron loss rapid calculation method and model based on rotating speed |
| CN113328674B (en) * | 2021-06-07 | 2022-08-09 | 广西大学 | High-speed permanent magnet motor permanent magnet loss compensation method and system considering time-space harmonic conditions |
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