CN109870684B - CP-OFDM-based radar range profile reconstruction method under background of fragment frequency spectrum - Google Patents

CP-OFDM-based radar range profile reconstruction method under background of fragment frequency spectrum Download PDF

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CN109870684B
CN109870684B CN201910211233.9A CN201910211233A CN109870684B CN 109870684 B CN109870684 B CN 109870684B CN 201910211233 A CN201910211233 A CN 201910211233A CN 109870684 B CN109870684 B CN 109870684B
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张天贤
刘辛雨
干娜
邓艳红
孔令讲
崔国龙
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University of Electronic Science and Technology of China
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Abstract

The invention discloses a CP-OFDM-based radar range profile reconstruction method under a fragment frequency spectrum background, which comprises the following steps: s1, dividing the resource block, dividing the OFDM signal into a plurality of resource blocks; s2, obtaining a transmitting signal by modulating the frequency to an available fragment frequency band, and analyzing an echo signal; and S3, performing pulse compression on the signal obtained in the step S2. The invention divides the symbol to be modulated into one resource block according to the number of subcarriers in the frequency band range by using the specific frequency band range and the number of subcarriers of the known fragmented frequency spectrum, correspondingly modulates to form a transmitting signal, splices the frequency bands of all the resource blocks when demodulating the target distance information, performs pulse compression processing to obtain a distance image with nearly zero distance side lobe, and can meet the basic requirements of a radar communication integrated system.

Description

CP-OFDM-based radar range profile reconstruction method under background of fragment frequency spectrum
Technical Field
The invention belongs to the field of radar imaging, and particularly relates to a radar range profile reconstruction method based on CP-OFDM under a fragment frequency spectrum background.
Background
The integrated signal sharing in the radar communication integrated technology enables the radar and the communication part not to be obviously separated in a time domain or a space domain, a set of hardware device is shared, the high-efficiency transmission of communication data is realized while the radar target detection is carried out, the distance and Doppler resolution capability are high, and the radar detection target principle is shown in figure 1. In the field of traditional radar imaging, linear frequency modulation signals with large time-band products are mostly adopted to detect and position a target, and distance position information with higher resolution is obtained. Due to the self-correlation characteristic of the linear frequency modulation signal, when a pulse compression method of matched filtering is adopted in back-end signal processing to reconstruct a target range profile, a side lobe is very high, so that a target with weak strength is interfered by a side lobe level of a strong target and is difficult to recover, and the problem of low communication rate exists in the process of overlapping communication signals on the basis of the radar signal, so that the radar signal has no great advantage as an integrated signal. The OFDM technology effectively resists multipath fading in communication, is easy to synchronize and balance, realizes high-efficiency information transmission and frequency band utilization, and the radar adopting the OFDM technology has the characteristics of flexible waveform design, high distance resolution, high Doppler resolution, frequency orthogonality, easy frequency diversity realization and the like. The cyclic prefix CP is added in front of the signal, so that the interference caused by multiple targets can be resisted, and the characteristic of nearly zero range sidelobe can be realized in range image reconstruction.
At present, many researches consider the application of OFDM in radar target detection, multi-target tracking and the like. The document "IRCI Free Range Reconstruction for SAR Imaging With the Arbitrary Length OFDM Pulse, IEEE Transactions on Signal Processing,2014,62(18): 4748-. However, modulation of the OFDM signal requires a continuous segment of subcarriers, and occupies a wide spectrum. In practice, due to the existence of multitasking, the spectrum resources are split into fragmented bands, and the spectrum block diagram is shown in fig. 2, making it difficult to be applied to practice. The effective utilization of the fragmented spectrum is realized by applying the OFDM of the spectrum blocks to Communication in the documents of Resource block Filtered-OFDM for future spectral analysis and power efficiency systems, Physical Communication,2014,11:36-55, but the application effectiveness of the OFDM based on the fragmented spectrum in radar detection is not proved by related documents.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provides a radar range profile reconstruction method based on CP-OFDM in a fragment spectrum background, which utilizes the specific frequency band range and the number of subcarriers of the known fragmented spectrum to divide a symbol to be modulated into resource blocks according to the number of subcarriers in the frequency band range, correspondingly modulates the symbol to form a transmitting signal, splices the frequency bands of the resource blocks when demodulating target range information, performs pulse compression processing to obtain a range profile with nearly zero range sidelobe and can meet the basic requirements of a radar communication integrated system.
The purpose of the invention is realized by the following technical scheme: a radar range profile reconstruction method based on CP-OFDM under a fragment spectrum background comprises the following steps:
s1, dividing the resource block, dividing the OFDM signal into a plurality of resource blocks;
s2, obtaining a transmitting signal by modulating the frequency to an available fragment frequency band, and analyzing an echo signal;
and S3, performing pulse compression on the signal obtained in the step S2.
Further, the specific implementation method of step S1 is as follows: let the OFDM signal have N subcarriers, and the complex weighting coefficient of each subcarrier is:
[S0,S1,...SN-1]T (1)
wherein S iskFrequency domain complex weighting coefficient representing k-th subcarrier, k-0, …, N-1 [ ·]TIs a vector transposition operation;
dividing N sub-carriers into W resource blocks according to the frequency spectrum distribution information; respectively carrying out front and back zero padding operation on the divided resource blocks to ensure that each resource block contains N subcarriers;
the subcarrier weighting coefficient of the w-th resource block is expressed as:
Sw＝[Sw0,...,Swk,...Sw(N-1)]T (2)
wherein S iswkIs the complex weighting coefficient of the kth subcarrier in the W-th resource block, W is 0, …, W;
the time domain discrete signal of the w-th resource block is represented as:
Figure GDA0002709037990000021
in order to prevent multipath interference, adding a CP before an OFDM time domain signal results in a time domain sequence:
Figure GDA0002709037990000022
where M is the length of the cyclic prefix, bwnThe first M elements and the last M elements of (a) have the same value.
Further, the specific implementation method of step S2 is as follows: and frequency-modulating the divided resource blocks to available fragment frequency bands to obtain a real transmitting signal sequence as follows:
xwn＝bwn·exp(j2πfwn)n＝0,1,...,N+M-2 (5)
wherein f iswIs the center frequency of the w-th sub-band;
assuming that the scattering coefficient of the target is D ═ D1,d2,...dM-1]After the target reflection, a scattering echo signal sequence is obtained and expressed as the convolution of a sending sequence and a target scattering coefficient; wherein d ismIs the scattering coefficient of the object of the m-th range cell, d m0 represents that the range bin has no target;
the echo sequence is subjected to down-frequency modulation according to the central frequency of the fragment frequency band to obtain an orthogonal frequency division multiplexing signal without frequency band division:
Figure GDA0002709037990000031
wherein u iswnIs a received signal sequence, gwnRepresenting a noise sequence.
Further, the specific implementation method of step S3 is as follows: removing CP from echo signal to resist multi-path interference, and obtaining new signal sequence as follows:
Figure GDA0002709037990000032
expression (7) is expressed in the form of a matrix multiplication:
pw＝Hwb'w+gw (8)
wherein p isw＝[pw(M-1),pwM,...pw(N+M-2)](ii) a Let aw＝[d0ε0,d1ε1,...,dM-1εM-1,0,...,0]T，HwIs awA circulant matrix composed of the elements in (a), wherein the circulant matrix contains a scattering coefficient of the target; b'w＝[bwM-1,bwM,...,bw(N+M-2)]，
Figure GDA0002709037990000033
Equation (8) is expressed as a cyclic convolution of the vector:
Figure GDA0002709037990000034
fourier transform is carried out on two ends of the formula (9) to obtain:
Pwk＝Dwk·Bwk+Gwk (10)
wherein P iswkIs pwFourier transform of (D)wkIs awFourier transform of (B)wkIs bwFourier transform of, i.e.
Figure GDA0002709037990000035
Figure GDA0002709037990000036
Figure GDA0002709037990000041
From formula (10) to obtain DwkThe estimated values of (c) are:
Figure GDA0002709037990000042
superposing the frequency spectrum of the target reflection coefficient estimated value obtained by each resource block, namely
Figure GDA0002709037990000043
To pair
Figure GDA0002709037990000044
IFFT conversion is carried out to obtain the estimated value of the target reflection coefficient
Figure GDA0002709037990000045
Figure GDA0002709037990000046
The invention has the beneficial effects that: the invention divides the symbol to be modulated into one resource block according to the number of subcarriers in the frequency band range by using the specific frequency band range and the number of subcarriers of the known fragmented frequency spectrum, correspondingly modulates to form a transmitting signal, splices the frequency bands of all the resource blocks when demodulating the target distance information, performs pulse compression processing to obtain a distance image with nearly zero distance side lobe, and can meet the basic requirements of a radar communication integrated system.
Drawings
FIG. 1 is a schematic diagram of a radar detecting a target;
FIG. 2 is an OFDM spectrum block diagram;
FIG. 3 is a flow chart of the method of the present invention;
FIG. 4 is a simulation result of range profile reconstruction with different CP lengths in an embodiment of the present invention;
FIG. 5 is a diagram illustrating simulation results of range profile reconstruction under different SNR environments according to an embodiment of the present invention;
fig. 6 is a graph of simulation results comparing a point spread function with a point spread function of a chirp signal in an embodiment of the present invention.
Detailed Description
The invention aims to research a resource block-based orthogonal frequency division multiplexing signal target distance reconstruction algorithm with a cyclic prefix in the background of a fragment frequency spectrum, and solve the problem that the existing CP-OFDM is not suitable for practical application with limited frequency spectrum resources.
The solution of the invention is to divide the symbol to be modulated into resource blocks according to the number of subcarriers in the frequency band range by using the specific frequency band range and the number of subcarriers of the known fragmented frequency spectrum, perform modulation correspondingly to form a transmitting signal, and splice the frequency bands of the resource blocks to perform pulse compression processing when demodulating the target distance information to obtain a distance image with nearly zero distance side lobe. The technical scheme of the invention is further explained by combining the attached drawings.
As shown in fig. 3, a method for reconstructing a radar range profile based on CP-OFDM in a background of a fragmented spectrum of the present invention includes the following steps:
s1, dividing the resource block, dividing the OFDM signal into a plurality of resource blocks; the specific implementation method comprises the following steps: let the OFDM signal have N sub-carriers, each sub-carrier having a complex weighting coefficient of
[S0,S1,...SN-1]T (1)
Wherein S iskFrequency domain complex weighting coefficient representing k-th subcarrier, k-0, …, N-1 [ ·]TIs a vector transposition operation;
dividing N sub-carriers into W resource blocks according to the frequency spectrum distribution information; respectively carrying out front and back zero padding operation on the divided resource blocks to ensure that each resource block contains N subcarriers;
the subcarrier weighting coefficient of the w-th resource block is expressed as:
Sw＝[Sw0,...,Swk,...Sw(N-1)]T (2)
wherein S iswkIs the complex weighting coefficient of the kth subcarrier in the W-th resource block, W is 0, …, W;
the time domain discrete signal of the w-th resource block is represented as:
Figure GDA0002709037990000051
in order to prevent multipath interference, adding a CP before an OFDM time domain signal results in a time domain sequence:
Figure GDA0002709037990000052
where M is the length of the cyclic prefix, bwnThe first M elements and the last M elements of (a) have the same value.
S2, obtaining a transmitting signal by modulating the frequency to an available fragment frequency band, and analyzing an echo signal; the echo of a simulation transmitted signal detection target is realized by adopting a target scattering coefficient value weighting transmitted signal and delay shift of a discrete signal, sequence delay is carried out zero filling before a sequence according to the position of the target, reflected signals of all targets are superposed to obtain reflected signals of all targets, namely, signals received by a radar receiver, after the signal of each module is subjected to respective frequency down-regulation according to central frequency, the length of front and back two sections of CP is removed to obtain the echo signal of a w-th module containing all target information, and simultaneously, noise simulation is superposed on the signal in an actual application scene;
the specific implementation method comprises the following steps: and frequency-modulating the divided resource blocks to available fragment frequency bands to obtain a real transmitting signal sequence as follows:
xwn＝bwn·exp(j2πfwn)n＝0,1,...,N+M-2 (5)
wherein f iswIs the center frequency of the w-th sub-band;
assuming that the scattering coefficient of the target is D ═ D1,d2,...dM-1]After the target reflection, a scattering echo signal sequence is obtained and expressed as the convolution of a sending sequence and a target scattering coefficient; wherein d ismIs the scattering coefficient of the object of the m-th range cell, d m0 represents that the range bin has no target;
the echo sequence is subjected to down-frequency modulation according to the central frequency of the fragment frequency band to obtain an orthogonal frequency division multiplexing signal without frequency band division:
Figure GDA0002709037990000061
wherein u iswnIs a received signal sequence, gwnRepresenting a noise sequence.
S3, performing pulse compression on the signal obtained in the step S2; the specific implementation method comprises the following steps: removing CP from echo signal to resist multi-path interference, and obtaining new signal sequence as follows:
Figure GDA0002709037990000062
expression (7) is expressed in the form of a matrix multiplication:
pw＝Hwb'w+gw (8)
wherein p isw＝[pw(M-1),pwM,...pw(N+M-2)](ii) a Let aw＝[d0ε0,d1ε1,...,dM-1εM-1,0,...,0]T，HwIs awA circulant matrix composed of the elements in (a), wherein the circulant matrix contains a scattering coefficient of the target; b'w＝[bwM-1,bwM,...,bw(N+M-2)]，
Figure GDA0002709037990000063
Equation (8) is expressed as a cyclic convolution of the vector:
Figure GDA0002709037990000064
fourier transform is carried out on two ends of the formula (9) to obtain:
Pwk＝Dwk·Bwk+Gwk (10)
wherein P iswkIs pwFourier transform of (D)wkIs awFourier transform of (B)wkIs bwFourier transform of, i.e.
Figure GDA0002709037990000065
Figure GDA0002709037990000066
Figure GDA0002709037990000067
Figure GDA0002709037990000071
From formula (10) to obtain DwkThe estimated values of (c) are:
Figure GDA0002709037990000072
superposing the frequency spectrum of the target reflection coefficient estimated value obtained by each resource block, namely
Figure GDA0002709037990000073
To pair
Figure GDA0002709037990000074
IFFT conversion is carried out to obtain the estimated value of the target reflection coefficient
Figure GDA0002709037990000075
Figure GDA0002709037990000076
The reconstruction method of the present invention is further verified by simulations below, all steps, conclusions verified on MatlabR2016 a.
Simulation scene: assuming that the maximum value M of the number of distance resolution units is 100, the number of subcarriers of an OFDM signal is 256, the number of resource blocks is 2, each of the OFDM signal and the resource blocks includes 128 subcarriers, and the signal bandwidth is B200 MHz.
Fig. 4 shows the distance image recovery results for different CP lengths, where CP is set to 90 and 99, respectively, and simulation results of (a) and (b) are obtained. As can be seen from the figure, if CP is 99, that is, if CP is long enough, the range can be recovered without distortion like in the case of no noise, and the side lobe level can reach-130 dB, once the CP length is reduced; when CP is 90, the range side lobe level is raised to 5-10dB by the interference from the multipath, and the weak target is difficult to recover.
Fig. 5(a) - (h) show the distance image reconstruction comparison of the RB-CP-OFDM and the linear frequency modulation signal (LFM) under different signal-to-noise ratios, which clearly shows that the reconstruction performance of the RB-CP-OFDM signal is better than that of the LFM signal, and the reconstruction performance of the LFM is not easily affected by noise due to its self-correlation property, and although the signal-to-noise ratio is high enough, a weak target still suffers from the interference of a strong target. And RB-CP-OFDM can still recover the range image of the target even under the condition of lower signal-to-noise ratio.
Fig. 6 shows the RB-CP-OFDM signal and the LFM signal point spread function, wherein the upper curve is the LFM signal point spread function and the lower curve is the RB-CP-OFDM signal point spread function. Comparing the distance side lobe of the two, proves that the RB-CP-OFDM with the sufficient CP can obtain lower distance side lobe and obtain greater advantage in the radar multi-target detection.
According to the specific implementation mode of the invention, the radar signal detection algorithm can meet the basic requirements of a radar communication integrated system.
It will be appreciated by those of ordinary skill in the art that the embodiments described herein are intended to assist the reader in understanding the principles of the invention and are to be construed as being without limitation to such specifically recited embodiments and examples. Those skilled in the art can make various other specific changes and combinations based on the teachings of the present invention without departing from the spirit of the invention, and these changes and combinations are within the scope of the invention.

Claims (2)

1. A radar range profile reconstruction method based on CP-OFDM under a fragment spectrum background is characterized by comprising the following steps:
s1, dividing the resource block, dividing the OFDM signal into a plurality of resource blocks; the specific implementation method comprises the following steps: let the OFDM signal have N subcarriers, and the complex weighting coefficient of each subcarrier is:
[S0,S1,...SN-1]T (1)
wherein S iskFrequency domain complex weighting coefficient representing k-th subcarrier, k-0, …, N-1 [ ·]TIs a vector transposition operation;
dividing N sub-carriers into W resource blocks according to the frequency spectrum distribution information; respectively carrying out front and back zero padding operation on the divided resource blocks to ensure that each resource block contains N subcarriers;
the subcarrier weighting coefficient of the w-th resource block is expressed as:
Sw＝[Sw0,...,Swk,...Sw(N-1)]T (2)
wherein S iswkA complex weighting coefficient of a kth subcarrier in a W-th resource block, wherein W is 0.
The time domain discrete signal of the w-th resource block is represented as:
Figure FDA0002941309540000011
in order to prevent multipath interference, adding a CP before an OFDM time domain signal results in a time domain sequence:
Figure FDA0002941309540000012
where M is the length of the cyclic prefix, bwnThe first M elements and the last M elements have the same value;
s2, obtaining a transmitting signal by modulating the frequency to an available fragment frequency band, and analyzing an echo signal; the specific implementation method comprises the following steps: and frequency-modulating the divided resource blocks to available fragment frequency bands to obtain a real transmitting signal sequence as follows:
xwn＝bwn·exp(j2πfwn) n＝0,1,...,N+M-2 (5)
wherein f iswIs the center frequency of the w-th sub-band;
assuming that the scattering coefficient of the target is D ═ D1,d2,...dM-1]After the target reflection, a scattering echo signal sequence is obtained and expressed as the convolution of a sending sequence and a target scattering coefficient; wherein d ismIs the target scattering coefficient of the mth range bin, M is 1,2 … M-1, dm0 represents that the range bin has no target;
the echo sequence is subjected to down-frequency modulation according to the central frequency of the fragment frequency band to obtain an orthogonal frequency division multiplexing signal without frequency band division:
Figure FDA0002941309540000021
wherein u iswnIs a received signal sequence, gwnRepresenting a noise sequence;
and S3, performing pulse compression on the signal obtained in the step S2.
2. The method for reconstructing radar range profile based on CP-OFDM in the background of fragmented spectrum according to claim 1, wherein the step S3 is implemented by: removing CP from echo signal to resist multi-path interference, and obtaining new signal sequence as follows:
Figure FDA0002941309540000022
expression (7) is expressed in the form of a matrix multiplication:
pw＝Hwb'w+gw (8)
wherein p isw＝[pw(M-1),pwM,...pw(N+M-2)](ii) a Let aw＝[d0ε0,d1ε1,...,dM-1εM-1,0,...,0]T，HwIs awThe cyclic matrix is composed of elements including scattering of the targetA coefficient; b'w＝[bwM-1,bwM,...,bw(N+M-2)]，
Figure FDA0002941309540000023
Equation (8) is expressed as a cyclic convolution of the vector:
Figure FDA0002941309540000024
fourier transform is carried out on two ends of the formula (9) to obtain:
Pwk＝Dwk·Bwk+Gwk (10)
wherein P iswkIs pwFourier transform of (D)wkIs awFourier transform of (B)wkIs bwFourier transform of, i.e.
Figure FDA0002941309540000025
Figure FDA0002941309540000026
Figure FDA0002941309540000031
Figure FDA0002941309540000032
From formula (10) to obtain DwkThe estimated values of (c) are:
Figure FDA0002941309540000033
superposing the frequency spectrum of the target reflection coefficient estimated value obtained by each resource block, namely
Figure FDA0002941309540000034
To pair
Figure FDA0002941309540000035
IFFT conversion is carried out to obtain the estimated value of the target reflection coefficient
Figure FDA0002941309540000036
Figure FDA0002941309540000037
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