CN109856650A - Code phase measuring method based on phase fringes - Google Patents
Code phase measuring method based on phase fringes Download PDFInfo
- Publication number
- CN109856650A CN109856650A CN201910035970.8A CN201910035970A CN109856650A CN 109856650 A CN109856650 A CN 109856650A CN 201910035970 A CN201910035970 A CN 201910035970A CN 109856650 A CN109856650 A CN 109856650A
- Authority
- CN
- China
- Prior art keywords
- input signal
- phase
- local
- signal
- fringes
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Landscapes
- Position Fixing By Use Of Radio Waves (AREA)
Abstract
The code phase measuring method based on phase fringes that the invention discloses a kind of, comprising: the intermediate-freuqncy signal and track loop for choosing receiver radio frequency front end down coversion enter the local replica carrier wave after tenacious tracking state and local copy codes；Carrier wave and Doppler frequency shift are filtered out to the intermediate-freuqncy signal and local replica carrier wave, obtain receiving input signal；Using local copy codes as local input signal；The Crosspower spectrum phase for receiving input signal and local input signal is calculated, phase fringes are generated；Fringe frequency is sought from phase fringes, the interval time delay for receiving input signal and local input signal is obtained, to obtain code phase measuring value.
Description
Technical field
The present invention relates to field of satellite location, in particular to a kind of code phase measuring method based on phase fringes.
Background technique
Global position system is a kind of technology that object is accurately positioned using satellite, can be used to vector aircraft,
Ship, vehicle and individual arrive punctually at the destination safely and accurately along selected route.Since the U.S. is from last century 70
Since age is successfully established global positioning system (Global Positioning System, GPS), Europe, Russia, China
Have launched the global position system of oneself, such as Galileo, Beidou.But GPS is still defending of being most widely used at present
Star positioning system.
GPS receiver mainly completes the tracking of navigation signal by carrier wave ring and code ring, track loop duplication
The carrier wave synchronous with satellite-signal and pseudo-code out obtain the data of navigation message to realize carrier wave removing and signal despreading
Code.While tracking signal, receiver according to duplication carrier signal gain of parameter satellite-signal Doppler frequency shift and load
Wave phase measured value, and according to the code phase and code pseudo-range measurements of the gain of parameter of the duplication pseudo-code satellite-signal.
Wherein, code tracking loop is usually to realize in the form of delay locked loop (Delay Locked Loop, DLL),
By copying the pseudo noise code of three parts of outs of phase, it is referred to as advanced (Early), immediately (Prompt) and lag (Late)
Replica code estimates i.e. time-code and receives the phase difference between code using the good autocorrelation performance of pseudo-code.On the one hand it obtains
On the other hand code phase measuring value inputs to pseudo-code digital controlled oscillator (NCO) simultaneously, constantly regulate what pseudo-code generator copied
Pseudo-code phase makes to replicate pseudo-code and receives the holding alignment of pseudo-code moment.Code phase measuring value can be used for assembling signal transmitting
Time, and then obtain a yard pseudo-range measurements.In the case where not considering the receivers external error source such as multipath and atmosphere delay,
A C/A code chip of GPS is 293 meters long, and code pseudorange measurement accuracy is that the code phase measuring value that the code ring of 1% chip exports includes
About 3 meters of error.
Code phase measuring error is much smaller than by the carrier phase measurement error of carrier wave ring output, can be as accurate as 1% carrier wave
Wavelength i.e. 1.9 millimeter.Compared with carrier-phase measurement, although the pseudo-range measurements precision that code phase is assembled into is lower,
There is no the problem of fuzziness, pseudo-range measurements can be obtained relatively simplely, is brought conveniently to practical application.Therefore, it is keeping away
Exempt from the case where calculating integer ambiguity, improve code pseudorange measurement accuracy, more accurate rapid survey result and more can be provided
It assists well obtaining carrier-phase measurement.
High-precision code pseudo-range measurements in order to obtain, domestic and foreign scholars, which study, improves code tracking loop using different methods
Precision.In " the town Luo Liu of bibliography 1；The technical research of high-precision satellite ranging and realization [D], Nanjing: Institutes Of Technology Of Nanjing,
In 2016:37-43 ", author proposes the loop architectures of the estimated value auxiliary pseudo-code ring using carrier doppler；In bibliography
2 " Liu Mengchao, Zhao Bingfeng；GNSS receiver adaptive bandwidth pseudo-code tracing loop designs [J]；Radio communication technology, 2017,
43 (4): 64-66, in 79 ", author proposes a kind of code tracking loop design scheme of adaptive bandwidth, is filtered by real-time adjustment loop
Wave device bandwidth promotes code tracking loop performance；Bibliography 3 " Deng Zhongliang, Zhao Yang, Yin Lu, etc.；A kind of raising pseudorange measurement accuracy
Technique study [C] // 6th China Satecom navigation Annual Conference collection of thesis；Beijing: China Satecom's navigation system management office
Academic exchange center in 2015:4 ", is transformed code tracking loop using compensating iterative thought, and improves and improve pseudorange
Measurement method；In bibliography 4 " Gong Guohui, Li Sikun；Improve 3 quadratic interpolations of DSSS signal PN code phase measuring precision
Method [J]；Communicate journal, 2007 (02): in 130-133 ", propose using 3 quadratic interpolattion process correlation spectrum peak datas with
Code phase measuring precision under low sampling rate is improved, and is compared with two o'clock, 3 linear interpolations；In 5 " sieve of bibliography
Naval, Peng Weidong, Li Mingyang, etc.；Pseudo-random code phases mensuration [J] based on sectional straight line fitting；Computer measurement and control
System；2015,23 (3): in 733 ", it is quasi- to do least square to relevant peaks two sides using correlation peak point as separation respectively by 727-729
It closes, using the difference of the abscissa of two straight-line intersections and zero skew reference value as the valuation of code phase, obtains more same than least square
Footwork and the more stable and accurate valuation result of 3 quadratic interpolattions；In bibliography 6 " Hu Xiulin, Zhang Jun, Yang Ling；Directly
Accurate measurement method [J] telecom technology of PN code phase in sequence spread spectrum system is connect, 2005,45 (3): in 128-131 ",
It is proposed that least square improves code phase measuring precision；In bibliography 7, " Zhang Bo, Guo Ying, Qi Zisen wait .PN code phase accurately to survey
Cumulative least square method [J] the BJ University of Aeronautics & Astronautics journal of amount, 2016,42 (10): in 2265-2270 ", in reference text
On the basis of offering 6, a kind of realization structure of cumulative least square method is given, keeps the scope of application of least square method wider, essence
Du Genggao.
Although domestic and foreign scholars give a variety of methods for improving code tracking loop precision in the above referred-to references, more than
Method is all to need two-way or more multichannel replica code signal to carry out related based on the correlation function of two signals and relevant peaks
It calculates, has some limitations.
There is also the same problems in other global position systems such as Galileo, Beidou.
Summary of the invention
It is an object of the invention to overcome code tracking loop method for improving accuracy in the prior art to need answering for two-way or more
Limitation caused by code signal processed, to provide a kind of code phase measuring method without more than two-way replicating code signal.
To achieve the goals above, the code phase measuring method based on phase fringes that the present invention provides a kind of, comprising:
Step 1), the intermediate-freuqncy signal for choosing receiver radio frequency front end down coversion and track loop enter tenacious tracking shape
Local replica carrier wave and local copy codes after state；
Step 2) filters out carrier wave and Doppler frequency shift to the intermediate-freuqncy signal and local replica carrier wave, obtains receiving input
Signal；Using local copy codes as local input signal；
Step 3) calculates the Crosspower spectrum phase for receiving input signal and local input signal, generates phase fringes；
Step 4) seeks fringe frequency from phase fringes, obtains the reception input signal and local input signal
It is spaced time delay, to obtain code phase measuring value.
It further include the step that delay compensation is done to local input signal between step 2) and step 3) in above-mentioned technical proposal
It suddenly and in the step 4) further include to receive the time delay that the interval time delay of input signal and local input signal subtracts compensation
The operation of amount.
In above-mentioned technical proposal, the delay compensation the step of after further include: for the reception input signal and
Time domain folding is done by the local input signal of delay compensation, obtains the reception input signal of high s/n ratio and the sheet of high s/n ratio
Ground input signal；
And it is described 3) in, calculate the reception input signal of the high s/n ratio and the local input signal of high s/n ratio
Crosspower spectrum phase, to obtain phase fringes.
In above-mentioned technical proposal, between step 2) and step 3) further include: for the reception input signal and described
Local input signal does time domain folding, obtains the reception input signal of high s/n ratio and the local input signal of high s/n ratio；
And it is described 3) in, calculate the reception input signal of the high s/n ratio and the local input signal of high s/n ratio
Crosspower spectrum phase, to obtain phase fringes.
In above-mentioned technical proposal, the time domain folding includes:
Input signal, local input signal will be received or be divided into n sections respectively by the local input signal of delay compensation；
Every segment data superposition summation of input signal will be received, obtains the reception input signal of high s/n ratio；It will be local defeated
The every segment data superposition summation for entering signal or the local input signal by delay compensation, obtains the local input letter of high s/n ratio
Number.
In above-mentioned technical proposal, the step 3) is specifically included:
If signal is f all the way1(t), another way signal is f2(t), Fourier transform is carried out to this two paths of signals respectively, is obtained
It arrives
The then cross-spectral density of two paths of signals are as follows:
Wherein, * indicates complex conjugate；
Power spectrum phase is plural number S12The argument main value of (ω):
φ (ω)=arg [S12(ω)]；
Wherein, the signal all the way is the reception input signal for receiving input signal or high s/n ratio；The another way letter
Number be local input signal, by delay compensation local input signal or high s/n ratio local input signal.
In above-mentioned technical proposal, in step 4), Fourier transformation is done to phase fringes to seek fringe frequency.
The present invention also provides a kind of code phase measuring device based on phase fringes, comprising:
Signal receives and chooses module, for choosing the intermediate-freuqncy signal of receiver radio frequency front end down coversion, and tracking ring
Road enters the local replica carrier wave after tenacious tracking state and local copy codes；
Filtering and Doppler frequency shift module, for filtering out carrier wave and Doppler to the intermediate-freuqncy signal and local replica carrier wave
Frequency displacement obtains receiving input signal；Using local copy codes as local input signal；
Crosspower spectrum phase computing module, for calculating the crosspower spectrum phase for receiving input signal and local input signal
Position generates phase fringes；
Fringe frequency seeks module, for seeking fringe frequency from phase fringes, obtain the reception input signal with
The interval time delay of local input signal.
It further include delay compensation module and deletion delay compensation amount module in above-mentioned technical proposal；Wherein,
Signal is received the local input signal exported with selection module and does delay compensation by the delay compensation module；
The deletion delay compensation amount module is used to seek fringe frequency the reception input signal that module is exported and this
The interval time delay of ground input signal subtracts the delay volume of compensation.
It further include that time domain folds module, which is used to be the reception input signal and warp in above-mentioned technical proposal
The local input signal for crossing delay compensation does time domain folding, obtains reception input signal and the local of high s/n ratio of high s/n ratio
Input signal；
And in Crosspower spectrum phase computing module, the reception input signal and high s/n ratio of the high s/n ratio are calculated
Local input signal Crosspower spectrum phase, to obtain phase fringes.
The present invention has the advantages that
Compared with traditional track loop, when method of the invention increases the calculation amount and calculating of receiver processor on a small quantity
Between, the problem of significantly improving the measurement accuracy of yard pseudorange, and integer ambiguity be not present.In the practical application of receiver,
High-precision code pseudo-range measurements can be provided with lower cost frequency, be widely used value.Also can simultaneously
Certain reference role is provided for precision distance measurement and positioning.
Detailed description of the invention
Fig. 1 is the identical signal Crosspower spectrum phase bar graph of two-way for postponing 1 second；
Fig. 2 is the structural schematic diagram of exemplary receiver code tracking loop；
Fig. 3 is the flow chart of phase fringes method of the invention；
Fig. 4 is the schematic diagram that time domain folds；
Fig. 5 is the schematic diagram of the intermediate-freuqncy signal inputted in an emulation experiment；
Fig. 6 is intermediate-freuqncy signal shown in Fig. 5 in the folded schematic diagram of time domain；
Fig. 7 is the cross-correlation power spectrum phase figure of the signal and local code signal in Fig. 6；
Fig. 8 is when extracting fringe frequency using Fourier transform, after carrying out Fourier transform again to the data of Fig. 7
The schematic diagram of power spectral amplitude；
Fig. 9 is code phase measuring error comparison diagram.
Specific embodiment
Before elaborating to method of the invention, the principle of phase fringes method is illustrated first.
Phase fringes method in Radar Technology is usually used in measuring same signal reaches pairwise correlation receiver after reflection
Time delays.Two paths of signals is denoted as f respectively1(t) and f2(t), wherein f2(t)=f1(t- τ), τ are that signal reaches two receivers
Time delay.Cross-correlation calculation is carried out to two paths of signals, ifThenSo, two-way is believed
Number cross-spectral density are as follows:
Wherein R12It (t) is f1(t) and f2(t) cross-correlation function.Therefore, the phase of cross-spectral density are as follows:
The π τ f of φ=ω τ=2 (2)
By formula (2) it is found that there are lines with frequency f for the phase of two paths of signals crosspower spectrum in the case that delay, τ is certain
Sexual intercourse, and slope is only related with signal time delay τ.In view of calculated cross-spectral density phase value range be [-
π, π], so φ~f straight line is cut into periodic striped, with reference to Fig. 1, every stripe slope is 2 π τ, fringe spacing in figure
T0Are as follows:
Fringe frequency f0(i.e. every 1Hz frequency band intra-striate number) are as follows:
Therefore, by counting the frequency of occurrences of phase fringes, the time delay of signal can be measured.
Use for reference Radar Technology in phase fringes method principle, in the gps receiver, can by received satellite-signal with
The pseudo-code signal that local NCO is generated is considered as the two-way coherent signal there are time delay to be measured, and the time delay measured is that code phase is surveyed
Magnitude can be used for assembling a yard pseudorange.Fig. 2 is the structural schematic diagram of exemplary receiver code tracking loop, is indicated in the figure
The position of phase fringes method of the invention in receiver code track loop.As shown, satellite-signal is through under radio-frequency front-end
After frequency conversion, into track loop；After track loop enters tenacious tracking state, using the signal of I branch frequency mixer output
(having eliminated carrier phase error and Doppler frequency shift) calculates cross-correlation with the instant branch pseudo noise code that pseudo-code NCO is generated
Power spectral density, the phase fringes frequency occurred by statistics, can be obtained code phase measuring value.
With reference to Fig. 3, in a preferred embodiment, phase fringes method of the invention the following steps are included:
Step 1), the intermediate frequency satellite-signal (hereinafter referred to as intermediate-freuqncy signal) for choosing receiver radio frequency front end down coversion, and
Track loop enters the local replica carrier wave after tenacious tracking state and local copy codes；
Intermediate-freuqncy signal and local replica carrier wave are passed through frequency mixer by step 2), are filtered out carrier wave and Doppler frequency shift, are connect
Receive input signal f1(t)；
Step 3), local copy codes are as local input signal f2(t)；
Step 4) does delay compensation to the obtained local input signal of step 3), obtains f2(t-τ0), wherein τ0It indicates
The delay volume of compensation；
Step 5), the reception input signal f for obtaining step 2)1(t) sheet by delay compensation obtained with step 4)
Ground input signal does time domain folding, obtains the reception input signal f of high s/n ratio1The local input signal of ' (t) and high s/n ratio
f2′(t-τ0), and keep the correlation of two paths of signals；
Step 6) calculates the Crosspower spectrum phase for passing through the folded two paths of signals of time domain, generates phase fringes；
Step 7) does Fourier transformation to phase fringes, obtains quadratic transformation amplitude spectrum | Φ (ψ) | the corresponding item of maximum value
Line frequency has also just obtained the interval time delay (τ+τ of two signals0)。
Yanzhong subtracts the delay volume of compensation when step 8), the interval obtained from step 7), can be obtained and compares delay lock loop
The code phase measuring value τ of higher precision.
In preferred embodiment above-mentioned, delay compensation is done to local input signal in step 4), in step 8)
Delay compensation value has been subtracted again.The purpose done so is to improve frequency band intra-striate quantity, more accurate so as to extract
Fringe frequency.Its principle are as follows: after receiver enters tenacious tracking state, the pseudo noise code that local code NCO is generated is had already passed through
The adjustment of delay lock loop is much smaller than chip lengths with the time delay received between signal；According to formula above-mentioned (4),
Fringe frequency f0Directly proportional to delay, τ, delay, τ is bigger, and striped quantity is more；And more fringe numbers to adopt in step 7)
The result of striped is extracted closer to theoretical value with Fourier transform.Therefore, increase local input signal and receive input signal
Between time delay, it will help extract more accurate fringe frequency.
When doing delay compensation to local input signal, the delay volume τ of compensation0It should be a set time, and τ0> > τ.
In aforementioned preferred embodiments, method of the invention has done delay compensation to local input signal.In other implementations
In example, method of the invention can not also do delay compensation to local input signal, that is, save the behaviour in step 4) and step 8)
Make.If not doing delay compensation to local input signal, method of the invention directly obtains step 2) when doing time domain folding
Receive input signal f1(t) local input signal obtained with step 3) does time domain folding；In step 7) in obtained Fu
Leaf transformation result is exactly the required code phase measuring value τ taken.
In aforementioned preferred embodiments, time domain folding has been done respectively to two paths of signals in step 5).The time domain folds
Purpose be to improve signal-to-noise ratio to effectively reduce noise power.Those skilled in the art's discovery: include in reception signal makes an uproar
Sound can cause a degree of influence to the extraction of fringe frequency；When GPS satellite is in zenith direction (90 ° of the elevation angle), signal
It is handled by radio-frequency front-end, into after track loop, noise bandwidth is the bandwidth 2.046MHz of C/A code signal, at this time signal-to-noise ratio
It (SNR) is about -16.5dB；And when satellite is in the low elevation angle (5 °), intermediate-freuqncy signal signal-to-noise ratio is about -24.5dB.It is lower
Signal-to-noise ratio phase fringes are submerged among noise, to extract fringe frequency bring very big difficulty.For this purpose, in the present invention
In, signal-to-noise ratio is improved by doing time domain folding respectively to two paths of signals.
The concrete operations that the time domain folds include:
First, it is assumed that two paths of signals uses f respectively1(t) and f2(t) it indicates, as shown in figure 4, by the data of two paths of signals point
It is not divided into n sections uniform, is expressed as f11(t),f12(t)……f1n(t) and f21(t),f22(t)……f2n(t)。
Then, every segment data is superimposed and is summed, obtain the folded signal data f ' of time domain1(t) and f '2(t) as follows:
In known GPS signal, the numeric data code code length of navigation message is 20ms, and PN-code capture is only 1ms.Namely in 20ms
It is interior, influence of the navigation message to pseudo-code phase can be ignored.With this condition, to receive signal carry out every section of 1ms duration when
Domain folds, and can effectively reduce noise power, improves signal-to-noise ratio.When folding number of segment is 10 sections, signal-to-noise ratio will improve about 10dB.
The two paths of signals f ' after improving signal-to-noise ratio is folded through time domain1(t) and f '2(t) crosspower spectrum phase is calculated again in the next steps
Position, can be obtained relatively clear phase fringes.
In aforementioned preferred embodiments, method of the invention has all done time domain folding to two paths of signals.In other embodiments
In, method of the invention can also save the step of time domain folds, then calculating the crosspower spectrum phase of two paths of signals in step 6)
When position, the Crosspower spectrum phase of the two paths of signals folded without time domain need to be calculated.
In step 6), the specific steps for calculating the power spectrum phase of two paths of signals include:
If reception input signal is f1(t), local input signal f2(t), Fourier change is carried out respectively to this two paths of signals
It changes, obtains
The then cross-spectral density of two paths of signals are as follows:
Wherein, * indicates complex conjugate；
Power spectrum phase is plural number S12The argument main value of (ω):
φ (ω)=arg [S12(ω)] (7)
It will be understood by those skilled in the art that if receiving the variation of input signal, the expression formula of local input signal, as before
It states and uses f in preferred embodiment1' (t) indicates the reception input signal of high s/n ratio, uses f2′(t-τ0) indicate high s/n ratio local
Input signal has no effect on the calculating process of power spectrum phase, as long as the relevant parameter in above-mentioned formula is subject to substitution.
In aforementioned preferred embodiments, in step 7), Fourier transformation is done to phase fringes to seek fringe frequency.It is false
If phase fringes are indicated with φ (f), when fringe frequency is f0When, fringe spacing T0=1/f0, single striped φ1(f) it can indicate
Are as follows:
Fourier transform is carried out to formula (8), obtains the amplitude spectrum of single striped are as follows:
When striped is with T0For period, when repeating, the Fourier transform amplitude spectrum of periodic a plurality of phase fringes are as follows:
By formula (10) it is found that the Crosspower spectrum phase striped φ (f) of two signals obtains width after Fourier transform again
Degree spectrum | Φ (ψ) |, as n=1, | Φ (ψ) | functional value be maximum value, the at this time π of ψ=2 f0, i.e., Φ~Amplitude is most in figure
The corresponding frequency of big value is the fringe frequency f in formula (4)0。
In aforementioned preferred embodiments, fringe frequency, in other embodiments, this field are sought using Fourier transformation
Other methods can also be used to seek fringe frequency, such as line fitting approach in technical staff.
In order to prove the effect of the method for the present invention, applicant carries out emulation in fact to above method using MATLAB software programming
It tests, simulation parameter is as shown in table 1.Intermediate-freuqncy signal, local load by software programming, after simulation generation satellite-signal down coversion
Wave signal and code signal.After the step described in the aforementioned preferred embodiments, simulation result is as shown in Fig. 5~Fig. 8.
Fig. 5 is the intermediate-freuqncy signal that simulation enters track loop after radio-frequency front-end processing, and useful signal is complete
It is submerged in noise；Fig. 6 is intermediate-freuqncy signal by being mixed with local carrier signal, and carries out the folded signal of time domain, can be with
It was found that noise amplitude is obviously reduced, Signal-to-Noise is effectively raised.
Fig. 7 is the cross-correlation power spectrum phase figure of the signal and local code signal in Fig. 6, and low-frequency range has apparent oblique stripe
The striped of line, high band is submerged in noise.The data point that part concentrates on 0 phase is that crosspower spectrum amplitude is lesser
Data are set as 0 phase since the rounding error of MATLAB software causes great phase deviation in order to prevent.Fig. 8 is to adopt
When extracting fringe frequency with Fourier transform, the power spectral amplitude after Fourier transform again is carried out to the data of Fig. 7, it is maximum
Value respective frequencies are to measure time delay.This result is subtracted into the compensation time, code phase measuring value can be obtained
Using procedure above, for different state of signal-to-noise, 1000 Monte-Carlo Simulations are carried out respectively and are simulated, and with
The measurement error of delay lock loop compares under same case.In the common three kinds of code phase discriminator algorithms of delay lock loop, phase
Than subtract before incoherent rear amplitude method and it is incoherent before subtract rear power method, the operand for the dot product power method that is concerned with is smaller, and obtains
Code phase measuring value it is the most accurate.It chooses and is compared using the delay lock loop of relevant dot product power method phase discriminator herein,
Its code phase measuring error mean square difference is calculated by following formula:
In formula: c is the light velocity, TcIt is wide for pseudo-code code, value hereinD is correlator spacing before and after code ring, according to mesh
The correlator spacing that preceding major part receiver manufacturer uses, value is 0.1 chip herein；T is signal length, i.e. 10ms；C/
N0For signal carrier-to-noise ratio, unit dB/Hz.Comparing result is as shown in Figure 9.
According to above the simulation experiment result, can be concluded that
(1) when satellite is in zenith direction, and snr of received signal is -15dB, code phase measuring precision be can achieve
0.39 meter, the 0.13% of about one chip width (293 meters), it is improved about than 1.82 meters of delay lock loop measurement accuracy
79%.
(2) with the decline of signal-to-noise ratio, measurement error can be gradually increased.And when satellite is in the low elevation angle (about 5 °), letter
It makes an uproar than falling to approximately -25dB, measurement error increases to 4.35 meters, is the 1.5% of chip width, but still measures than delay lock loop
5.76 meters of precision are improved about 24%.
(3) compared with traditional track loop, method of the invention increases the calculation amount and meter of receiver processor on a small quantity
The problem of evaluation time significantly improves the measurement accuracy of yard pseudorange, and there is no integer ambiguities.In the practical application of receiver
In, high-precision code pseudo-range measurements can be provided with lower cost frequency, be widely used value.Simultaneously
Certain reference role can be provided for precision distance measurement and positioning.
In above multiple embodiments, the realization process of the method for the present invention is described by taking GPS as an example.But in view of
There is also the same problems for other kinds of satellite navigation system, and those skilled in the art is it is to be appreciated that method of the invention
It is equally applicable in these satellite navigation systems.
The present invention also provides a kind of code phase measuring devices based on phase fringes of virtualization, comprising:
Signal receives and chooses module, for choosing the intermediate-freuqncy signal of receiver radio frequency front end down coversion, and tracking ring
Road enters the local replica carrier wave after tenacious tracking state and local copy codes；
Filtering and Doppler frequency shift module, for filtering out carrier wave and Doppler to the intermediate-freuqncy signal and local replica carrier wave
Frequency displacement obtains receiving input signal；Using local copy codes as local input signal；
Crosspower spectrum phase computing module, for calculating the crosspower spectrum phase for receiving input signal and local input signal
Position generates phase fringes；
Fringe frequency seeks module, for seeking fringe frequency from phase fringes, obtain the reception input signal with
The interval time delay of local input signal.
The measuring device further includes delay compensation module and deletion delay compensation amount module；Wherein,
Signal is received the local input signal exported with selection module and does delay compensation by the delay compensation module；
The deletion delay compensation amount module is used to seek fringe frequency the reception input signal that module is exported and this
The interval time delay of ground input signal subtracts the delay volume of compensation.
The measuring device further includes that time domain folds module, which is used for as the reception input signal and passes through time delay
The local input signal of compensation does time domain folding, obtains the reception input signal of high s/n ratio and the local input letter of high s/n ratio
Number；
And in Crosspower spectrum phase computing module, the reception input signal and high s/n ratio of the high s/n ratio are calculated
Local input signal Crosspower spectrum phase, to obtain phase fringes.
It should be noted last that the above examples are only used to illustrate the technical scheme of the present invention and are not limiting.Although ginseng
It is described the invention in detail according to embodiment, those skilled in the art should understand that, to technical side of the invention
Case is modified or replaced equivalently, and without departure from the spirit and scope of technical solution of the present invention, should all be covered in the present invention
Scope of the claims in.
Claims (10)
1. a kind of code phase measuring method based on phase fringes, comprising:
After step 1), the intermediate-freuqncy signal for choosing receiver radio frequency front end down coversion and track loop enter tenacious tracking state
Local replica carrier wave and local copy codes；
Step 2) filters out carrier wave and Doppler frequency shift to the intermediate-freuqncy signal and local replica carrier wave, obtains receiving input signal；
Using local copy codes as local input signal；
Step 3) calculates the Crosspower spectrum phase for receiving input signal and local input signal, generates phase fringes；
Step 4) seeks fringe frequency from phase fringes, obtains the interval for receiving input signal and local input signal
Time delay, to obtain code phase measuring value.
2. the code phase measuring method according to claim 1 based on phase fringes, which is characterized in that in step 2) and step
It is rapid 3) between further include the steps that doing local input signal in delay compensation and the step 4) further include for receive input
The interval time delay of signal and local input signal subtracts the operation of the delay volume of compensation.
3. the code phase measuring method according to claim 2 based on phase fringes, which is characterized in that mended in the time delay
After the step of repaying further include: do time domain folding for the reception input signal and by the local input signal of delay compensation
It is folded, obtain the reception input signal of high s/n ratio and the local input signal of high s/n ratio；
And it is described 3) in, calculate the mutual of the reception input signal of the high s/n ratio and the local input signal of high s/n ratio
Power spectrum phase, to obtain phase fringes.
4. the code phase measuring method according to claim 1 based on phase fringes, which is characterized in that in step 2) and step
It is rapid 3) between further include: do time domain folding for the reception input signal and the local input signal, obtain high s/n ratio
Reception input signal and high s/n ratio local input signal；
And it is described 3) in, calculate the mutual of the reception input signal of the high s/n ratio and the local input signal of high s/n ratio
Power spectrum phase, to obtain phase fringes.
5. the code phase measuring method according to claim 3 or 4 based on phase fringes, which is characterized in that the time domain
Folding includes:
Input signal, local input signal will be received or be divided into n sections respectively by the local input signal of delay compensation；
Every segment data superposition summation of input signal will be received, obtains the reception input signal of high s/n ratio；Local input is believed
Number or by delay compensation local input signal every segment data be superimposed summation, obtain the local input signal of high s/n ratio.
6. the code phase measuring method according to claim 1 or 2 or 3 or 4 based on phase fringes, which is characterized in that institute
Step 3) is stated to specifically include:
If signal is f all the way1(t), another way signal is f2(t), Fourier transform is carried out to this two paths of signals respectively, is obtained
The then cross-spectral density of two paths of signals are as follows:
Wherein, * indicates complex conjugate；
Power spectrum phase is plural number S12The argument main value of (ω):
φ (ω)=arg [S12(ω)]；
Wherein, the signal all the way is the reception input signal for receiving input signal or high s/n ratio；The another way signal is
Local input signal, or by the local input signal of delay compensation or the local input signal of high s/n ratio.
7. the code phase measuring method according to claim 1 or 2 or 3 or 4 based on phase fringes, which is characterized in that
In step 4), Fourier transformation is done to phase fringes to seek fringe frequency.
8. a kind of code phase measuring device based on phase fringes characterized by comprising
Signal receive with choose module, for choose receiver radio frequency front end down coversion intermediate-freuqncy signal and track loop into
Local replica carrier wave and local copy codes after entering tenacious tracking state；
Filtering and Doppler frequency shift module, for filtering out carrier wave and Doppler's frequency to the intermediate-freuqncy signal and local replica carrier wave
It moves, obtains receiving input signal；Using local copy codes as local input signal；
Crosspower spectrum phase computing module, it is raw for calculating the Crosspower spectrum phase for receiving input signal and local input signal
At phase fringes；
Fringe frequency seeks module, for seeking fringe frequency from phase fringes, obtains the reception input signal and local
The interval time delay of input signal.
9. the code phase measuring device according to claim 8 based on phase fringes, which is characterized in that further include that time delay is mended
It repays module and deletes delay compensation amount module；Wherein,
Signal is received the local input signal exported with selection module and does delay compensation by the delay compensation module；
The deletion delay compensation amount module is used to seek fringe frequency the reception input signal that module is exported and local is defeated
The interval time delay for entering signal subtracts the delay volume of compensation.
10. the code phase measuring device according to claim 9 based on phase fringes, which is characterized in that further include time domain
Module is folded, which is used to do time domain folding for the reception input signal and by the local input signal of delay compensation
It is folded, obtain the reception input signal of high s/n ratio and the local input signal of high s/n ratio；
And in Crosspower spectrum phase computing module, the reception input signal of the high s/n ratio and the sheet of high s/n ratio are calculated
The Crosspower spectrum phase of ground input signal, to obtain phase fringes.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910035970.8A CN109856650B (en) | 2019-01-15 | 2019-01-15 | Code phase measuring method based on phase stripes |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910035970.8A CN109856650B (en) | 2019-01-15 | 2019-01-15 | Code phase measuring method based on phase stripes |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN109856650A true CN109856650A (en) | 2019-06-07 |
| CN109856650B CN109856650B (en) | 2020-11-13 |
Family
ID=66894839
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201910035970.8A Active CN109856650B (en) | 2019-01-15 | 2019-01-15 | Code phase measuring method based on phase stripes |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN109856650B (en) |
Citations (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20030193430A1 (en) * | 2002-03-22 | 2003-10-16 | Gresham Robert Ian | Pulse radar detection system |
| CN103152073A (en) * | 2013-02-17 | 2013-06-12 | 哈尔滨工程大学 | Pseudo code capture method based on hysteresis comparison judgment |
| CN103454651A (en) * | 2013-08-30 | 2013-12-18 | 上海交通大学 | Fast GPS L2C CM code capturing method |
| CN103592663A (en) * | 2013-11-26 | 2014-02-19 | 东南大学 | Method for capturing CL codes of GPS L2C signals |
| CN104237871A (en) * | 2013-06-08 | 2014-12-24 | 中国科学院声学研究所 | Delay inequality estimation method based on phase compensation |
| CN105301580A (en) * | 2015-10-30 | 2016-02-03 | 哈尔滨工程大学 | Passive detection method based on split array cross-spectrum phase difference variance weighing |
| CN108401581B (en) * | 2013-11-11 | 2016-05-11 | 中国电子科技集团公司第五十四研究所 | A kind of PN code quick capturing methods in satellite spectrum-spread communication system |
| CN108205080A (en) * | 2018-01-08 | 2018-06-26 | 哈尔滨工程大学 | Coherent averaging technique harmonic signal power Power estimation method |
| CN108490458A (en) * | 2018-02-28 | 2018-09-04 | 上海交通大学 | Satellite navigation multipath signal parameter Estimation and error inhibition method |
| CN108828602A (en) * | 2018-03-06 | 2018-11-16 | 北京大学 | A kind of pulsion phase dry method tests the speed the fuzzy signal processing method of middle release rate |
| CN109100757A (en) * | 2018-09-26 | 2018-12-28 | 中国科学院国家授时中心 | A kind of method for evaluating quality of New Satellite navigation signal |
-
2019
- 2019-01-15 CN CN201910035970.8A patent/CN109856650B/en active Active
Patent Citations (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20030193430A1 (en) * | 2002-03-22 | 2003-10-16 | Gresham Robert Ian | Pulse radar detection system |
| CN103152073A (en) * | 2013-02-17 | 2013-06-12 | 哈尔滨工程大学 | Pseudo code capture method based on hysteresis comparison judgment |
| CN104237871A (en) * | 2013-06-08 | 2014-12-24 | 中国科学院声学研究所 | Delay inequality estimation method based on phase compensation |
| CN103454651A (en) * | 2013-08-30 | 2013-12-18 | 上海交通大学 | Fast GPS L2C CM code capturing method |
| CN108401581B (en) * | 2013-11-11 | 2016-05-11 | 中国电子科技集团公司第五十四研究所 | A kind of PN code quick capturing methods in satellite spectrum-spread communication system |
| CN103592663A (en) * | 2013-11-26 | 2014-02-19 | 东南大学 | Method for capturing CL codes of GPS L2C signals |
| CN105301580A (en) * | 2015-10-30 | 2016-02-03 | 哈尔滨工程大学 | Passive detection method based on split array cross-spectrum phase difference variance weighing |
| CN108205080A (en) * | 2018-01-08 | 2018-06-26 | 哈尔滨工程大学 | Coherent averaging technique harmonic signal power Power estimation method |
| CN108490458A (en) * | 2018-02-28 | 2018-09-04 | 上海交通大学 | Satellite navigation multipath signal parameter Estimation and error inhibition method |
| CN108828602A (en) * | 2018-03-06 | 2018-11-16 | 北京大学 | A kind of pulsion phase dry method tests the speed the fuzzy signal processing method of middle release rate |
| CN109100757A (en) * | 2018-09-26 | 2018-12-28 | 中国科学院国家授时中心 | A kind of method for evaluating quality of New Satellite navigation signal |
Non-Patent Citations (2)
| Title |
|---|
| A. J. VAN DIERENDONCK ET AL.: "Theory and Performance of Narrow Correlator Spacing in a GPS Receiver", 《NAVIGATION: JOURNAL OF THE INSTITUTE OF NAUIGATION》 * |
| 张志勇 等: "一种基于相位测量的激光测距方法", 《光电工程》 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN109856650B (en) | 2020-11-13 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| Antoniou et al. | GNSS-based bistatic SAR: A signal processing view | |
| Rius et al. | Altimetry with GNSS-R interferometry: First proof of concept experiment | |
| US4797677A (en) | Method and apparatus for deriving pseudo range from earth-orbiting satellites | |
| Groves et al. | Novel multipath mitigation methods using a dual-polarization antenna | |
| CN103116169B (en) | Anti-inference method based on vector tracking loop | |
| CN107728172A (en) | A kind of spaceborne receiver of the Big Dipper/GPS dual-mode and its navigation locating method | |
| Su et al. | Triple-frequency carrier phase precise time and frequency transfer models for BDS-3 | |
| CN102183770A (en) | GPS (Global Positioning System) pseudo-random code tracking loop for preventing multi-path interference and method for preventing multi-path interference thereof | |
| CN109633698B (en) | Indoor pseudo satellite anti-multipath method based on narrow correlation and robust adaptive filtering | |
| Jia et al. | Multipath interference mitigation in GNSS via WRELAX | |
| CN102033236A (en) | Position and speed combined estimation method for satellite navigation | |
| CN106842263A (en) | Based on the satellite navigation method that navigation signal space time processing is combined with vector tracking | |
| Jovanovic et al. | Multipath mitigation techniques for CBOC, TMBOC and AltBOC signals using advanced correlators architectures | |
| JPH0748078B2 (en) | Distance measurement method by correlation of spread spectrum dual frequency signals | |
| Yang et al. | Post-correlation semi-coherent integration for high-dynamic and weak GPS signal acquisition | |
| Kim et al. | An ultra-tightly coupled GPS/INS integration using federated Kalman filter | |
| CA2773548C (en) | Dual-frequency receiver for satellite-based positioning and associated method of reception | |
| Khan et al. | Acquisition strategies of GNSS receiver | |
| Li et al. | Implementation and performance of clock steering in a software GPS L1 single frequency receiver | |
| CN109856650A (en) | Code phase measuring method based on phase fringes | |
| Bai et al. | GNSS-R open-loop difference phase altimetry: Results from a bridge experiment | |
| Tamazin | High resolution signal processing techniques for enhancing GPS receiver performance | |
| Liu et al. | Local‐area nanosecond‐accuracy time synchronisation based on GPS L1 observations | |
| Paonni et al. | Looking for an Optimum S‐Curve Shaping of the Different MBOC Implementations | |
| Xiang et al. | A new inter-satellite ranging method based on pseudo-range and dual-frequency carrier phase |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |