CN109842430A - LoRa modulated signal demodulation method under multipath channel - Google Patents
LoRa modulated signal demodulation method under multipath channel Download PDFInfo
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Abstract
The invention discloses the LoRa modulated signal demodulation method under a kind of multipath channel, mainly solve the problems, such as that the prior art is poor to the direct demodulation performance of LoRa modulated signal.Its implementation are as follows: to after down-sampling targeting signal and load signal directly demodulated, obtain directly demodulation after targeting signal A and load signal D；The maximum value in A is found, and each M point that retain maximum value or so, length is the targeting signal C of (2M+1) after intercept, will be in C less than its maximum valuePoint data reset to 0, obtain new targeting signal B；New targeting signal B and the load signal D directly after demodulation are made into matched filtering, obtain new load signal E；Position P corresponding to each symbol maximum value is found in E, and the decimal system is successively carried out to it to binary conversion and Gray's inverse mapping, obtains modulation intelligence bit.The present invention improves the demodulation performance of system, the processing that can be used in the case where multipath channel in receiving end to LoRa modulated signal.
Description
Technical field
The invention belongs to fields of communication technology, and in particular to a kind of demodulation method of LoRa modulated signal can be used for multipath
Processing in the case where channel in receiving end to LoRa modulated signal.
Background technique
With development of the Internet user from people to object, Internet of Things IoT causes the great interest of people.Internet of Things makes
It is interconnected between object around us, while sending and receiving for message can be carried out to internet.In order to meet Internet of Things
The various demands of net application, low-power consumption wide area LPWAN provide novel communication paradigms.LPWAN technology includes ultra-narrow band skill
Art SigFox, remote technology LoRa etc., the proposition of these technologies meet wide area of the Internet of Things from several kilometers to tens kilometer and connect
It connects, realizes low data rate, the application of low-power consumption and poor throughput.In LPWAN be recently proposed and prevailing
In technology, semiconductor maker Semtech has had been incorporated into its long-range LoRaTMThe advanced spread spectrum of product line is answered extensively
With.Different from the Direct Sequence Spread Spectrum DSSS of message signale is modulated in pseudo noise code, LoRa is used, and there is frequency to increase at any time
Up-chirp or the swept-frequency signal of reduction down-chirp is added to carry out coded message signal, it can be seen that be exactly on LoRa technological essence
A kind of derivative of chirp band spectrum modulation.
Chirp spread-spectrum modulation technique CSS neither uses pseudo noise code as spreading code, also without frequency pattern, but it is sharp
Spread spectrum communication is realized with the matched filtering of chirp signal and pulse compression characteristics.In wireless communication field, chirp spread spectrum is adjusted
Technology processed is still a kind of novel technology, although being listed in one of the physical criterion of IEEE 802.15.4, still
There are many shortcomings.For example, if chirp spread spectrum is not used alone in conjunction with other modulation techniques carries out information transmission
General link capacity is all relatively low, and the raising of message transmission rate will be by shortening chirp signal duration, or uses and hand over
Folded technology realizes, however either shortens duration of chirp signal and still carry out overlapping all improving system to signal
Complexity and power consumption.
It is general for the demodulation of signal in such a way that tradition directly demodulates in LoRa modulating system, as shown in fig. 6,
I.e. to the dot product for receiving signal progress and original down-chirp, Fast Fourier Transform (FFT) FFT is then carried out, maximum value is finally carried out
Judgement.The case where direct demodulation mode can obtain preferable demodulation performance under the channel of single diameter, but channel is multipath
Under, the demodulation performance of system, which just will appear, sharply to be declined, i.e., error bit ability will decline, and the reliability of system is caused to reduce.
Summary of the invention
It is an object of the invention to deficiency in view of the above technology, the LoRa modulated signal solution under a kind of multipath channel is proposed
Tune method, to improve the error bit ability of receiving end, to improve the reliability of system.
To achieve the above object, technical scheme is as follows:
(1) corresponding dot product will be carried out with original down-chirp signal by the targeting signal after down-sampling, then successively
It carries out FFT and seeks absolute value, length is 2 after obtaining directly demodulationSFTargeting signal A, wherein SF be spreading factor；
(2) interception and reset data are carried out to the targeting signal after direct demodulation, obtain new targeting signal B:
(2a) finds the targeting signal A maximum value after directly demodulating, and retains maximum value or so M point, is truncated to a length of
For the size of the targeting signal C, M of (2M+1) a point according to value the case where channel, value range is 1 to 2SF-1-1；
(2b) is by value and maximum value of each point of targeting signal C after interceptionIt is compared: when the value of certain point
Greater than maximum valueWhen, then the value of the point remains unchanged, when the value of certain point is less than maximum valueWhen, then by the value of the point
0 is reset to, new targeting signal B is obtained, wherein the size of P is according to value the case where channel,
(3) it will be carried out by each of load signal after down-sampling symbol with original down-chirp signal corresponding
Dot product, then successively carry out FFT and take absolute value to each symbol, obtain the load signal D after directly demodulation；
(4) each of the load signal D after directly demodulating symbol and new targeting signal B are subjected to matched filtering
Operation obtains new load signal E；
(5) position corresponding to each symbol maximum value is found in new load signal E, successively it is carried out ten into
Binary conversion and Gray's inverse mapping are made, modulation intelligence bit is obtained.
Compared with prior art, the present invention having the advantage that
1. the reliability of lifting system
In the present invention, passes through the matched filter operation of targeting signal and load signal in receiving end, take full advantage of leading
The channel information for including in signal, to reduce the influence of channel；Simultaneously because passing through during obtaining targeting signal
Interception and reset data to targeting signal, reduce the introducing of noise；It is directly right compared in traditional Direct demodulation
The load signal received is demodulated, and the present invention is influenced less by channel and noise, and the demodulation performance of acquisition is higher, from
And the reliability of LoRa modulated signal demodulating system can be improved.
2. error bit ability is good
Experiments have shown that being set as fixing two diameters in channel, under conditions of SF=7, the bit error rate is 10-3Locate property of the invention
There can be the promotion of 1.5dB compared to traditional Direct demodulation, there was only 0.5dB compared with the performance under additive Gaussian white noise channel
Gap.
Detailed description of the invention
Fig. 1 is LoRa signal frequency modulation figure used in the present invention；
Fig. 2 is LoRa signal modulation figure used in the present invention；
Fig. 3 is realization block diagram of the invention；
Fig. 4 is the implementation flow chart of targeting signal and load signal when demodulating in the present invention；
Fig. 5 be in the present invention demodulation when to targeting signal interception and reset data realization principle figure；
Fig. 6 is the schematic diagram demodulated with traditional demodulation method to LoRa signal；
Fig. 7 is not intercept with the present invention, traditional Direct demodulation and using matched filtering to targeting signal
With non-these four methods of zero setting of interception, in SF=7, channel is the error bit ability comparison diagram fixed under two diameters；
Fig. 8 is not intercept with the present invention, traditional Direct demodulation and using matched filtering to targeting signal
With non-these four methods of zero setting of interception, in SF=8, channel is the error bit ability comparison diagram fixed under two diameters.
Specific embodiment
Below in conjunction with the drawings and specific embodiments, the object, technical solutions and advantages of the present invention are described in detail.It is aobvious
So, based on the embodiments of the present invention, those of ordinary skill in the art are obtained without making creative work
Every other embodiment, shall fall within the protection scope of the present invention.
The present invention relates to a kind of demodulation method of LoRa signal, LoRa signal is with up-chirp or down-chirp
Swept-frequency signal carrys out encoded signal information.
Referring to Fig.1, the frequency modulation(PFM) of the LoRa signal, including unmodulated LoRa signal, the i.e. frequency of up-chirp signal
Rate curve line 1, the frequency curve line 2 of LoRa signal after modulation.
Referring to Fig. 2, the LoRa signal modulation, including unmodulated LoRa signal graph a, LoRa signal graph b after modulation.
Current major part is all traditional Direct demodulation about the demodulation use of LoRa modulated signal, and this method is in list
Under diameter channel, preferable performance can be obtained, but under multipath channel, error bit ability can significantly decrease, system can
It is deteriorated by property.The present invention is exactly to solve the problems, such as the demodulation of the LoRa modulated signal under multipath channel.
Referring to Fig. 3, steps are as follows for realization of the invention:
Step 1, targeting signal and load signal are obtained.
It is respectively that original up-chirp and original down-chirp carries out down-sampling to reception signal, unmodulated LoRa signal；
The symbolic number of targeting signal and load signal according to known to receiving end divides the reception signal after down-sampling
It cuts, obtains targeting signal F and load signal P1.
Step 2, new targeting signal B and load signal D are obtained.
Referring to Fig. 4, this step is implemented as follows:
(2a) obtains new targeting signal B:
(2a1) is that original down-chirp is carried out a little by targeting signal F and by the unmodulated LoRa signal after down-sampling
Multiply, then successively carry out FFT and seek absolute value, obtaining length is 2SFTargeting signal A；
(2a2) is 2 to lengthSFTargeting signal A intercepted:
Referring to Fig. 5, the realization of this step are as follows: save maximum value or so M point, obtain the signal that length is (2M+1) a point
C finds out maximum value from the targeting signal A after direct demodulation, and determines the subscript MAX of the corresponding position of the maximum value, by MAX
Compared with M carries out size:
As MAX≤M, 2 will be designated as under targeting signal ASF(MAX-M) is designated as 2 underSFThis segment signal is as interception letter
Number front half section, will be designated as under targeting signal A 1 to this segment signal of subscript MAX+M as the second half section of intercept signal, front and back two
Section constitutes targeting signal C；
When MAX >=2SFWhen-M, it will be designated as MAX-M under targeting signal A and be designated as 2 underSFThis segment signal is as intercept signal
Front half section, 1 will be designated as under targeting signal A to subscript MAX+M-2SFSecond half section of this segment signal as intercept signal, front and back
Two sections of composition targeting signal C；
When MAX is unsatisfactory for above-mentioned two situations, it is leading that this segment signal of MAX-M to MAX+M composition is designated as under targeting signal A
Signal C；
(2a3) resets the targeting signal C after interception:
By the value of the every bit in the targeting signal C after interception and maximum valueCompare as size, when certain point
Value is less than maximum valueWhen, which resets to 0, when the value of certain point is more than or equal to maximum valueWhen, keep the point
It is worth constant, obtains new targeting signal B, wherein the size of P is according to value the case where channel,
(2b) obtains new load signal D:
It will be original down- by each of load signal P1 after down-sampling symbol and unmodulated LoRa signal
Chirp signal carries out corresponding dot product, then successively carries out FFT to each symbol and take absolute value, and obtains after directly demodulating
Load signal D.
Step 3, new load signal E is obtained.
Each of new targeting signal B and load signal D symbol is subjected to matched filtering, is keeping load signal D
In each symbol it is fixed in the case where, new targeting signal B is carried out to slide dot product point by point with it, when new targeting signal
When B is overlapped with the last one point of each symbol in load signal D, by each symbol in load signal D since starting point
It gradually moves and is placed on the last one point below, when the starting point of new targeting signal B and load signal D are overlapped again,
Operation is terminated, acquired results are new load signal E.
Step 4, modulation intelligence bit is obtained.
(5a) finds the subscript m ax of position corresponding to each symbol maximum value in new load signal E, calculates max+
The value of M-MAX, by the calculated result and 2SFMake complementation, to eliminate the influence of initial position MAX-M, obtains new load signal
The physical location P of each symbol maximum value in E；
The P that (5b) is obtained with (5a) takes coefficient d 0 of its remainder as binary gray code lowest order divided by 2, then after
Continue quotient divided by 2, coefficient d 1 of the gained remainder as binary gray code time low level repeats down always, until quotient is 0, obtains
To binary gray code b；
(5c) retains highest order of the highest order of binary gray code b as natural binary code, by natural binary code
A time high position of the highest order with the result after time high-order Gray code phase exclusive or as natural binary code；
(5d) successively finds out remaining position of natural binary code according to method identical with (5c), obtains modulation intelligence ratio
It is special.
Below in conjunction with emulation experiment, technical effect of the invention is described in further detail:
Experiment 1,
1.1) experiment condition: SF=7 i.e. symbol lengths are set as 128 points, sample frequency Fs=10MHz up-samples multiple
It is 8, signal bandwidth B=Fs/8, the byte-sized for inputting modulation intelligence is Byte=64, and channel is two fixed diameters, and
Delay time between two diameters is 0.6us, retains targeting signal A maximum value or so each 16 points, takes
1.2) experiment content
It is above-mentioned 1.1) under the conditions of, LoRa signal is demodulated with the method for the present invention and traditional demodulation method, as a result
It is as shown in Figure 7:
From fig.7, it can be seen that the method for the present invention compares traditional demodulation method, it is 10 in the bit error rate-3Locate error bit ability to obtain
The promotion of 1.5dB, and 33 points are not set 0 targeting signal compared with 128 points of long targeting signals, error bit ability is promoted,
33 points of length set 0 targeting signal with it is 33 points long do not set 0 targeting signal compared with, error bit ability is equally also promoted.From can
For the angle of property, under identical SNR, bit error rate is lower, and the reliability of the system is better.
It is also seen that from 5 curves of Fig. 7 under the performance and theoretical case additive white Gaussian noise AWGN of the method for the present invention
Performance it is close, i.e. the only gap of 0.5dB.
Experiment 2,
2.1) experiment condition: SF=8 i.e. symbol lengths are set as 256 points, sample frequency Fs=10MHz up-samples multiple
It is 8, signal bandwidth B=Fs/8, the byte-sized for inputting modulation intelligence is Byte=64, and channel is two fixed diameters, and
Delay time between two diameters is 0.6us, retains targeting signal A maximum value or so each 16 points, takes
2.2) experiment content
It is above-mentioned 2.1) under the conditions of, LoRa signal is demodulated with the method for the present invention and traditional demodulation method, as a result
It is as shown in Figure 8:
As seen from Figure 8, the method for the present invention compares traditional demodulation method, is 10 in the bit error rate-3Locate error bit ability to obtain
The promotion of 1.5dB, and 33 points are not set 0 targeting signal compared with 256 points of long targeting signals, error bit ability is promoted,
33 points of length set 0 targeting signal with it is 33 points long do not set 0 targeting signal compared with, error bit ability is equally also promoted.
For the angle of reliability, under identical SNR, bit error rate is lower, and the reliability of the system is better.
To sum up, the demodulation method of the LoRa modulated signal under a kind of multipath channel of the invention and traditional LoRa, which are modulated, believes
Number Direct demodulation is compared, identical in SF, is fixed under conditions of two diameters, is 10 in the bit error rate-3Locate error bit ability to obtain
The promotion of 1.5dB, at the same set leading after 0 and do not set 0 it is leading, and do not intercept leading, not matched method is compared, property
Can all be it is best, differed with the performance under theoretical case additive white Gaussian noise AWGN only 0.5dB, show the present invention in multipath
There is better demodulation performance, the reliability of system is higher under channel.
Claims (4)
1. the LoRa modulated signal demodulation method under a kind of multipath channel, which is characterized in that include the following:
(1) corresponding dot product will be carried out with original down-chirp signal by the targeting signal after down-sampling, then successively carried out
FFT and absolute value is sought, length is 2 after obtaining directly demodulationSFTargeting signal A, wherein SF be spreading factor；
(2) interception and reset data are carried out to the targeting signal after direct demodulation, obtain new targeting signal B:
(2a) finds the targeting signal A maximum value after directly demodulating, and retains maximum value or so M point, is truncated to a length of (2M+
1) for the size of the targeting signal C, M of a point according to value the case where channel, value range is 1 to 2SF-1-1；
(2b) is by value and maximum value of each point of targeting signal C after interceptionIt is compared: when the value of certain point is greater than
Equal to maximum valueWhen, then the value of the point remains unchanged, when the value of certain point is less than maximum valueWhen, then by the value of the point
0 is reset to, new targeting signal B is obtained, wherein the size of P is according to value the case where channel,
It (3) will be by each of load signal after down-sampling symbol and original down-chirp signal progress corresponding points
Multiply, then successively carry out FFT and take absolute value to each symbol, obtains the load signal D after directly demodulation；
(4) each of the load signal D after directly demodulating symbol and new targeting signal B are subjected to matched filtering fortune
It calculates, obtains new load signal E；
(5) position P corresponding to each symbol maximum value is found in new load signal E, and the decimal system successively is carried out to it
To binary conversion and Gray's inverse mapping, modulation intelligence bit is obtained.
2. the method according to claim 1, wherein being 2 to length in step (2a)SFTargeting signal A carry out
Interception saves maximum value or so M point, obtains the signal C that length is (2M+1) a point, the targeting signal A after directly demodulating
In find out maximum value, and determine the subscript MAX of the corresponding position of the maximum value, by MAX with M progress size compared with:
As MAX≤M, 2 will be designated as under targeting signal ASF(MAX-M) is designated as 2 underSFThis segment signal is as intercept signal
Front half section will be designated as 1 to this segment signal of subscript MAX+M as the second half section of intercept signal, two sections of front and back structure under targeting signal A
At targeting signal C；
When MAX >=2SFWhen-M, it will be designated as MAX-M under targeting signal A and be designated as 2 underSFBefore this segment signal is as intercept signal
Half section, 1 to subscript MAX+M-2 will be designated as under targeting signal ASFSecond half section of this segment signal as intercept signal, two sections of front and back
Constitute targeting signal C；
When MAX is unsatisfactory for above-mentioned two situations, it is designated as this segment signal of MAX-M to MAX+M under targeting signal A and constitutes targeting signal
C。
3. the method according to claim 1, wherein will be in new targeting signal B and load signal D in (4)
Each symbol carries out matched filtering, be in keeping load signal D each symbol it is fixed in the case where, will be new leading
Signal B carries out point-by-point sliding dot product, when new targeting signal B is overlapped with the last one point of each symbol in load signal D,
Each symbol in load signal D is gradually moved since starting point and is placed on the last one point below, until new leading
When the starting point of signal B and load signal D are overlapped again, operation is terminated.
4. the method according to claim 1, wherein being carried out in step (5) to load signal E new after matching
Maximum value detection, and Gray code inverse mapping is carried out to the binary system finally generated, realize that steps are as follows:
(5a) finds the subscript m ax of position corresponding to each symbol maximum value in new load signal E, calculates max+M-MAX
Value, by the calculated result and 2SFMake complementation, to eliminate the influence of initial position MAX-M, obtains every in new load signal E
The physical location P of one symbol maximum value；
The P that (5b) obtains (5a) takes coefficient d 0 of its remainder as binary gray code lowest order divided by 2, then proceed to by
Quotient is divided by 2, coefficient d 1 of the gained remainder as binary gray code time low level, repeats down always until quotient is 0, obtain two into
Gray code b processed；
(5c) retains highest order of the highest order of binary gray code b as natural binary code, most by natural binary code
A time high position of the high-order result with after time high-order Gray code phase exclusive or as natural binary code；
(5d) successively finds out remaining position of natural binary code according to method identical with (5c), obtains modulation intelligence bit.
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Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111181596A (en) * | 2019-12-31 | 2020-05-19 | 北京升哲科技有限公司 | Modulation-demodulation method and system |
| CN111181600A (en) * | 2019-12-31 | 2020-05-19 | 北京升哲科技有限公司 | Chirp spread spectrum modulation and demodulation method and system based on QPSK |
| CN112671680A (en) * | 2021-01-20 | 2021-04-16 | 哈尔滨工业大学 | LoRa demodulation method based on multiple bandwidth sampling for improving error code performance |
| CN113099487A (en) * | 2021-03-24 | 2021-07-09 | 重庆邮电大学 | Demodulation method of LoRa air interface data |
| CN113194053A (en) * | 2021-03-24 | 2021-07-30 | 哈尔滨工业大学 | Multi-path LoRa modulation and demodulation method based on fractional Fourier transform for high-speed transmission |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP2037605A1 (en) * | 2006-06-30 | 2009-03-18 | Fujitsu Ltd. | Digital mobile communication system and its transmission/reception method |
| JP2009230318A (en) * | 2008-03-21 | 2009-10-08 | Aiphone Co Ltd | Television intercom device |
| CN102437900A (en) * | 2011-12-28 | 2012-05-02 | 大唐微电子技术有限公司 | Digital interphone and method for reducing error rate of digital interphone |
| CN105721375A (en) * | 2016-03-28 | 2016-06-29 | 电子科技大学 | Low signal-to-noise ratio short preamble burst signal demodulation system and method |
| CN106850487A (en) * | 2014-12-10 | 2017-06-13 | 上海数字电视国家工程研究中心有限公司 | The method of reseptance of leading symbol |
| CN106878218A (en) * | 2017-01-25 | 2017-06-20 | 河南科技大学 | A kind of high reliability demodulation method for IEEE802.15.4 |
| CN107426122A (en) * | 2017-09-07 | 2017-12-01 | 西安电子科技大学 | Low complex degree minimum mean-squared error algorithm method for GFDM systems |
-
2019
- 2019-04-10 CN CN201910286472.0A patent/CN109842430B/en active Active
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP2037605A1 (en) * | 2006-06-30 | 2009-03-18 | Fujitsu Ltd. | Digital mobile communication system and its transmission/reception method |
| JP2009230318A (en) * | 2008-03-21 | 2009-10-08 | Aiphone Co Ltd | Television intercom device |
| CN102437900A (en) * | 2011-12-28 | 2012-05-02 | 大唐微电子技术有限公司 | Digital interphone and method for reducing error rate of digital interphone |
| CN106850487A (en) * | 2014-12-10 | 2017-06-13 | 上海数字电视国家工程研究中心有限公司 | The method of reseptance of leading symbol |
| CN105721375A (en) * | 2016-03-28 | 2016-06-29 | 电子科技大学 | Low signal-to-noise ratio short preamble burst signal demodulation system and method |
| CN106878218A (en) * | 2017-01-25 | 2017-06-20 | 河南科技大学 | A kind of high reliability demodulation method for IEEE802.15.4 |
| CN107426122A (en) * | 2017-09-07 | 2017-12-01 | 西安电子科技大学 | Low complex degree minimum mean-squared error algorithm method for GFDM systems |
Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN111181596A (en) * | 2019-12-31 | 2020-05-19 | 北京升哲科技有限公司 | Modulation-demodulation method and system |
| CN111181600A (en) * | 2019-12-31 | 2020-05-19 | 北京升哲科技有限公司 | Chirp spread spectrum modulation and demodulation method and system based on QPSK |
| CN111181596B (en) * | 2019-12-31 | 2021-11-30 | 北京升哲科技有限公司 | Modulation-demodulation method and system |
| CN111181600B (en) * | 2019-12-31 | 2022-01-11 | 北京升哲科技有限公司 | Chirp spread spectrum modulation and demodulation method and system based on QPSK |
| CN112671680A (en) * | 2021-01-20 | 2021-04-16 | 哈尔滨工业大学 | LoRa demodulation method based on multiple bandwidth sampling for improving error code performance |
| CN112671680B (en) * | 2021-01-20 | 2023-01-31 | 哈尔滨工业大学 | LoRa demodulation method based on multiple bandwidth sampling for improving error code performance |
| CN113099487A (en) * | 2021-03-24 | 2021-07-09 | 重庆邮电大学 | Demodulation method of LoRa air interface data |
| CN113194053A (en) * | 2021-03-24 | 2021-07-30 | 哈尔滨工业大学 | Multi-path LoRa modulation and demodulation method based on fractional Fourier transform for high-speed transmission |
| CN113099487B (en) * | 2021-03-24 | 2022-05-03 | 重庆邮电大学 | Demodulation method of LoRa air interface data |
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