CN109639153B - Model prediction control method of Quasi-Z source indirect matrix converter - Google Patents

Model prediction control method of Quasi-Z source indirect matrix converter Download PDF

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CN109639153B
CN109639153B CN201811604068.5A CN201811604068A CN109639153B CN 109639153 B CN109639153 B CN 109639153B CN 201811604068 A CN201811604068 A CN 201811604068A CN 109639153 B CN109639153 B CN 109639153B
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CN109639153A (en
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刘钰山
葛宝明
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Beijing University of Aeronautics and Astronautics
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits

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Abstract

The embodiment of the invention discloses a model prediction control method of a Quasi-Z source indirect matrix converter, which is used for controlling Quasi-Z source network output voltage, input reactive power and load current of the Quasi-Z source indirect matrix converter in the next control period through only one control closed loop on the basis of establishing a Quasi-Z source network discrete time model without a complex modulation algorithm and an additional closed loop control strategy of the matrix converter. The embodiment of the invention has the characteristics of simple algorithm, easy digital realization, fast dynamic response and high steady-state precision.

Description

Model prediction control method of Quasi-Z source indirect matrix converter
Technical Field
The invention relates to the technical field of converter control, in particular to a model prediction control method of a Quasi-Z source indirect matrix converter.
Background
The Quasi-Z source indirect matrix converter combines the advantages of the Quasi-Z source converter and the indirect matrix converter, and presents unique advantages in an alternating current-alternating current conversion system: 1) the advantages that the traditional indirect matrix converter has no intermediate direct current link, the input and output currents are sine waves, and energy flows bidirectionally are inherited; 2) the function of pumping up the voltage of the power grid is realized, the voltage gain is improved, and the limitation of the voltage transmission ratio of the traditional indirect matrix converter is overcome; 3) an extra LC filter is not needed at the input side, so that the hardware structure of the system is greatly simplified; 4) two switching tubes of the same bridge arm in the converter are allowed to be conducted simultaneously without damaging devices, so that the complexity of system control is reduced, and the safety of the system is improved; 5) the converter has certain ride-through capability on the voltage drop of the power grid, namely the function of resisting the interference of the voltage drop of the power grid, and improves the stability of the converter system. Therefore, the Quasi-Z source indirect matrix converter has a good application prospect in the field of alternating current conversion.
The space vector modulation strategy of the existing Quasi-Z source indirect matrix converter needs to carry out voltage and current vector operation and duty ratio synthesis on a rectification stage and an inversion stage respectively, the algorithm is complex, and when the Quasi-Z source indirect matrix converter is applied to the fields of alternating current speed regulation and the like, an additional closed-loop control strategy needs to be designed.
Disclosure of Invention
The embodiment of the invention aims to provide a model prediction control method of a Quasi-Z source indirect matrix converter, which is used for solving the problem of complex algorithm caused by the fact that the space vector modulation strategy of the existing Quasi-Z source indirect matrix converter needs to carry out voltage and current vector operation and duty ratio synthesis on a rectification stage and an inversion stage respectively.
In order to achieve the above object, an embodiment of the present invention provides a model prediction control method for a Quasi-Z source indirect matrix converter, where the method includes: measuring a plurality of voltage and current values of different nodes of the Quasi-Z source indirect matrix converter at the moment k; establishing a switching function according to the corresponding relation between each switch combination state and each group of switch state vectors of the Quasi-Z source indirect matrix converter at the time k, and extracting a rectifier stage switch state S corresponding to each group of switch state vectorsrecAnd inverter stage switching state SinvWherein S isrec＝[Sap,Sbp,Scp]，Sinv＝[SAp,SBp,SCp](ii) a Voltage and current measured values at time k and rectifier stage switching state S obtained by measurementrecAnd inverter stage switching state SinvAnd predicting the output voltage u 'of the Quasi-Z source network at the time of k +1 of the next control cycle'abc(k +1), input reactive power Q (k +1) and value i of load current value in alpha beta coordinate systemsα(k +1) and isβ(k + 1); outputting the voltage u 'to the Quasi-Z source network at the time of k +1 of the next control cycle'abc(k +1), input reactive power Q (k +1) and value i of load current value in alpha beta coordinate systemsα(k +1) and isβThe predicted values of (k +1) are respectively given reference values u'* abc、Q*、i* sαAnd i* sβComparing to form a value function g; the switching state S of the rectifier stage corresponding to each group of switching state vectors in the switching functionrecAnd inverter stage switching state SinvSubstituting a value function g containing a predicted value and a given reference value, and taking a switch combination state corresponding to the switch state vector with the minimum value of the value function g as the output of a prediction control strategy; and at the moment k +1, controlling each switch of the Quasi-Z source indirect matrix converter by using the output of the prediction control strategy.
Further, the measuring a plurality of voltage and current values of different nodes of the Quasi-Z source indirect matrix converter at the time k comprises: measuring the grid voltage u at time kabc(k) (ii) a Measuring input current i of Quasi-Z source network at moment kL1abc(k) (ii) a Measuring the k time QOutput voltage u 'of uasi-Z source network'abc(k) (ii) a And measuring the load current i of the Quasi-Z source indirect matrix converter at the time kABC(k) And a load voltage uABC(k)。
Further, predicting the Quasi-Z source network output voltage u 'at the time of k +1 of the next control cycle'abc(k +1) includes: measuring the measured value i at the k momentABC(k)、u'abc(k) And iL1abc(k) An input voltage prediction model; the voltage prediction model predicts u 'according to a voltage prediction calculation formula shown in the table below'abc(k+1)：
Figure BDA0001923185780000031
Wherein u '(k +1) ═ u'abc(k+1)，u'(k)＝u'abc(k)，iL1(k)＝iL1abc(k)，i'o(k)＝Srec SinviABC(k)＝Srec Sinv[iA(k),iB(k),iC(k)]，TsFor controlling the period, C is a Quasi-Z source network capacitor Ca1、Cb1、Cc1、Ca2、Cb2And Cc2，Ca1＝Cb1＝Cc1＝Ca2＝Cb2＝Cc2。
Further, predicting the Quasi-Z source network input reactive power Q (k +1) at the time of the next control cycle k +1 comprises: measured value u of k time obtained by measurementabc(k) After the input reactive power prediction model is subjected to three-phase abc-two-phase alpha-beta coordinate transformation, a voltage component u under an alpha-beta coordinate is obtainediα(k) And uiβ(k) (ii) a Predicting Q (k +1) by the following reactive power prediction calculation formula in the reactive power prediction model:
Q(k+1)＝uiα(k)iL1β(k+1)-uiβ(k)iL1α(k+1)
wherein iL1α(k +1) and iL1βThree-phase input current i of Quasi-Z source network with (k +1) as k +1 momentL1abc(k +1) component in α β coordinate, iL1abc(k +1) forecasting by a reactive power forecasting model according to a three-phase input current forecasting calculation formula of the Quasi-Z source network at the k +1 moment shown in the following table:
Figure BDA0001923185780000032
wherein iL1(k+1)＝iL1abc(k+1)，iL1(k)＝iL1abc(k)，u'(k+1)＝u'abc(k+1)，ui(k)＝uabc(k)，TsFor controlling the period, L is a Quasi-Z source network inductor La1、Lb1、Lc1、La2、Lb2And Lc2，La1＝Lb1＝Lc1＝La2＝Lb2＝Lc2，RLIs a Quasi-Z source network inductor La1、Lb1、Lc1、La2、Lb2And Lc2Internal resistance of (2).
Further, predicting a value i of a load current value of the Quasi-Z source indirect matrix converter at the time of the next control cycle k +1 in an alpha beta coordinate systemsα(k +1) and isβ(k +1) includes: measuring the measured value i at the k momentABC(k) And uABC(k) Inputting a current prediction model after three-phase abc-two-phase alpha beta coordinate transformation; predicting i by the following current prediction calculation formula in the current prediction modelsα(k +1) and isβ(k+1)：
Figure BDA0001923185780000041
Wherein isα(k) And isβ(k) Is a load current iABC(k) Values in the α β coordinate system, Uα(k) And Uβ(k) Is a load voltage uABC(k) Value in the α β coordinate system, TsFor controlling the period, LLIs load inductance, R'LIs a loadAnd (4) resistance.
Further, the expression of the cost function g is:
Figure BDA0001923185780000043
wherein λ is1、λ2、λ3、λ4、λ5And λ6Six weight factors are 0.2, 0.1 and 0.3, Q*＝0。
Further, the correspondence between each switch combination state and each group of switch state vectors of the Quasi-Z source indirect matrix converter includes: each group of switch state vectors comprises 10 rectifier stage current vectors I1To I10And 8 inverter stage voltage vectors U0To U7Wherein the current vector I of the rectifier stage1To I6Is 6 effective vectors, I7To I9Is 3 zero vectors, I10Is 1 direct zero vector, voltage vector U1To U6Is 6 effective vectors, U0And U7Is 2 zero vectors; according to 10 rectifier stage current vectors I1To I10And 8 inverter stage voltage vectors U0To U7Switching Quasi-Z source network SxRectifier stage switch Sa,b,cAnd inverter stage switch SA,B,CThe switch states of (a) form a correspondence as shown in the following table:
Figure BDA0001923185780000044
Figure BDA0001923185780000061
where 1 indicates that the switch is on and 0 indicates that the switch is off.
Further, of said predictive control strategyThe output includes: Quasi-Z source network switch SxRectifier stage switch Sa,b,cAnd inverter stage switch SA,B,CControl signal g ofz、grecAnd ginv。
The embodiment of the invention has the following advantages:
the embodiment of the invention discloses a model prediction control method of a Quasi-Z source indirect matrix converter, which is used for controlling Quasi-Z source network output voltage, input reactive power and load current of the Quasi-Z source indirect matrix converter in the next control period through only one control closed loop on the basis of establishing a Quasi-Z source network discrete time model without a complex modulation algorithm and an additional closed loop control strategy of the matrix converter. The embodiment of the invention has the characteristics of simple algorithm, easy digital realization, fast dynamic response and high steady-state precision.
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FIG. 1 is a schematic diagram of a model prediction control method of a Quasi-Z source indirect matrix converter disclosed by the invention.
FIG. 2 is a circuit diagram of a Quasi-Z source indirect matrix converter disclosed in the present invention.
The method comprises the following steps of 01-alternating current power supply, 02-Quasi-Z source network, 03-front end rectification stage, 04-rear end inverter stage, 05-alternating current load, 06-voltage prediction model, 07-reactive power prediction model and 08-current prediction model.
Detailed Description
The present invention is described in terms of particular embodiments, other advantages and features of the invention will become apparent to those skilled in the art from the following disclosure, and it is to be understood that the described embodiments are merely exemplary of the invention and that it is not intended to limit the invention to the particular embodiments disclosed. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Example 1
In order to realize the control of the Quasi-Z source indirect matrix converter which is easy to realize and quick in response, the embodiment of the invention discloses a model prediction control method of the Quasi-Z source indirect matrix converter, wherein, referring to the figure 1 and the figure 2, the Quasi-Z source indirect matrix converter comprises a Quasi-Z source network 02, a front end rectification stage 03 and a rear end inversion stage 04 which are sequentially connected, the Quasi-Z source network 02 is powered by an alternating current power supply 01, and the output end of the rear end inversion stage 04 is connected with an alternating current load 05.
Referring to fig. 1, in the model predictive control method for the Quasi-Z source indirect matrix converter disclosed in this embodiment, first, a plurality of voltage and current values of different nodes of the Quasi-Z source indirect matrix converter at the time k are measured, which specifically includes: measuring the grid voltage u at time kabc(k) (ii) a Measuring input current i of Quasi-Z source network at moment kL1abc(k) (ii) a Measuring output voltage u 'of Quasi-Z source network at moment k'abc(k) (ii) a And measuring the load current i of the Quasi-Z source indirect matrix converter at the time kABC(k) And a load voltage uABC(k)。
Meanwhile, referring to fig. 2, a switching function may be established according to a correspondence relationship between each switching combination state of the Quasi-Z source indirect matrix converter at the time k and each group of switching state vectors, and a rectifier stage switching state S corresponding to each group of switching state vectors is extractedrecAnd inverter stage switching state SinvWherein S isrec＝[Sap,Sbp,Scp]，Sinv＝[SAp,SBp,SCp]。
Further, the correspondence between each switch combination state and each group of switch state vectors of the Quasi-Z source indirect matrix converter includes: each group of switch state vectors comprises 10 rectifier stage current vectors I1To I10And 8 inverter stage voltage vectors U0To U7Wherein the current vector I of the rectifier stage1To I6Is 6 effective vectors, I7To I9Is 3 zero vectors, I10Is 1 direct zero vector, voltage vector U1To U6Is 6 effective vectors, U0And U7Is 2 zero vectors; according to 10 rectifier stage current vectors I1To I10And 8 inverter stage voltage vectors U0To U7Convert Quasi-Z source network switch SxRectifier stage switch Sa,b,cAnd inverter stage switch SA,B,CThe switch states of (a) form a correspondence as shown in the following table:
Figure BDA0001923185780000081
Figure BDA0001923185780000091
Figure BDA0001923185780000101
where 1 indicates that the switch is on and 0 indicates that the switch is off, as shown in the table above, the Quasi-Z source network switch SxIs in the state of a rectifier stage switch Sa,b,cState-matched only when the rectifier stage switch Sa,b,cWhen the states of the switches are connected, the Quasi-Z source network switch SxIs open, otherwise, the Quasi-Z source network switch SxThe states of (1) are connected.
Then, several voltage and current measured values and the switching state S of the rectifier stage are obtained by measurement at the k timerecAnd inverter stage switching state SinvAnd predicting the output voltage u 'of the Quasi-Z source network at the time of k +1 of the next control cycle'abc(k +1), input reactive power Q (k +1) and value i of load current value in alpha beta coordinate systemsα(k +1) and isβ(k+1)。
Further, predicting the Quasi-Z source network output voltage u 'at the time of k +1 of the next control cycle'abc(k +1) includes: measuring the measured value i at the k momentABC(k)、u'abc(k) And iL1abc(k) An input voltage prediction model 06; the voltage prediction model 06 predicts u 'from the voltage prediction calculation formula shown in the following table'abc(k+1)：
Figure BDA0001923185780000111
Wherein u '(k +1) ═ u'abc(k+1)，u'(k)＝u'abc(k)，iL1(k)＝iL1abc(k)，i'o(k)＝Srec SinviABC(k)＝Srec Sinv[iA(k),iB(k),iC(k)]，TsFor controlling the period, C is a Quasi-Z source network capacitor Ca1、Cb1、Cc1、Ca2、Cb2And Cc2，Ca1＝Cb1＝Cc1＝Ca2＝Cb2＝Cc2。
Further, predicting the input reactive power Q (k +1) of the Quasi-Z source network at the time of the next control cycle k +1 comprises: measured value u of k time obtained by measurementabc(k) After the input reactive power prediction model 07 is subjected to three-phase abc-two-phase alpha beta coordinate transformation, a voltage component u under an alpha beta coordinate is obtainediα(k) And uiβ(k) (ii) a Q (k +1) is predicted by the following reactive power prediction calculation formula in the reactive power prediction model 07:
Q(k+1)＝uiα(k)iL1β(k+1)-uiβ(k)iL1α(k+1)
wherein iL1α(k +1) and iL1βThree-phase input current i of Quasi-Z source network with (k +1) as k +1 momentL1abc(k +1) component in α β coordinate, iL1abc(k +1) forecasting by a reactive power forecasting model according to a three-phase input current forecasting calculation formula of the Quasi-Z source network at the k +1 moment shown in the following table:
wherein iL1(k+1)＝iL1abc(k+1)，iL1(k)＝iL1abc(k)，u'(k+1)＝u'abc(k+1)，ui(k)＝uabc(k)，TsFor controlling the period, L is a Quasi-Z source network inductor La1、Lb1、Lc1、La2、Lb2And Lc2，La1＝Lb1＝Lc1＝La2＝Lb2＝Lc2，RLIs a Quasi-Z source network inductor La1、Lb1、Lc1、La2、Lb2And Lc2Internal resistance of (2).
Further, the value i of the load current value of the Quasi-Z source indirect matrix converter at the time of the next control cycle k +1 in the alpha beta coordinate system is predictedsα(k +1) and isβ(k +1) includes: measuring the measured value i at the k momentABC(k) And uABC(k) The current prediction model 08 is input after three-phase abc-two-phase alpha beta coordinate transformation, and furthermore, a measured value i at the time kABC(k) And uABC(k) After current filtering and voltage filtering are respectively carried out, three-phase abc-two-phase alpha-beta coordinate transformation treatment is carried out; i is predicted by the following current prediction calculation formula in the current prediction model 08sα(k +1) and isβ(k+1)：
Figure BDA0001923185780000121
Figure BDA0001923185780000122
Wherein isα(k) And isβ(k) Is a load current iABC(k) Values in the α β coordinate system, Uα(k) And Uβ(k) Is a load voltage uABC(k) Value in the α β coordinate system, TsFor controlling the period, LLIs load inductance, R'LIs a load resistor.
Then, outputting the voltage u 'to the Quasi-Z source network at the time of k +1 of the next control cycle'abc(k +1), input reactive power Q (k +1) and value i of load current value in alpha beta coordinate systemsα(k +1) and isβThe predicted values of (k +1) are respectively given reference values u'* abc、Q*、i* sαAnd i* sβBy comparison, a cost function g is composed. The expression of the cost function g is as follows:
Figure BDA0001923185780000123
wherein λ is1、λ2、λ3、λ4、λ5And λ6Six weight factors are 0.2, 0.1 and 0.3, Q*＝0。
Then, the switching state S of the rectifier stage corresponding to each group of switching state vectors in the switching functionrecAnd inverter stage switching state SinvSubstituting a cost function g containing a predicted value and a given reference value, and taking a switch combination state corresponding to the switch state vector with the minimum value of the cost function g as the output of a prediction control strategy, wherein the output of the prediction control strategy comprises the following steps: Quasi-Z source network switch SxRectifier stage switch Sa,b,cAnd inverter stage switch SA,B,CControl signal g ofz、grecAnd ginv；
Finally, at the moment k +1, the output of the predictive control strategy is used for controlling each switch of the Quasi-Z source indirect matrix converter, namely the control signal gz、grecAnd ginvRespectively control Sx、Sa,b,cAnd SA,B,CThe switch state of (1).
According to the control method provided by the embodiment of the invention, the output voltage and the input reactive power of the Quasi-Z source network and the load current of the Quasi-Z source indirect matrix converter in the next control period are controlled by one closed-loop control, and complex vector operation, duty ratio synthesis or design of an additional control strategy is not needed. The control algorithm of the embodiment of the invention is simple and easy to realize digitally, and complex vector operation and duty ratio synthesis of the traditional control strategy are not needed; under the control algorithm provided by the embodiment of the invention, the voltage and current tracking reference value of the Quasi-Z source indirect matrix converter has the advantages of fast dynamic response and high steady-state precision.
Although the invention has been described in detail above with reference to a general description and specific examples, it will be apparent to one skilled in the art that modifications or improvements may be made thereto based on the invention. Accordingly, such modifications and improvements are intended to be within the scope of the invention as claimed.

Claims (7)

1. A model prediction control method of a Quasi-Z source indirect matrix converter is characterized by comprising the following steps:
measuring a plurality of voltage and current values of different nodes of the Quasi-Z source indirect matrix converter at the moment k;
establishing a switching function according to the corresponding relation between each switch combination state and each group of switch state vectors of the Quasi-Z source indirect matrix converter at the time k, and extracting a rectifier stage switch state S corresponding to each group of switch state vectorsrecAnd inverter stage switching state SinvWherein S isrec＝[Sap,Sbp,Scp]，Sinv＝[SAp,SBp,SCp]；
Voltage and current measured values at time k and rectifier stage switching state S obtained by measurementrecAnd inverter stage switching state SinvAnd predicting the output voltage u 'of the Quasi-Z source network at the time of k +1 of the next control cycle'abc(k +1), input reactive power Q (k +1) and value i of load current value in alpha beta coordinate systemsα(k +1) and isβ(k+1)；
Outputting the voltage u 'to the Quasi-Z source network at the time of k +1 of the next control cycle'abc(k +1), input reactive power Q (k +1) and value i of load current value in alpha beta coordinate systemsα(k +1) and isβThe predicted values of (k +1) are respectively given reference values u'* abc、Q*、i* sαAnd i* sβComparing to form a value function g;
the switching state S of the rectifier stage corresponding to each group of switching state vectors in the switching functionrecAnd inverter stage switching state SinvSubstituting a value function g containing a predicted value and a given reference value, and taking a switch combination state corresponding to a switch state vector which enables the value of the value function g to be minimum as the output of a prediction control strategy; and
at the moment of k +1, controlling each switch of the Quasi-Z source indirect matrix converter by using the output of a predictive control strategy;
the measuring of the voltage and current values of different nodes of the Quasi-Z source indirect matrix converter at the k moment comprises the following steps:
measuring the grid voltage u at time kabc(k)；
Measuring input current i of Quasi-Z source network at moment kL1abc(k)；
Measuring output voltage u 'of Quasi-Z source network at moment k'abc(k) (ii) a And
measuring load current i of Quasi-Z source indirect matrix converter at moment kABC(k) And a load voltage uABC(k)。
2. The method of claim 1, wherein the Quasi-Z source network output voltage u 'at time k +1 of a next control cycle is predicted'abc(k +1) includes:
measuring the measured value i at the k momentABC(k)、u'abc(k) And iL1abc(k) An input voltage prediction model;
the voltage prediction model predicts u 'according to a voltage prediction calculation formula shown in the table below'abc(k+1)：
Figure FDA0002223561710000021
Wherein u '(k +1) ═ u'abc(k+1)，u'(k)＝u'abc(k)，iL1(k)＝iL1abc(k)，i'o(k)＝Srec SinviABC(k)＝Srec Sinv[iA(k),iB(k),iC(k)]，TsFor controlling the period, C is a Quasi-Z source network capacitor Ca1、Cb1、Cc1、Ca2、Cb2And Cc2，Ca1＝Cb1＝Cc1＝Ca2＝Cb2＝Cc2。
3. The method of claim 2, wherein predicting the Quasi-Z source network input reactive power Q (k +1) at the time of the next control cycle k +1 comprises:
measured value u of k time obtained by measurementabc(k) After the input reactive power prediction model is subjected to three-phase abc-two-phase alpha-beta coordinate transformation, a voltage component u under an alpha-beta coordinate is obtainediα(k) And uiβ(k)；
Predicting Q (k +1) by the following reactive power prediction calculation formula in the reactive power prediction model:
Q(k+1)＝uiα(k)iL1β(k+1)-uiβ(k)iL1α(k+1)
wherein iL1α(k +1) and iL1βThree-phase input current i of Quasi-Z source network with (k +1) as k +1 momentL1abc(k +1) component in α β coordinate, iL1abc(k +1) forecasting by a reactive power forecasting model according to a three-phase input current forecasting calculation formula of the Quasi-Z source network at the k +1 moment shown in the following table:
Figure FDA0002223561710000031
wherein iL1(k+1)＝iL1abc(k+1)，iL1(k)＝iL1abc(k)，u'(k+1)＝u'abc(k+1)，ui(k)＝uabc(k)，TsFor controlling the period, L is a Quasi-Z source network inductor La1、Lb1、Lc1、La2、Lb2And Lc2，La1＝Lb1＝Lc1＝La2＝Lb2＝Lc2，RLIs a Quasi-Z source network inductor La1、Lb1、Lc1、La2、Lb2And Lc2Internal resistance of (2).
4. The method according to claim 1, characterized by predicting the value i of the load current value of the Quasi-Z source indirect matrix converter at the time of the next control cycle k +1 in the α β coordinate systemsα(k +1) and isβ(k +1) includes:
measuring the measured value i at the k momentABC(k) And uABC(k) Inputting a current prediction model after three-phase abc-two-phase alpha beta coordinate transformation;
predicting i by the following current prediction calculation formula in the current prediction modelsα(k +1) and isβ(k+1)：
Figure FDA0002223561710000032
Wherein isα(k) And isβ(k) Is a load current iABC(k) Values in the α β coordinate system, Uα(k) And Uβ(k) Is a load voltage uABC(k) Value in the α β coordinate system, TsFor controlling the period, LLIs load inductance, R'LIs a load resistor.
5. The method of claim 1, wherein the cost function g is expressed as:
Figure FDA0002223561710000034
wherein λ is1、λ2、λ3、λ4、λ5And λ6Six weight factors are 0.2, 0.1 and 0.3, Q*＝0。
6. The method of claim 1, wherein the correspondence between the respective switch combination states and the respective sets of switch state vectors of the Quasi-Z source indirect matrix converter comprises:
each group of switch state vectors comprises 10 rectifier stage current vectors I1To I10And 8 inverter stage voltage vectors U0To U7Wherein the current vector I of the rectifier stage1To I6Is 6 effective vectors, I7To I9Is 3 zero vectors, I10Is 1 direct zero vector, voltage vector U1To U6Is 6 effective vectors, U0And U7Is 2 zero vectors;
according to 10 rectifier stage current vectors I1To I10And 8 inverter stage voltage vectors U0To U7Switching Quasi-Z source network SxRectifier stage switch Sa,b,cAnd inverter stage switch SA,B,CThe switch states of (a) form a correspondence as shown in the following table:
Figure FDA0002223561710000041
Figure FDA0002223561710000051
Figure FDA0002223561710000061
where 1 indicates that the switch is on and 0 indicates that the switch is off.
7. The method of claim 1, wherein the output of the predictive control strategy comprises: Quasi-Z source network switch SxRectifier stage switch Sa,b,cAnd inverter stage switch SA,B,CControl signal g ofz、grecAnd ginv。
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