CN109412440B - Carrier phase-shifting SVPWM (space vector pulse width modulation) method suitable for line voltage cascaded triple converter - Google Patents

Carrier phase-shifting SVPWM (space vector pulse width modulation) method suitable for line voltage cascaded triple converter Download PDF

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CN109412440B
CN109412440B CN201710927377.5A CN201710927377A CN109412440B CN 109412440 B CN109412440 B CN 109412440B CN 201710927377 A CN201710927377 A CN 201710927377A CN 109412440 B CN109412440 B CN 109412440B
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CN109412440A (en
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王志强
于安波
夏长亮
左志文
姚欢
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Tianjin Polytechnic University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/493—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode the static converters being arranged for operation in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H02M7/53873—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

The invention belongs to the field of power electronic circuit control, and relates to a carrier phase shift PWM (pulse-width modulation) method suitable for a line voltage cascade type triplex converter. The method can be applied to the fields of motor speed regulation, renewable energy power generation and the like, and has the advantages of effectively reducing the problem of overlarge current of a unit-to-unit connection loop caused by the traditional carrier phase-shifting SVPWM, removing a large number of non-ideal switching states and reducing voltage spikes and harmonic waves on the alternating current side; and the direct current bus voltage utilization effect which can be achieved by SVPWM is kept; meanwhile, the generated redundant switch state effectively reduces current harmonic waves by utilizing the carrier phase shift effect.

Description

Carrier phase-shifting SVPWM (space vector pulse width modulation) method suitable for line voltage cascaded triple converter
Technical Field
The invention belongs to the field of power electronic circuit control, and relates to a carrier phase shift PWM (pulse-width modulation) method suitable for a line voltage cascade type triplex converter, which can be applied to the fields of motor speed regulation, renewable energy power generation and the like.
Background
The application fields of power electronic technology in electric transmission and new energy power generation are continuously expanded, and the voltage and power levels faced by the power electronic technology are also continuously improved. And limited by the development speed of semiconductor technology, the voltage and power levels of a single semiconductor device are often difficult to adapt to some high-voltage and high-power occasions. If a high-voltage mine is lifted, the voltage of a motor terminal reaches more than 6kV, so that the voltage of a direct-current bus of a motor side inverter is required to reach more than 10kV, and the traditional two-level or even three-level structure is difficult to adapt. Therefore, scientific researchers at home and abroad form the converter with a multiple structure by recombining the two level modules. The patent provides a novel carrier phase-shifting SVPWM modulation method, and the method has the advantages that the redundant switch state brought by carrier phase shifting and the characteristic of the specific high direct current bus voltage utilization rate of SVPWM are fully utilized, and the line voltage harmonic content is reduced.
Disclosure of Invention
The invention aims to overcome the defects in the prior art and provides a carrier phase shift PWM (pulse-width modulation) modulation method suitable for a line voltage cascade type triple converter. The invention adopts the following technical scheme:
firstly, defining the number and phase sequence corresponding to each component unit in the line voltage cascade type triple converter; three phases of unit 1 are defined as a1, b1 and c1 phases respectively, and are 120 degrees different from each other, three phases of unit 2 are a2, b2 and c2 phases respectively, and are 120 degrees different from each other, and three phases of unit 3 are a3, b3 and c3 phases respectively, and are 120 degrees different from each other; selecting an a1 phase bridge arm of a unit 1 as an A phase bridge arm of the overall triplex converter, a B2 phase bridge arm of a unit 2 as a B phase bridge arm of the overall triplex converter, and a C3 phase bridge arm of a unit 3 as a C phase bridge arm of the overall triplex converter, and regarding the three bridge arms as a switch group which is marked as a switch group 1; taking the a2 phase bridge arm of the unit 2 as the A phase of a new switch group, the B1 phase bridge arm of the unit 1 as the B phase of the new switch group, the C2 phase bridge arm of the unit 2 as the C phase of the new switch group, and defining the new switch group as the switch group 2; taking the a3 phase bridge arm of the cell 3 as the A phase of another new switch group, the B3 phase bridge arm of the cell 3 as the B phase of the another new switch group, the C1 phase bridge arm of the cell 1 as the C phase of the another new switch group, and the switch group is marked as the switch group 3;
secondly, the switch group 1 can be regarded as a set of three-phase two-level topological structure, and modulated by adopting a two-level SVPWM method, and marked as an SVPWM calculation unit 1; for the switch group 2, a two-level SVPWM modulation method is also adopted and is marked as an SVPWM calculation unit 2, the modulation wave of the SVPWM calculation unit 2 is the same as that used by the SVPWM calculation unit 1, but the carrier wave lags behind 1/3 switching cycles; for the switch group 3, an SVPWM modulation method is also adopted, which is marked as an SVPWM calculation unit 3, and the modulation wave of the SVPWM3 is the same as that used by the SVPWM calculation unit 1, but the carrier wave lags behind 1/3 switching cycles; the digital control system can generate a corresponding SVPWM waveform according to the size relation between the modulation wave and the carrier wave;
influenced by the structural characteristics of the line voltage cascade type triple converter, wherein the method for acquiring the modulation wave in the two-level SVPWM is as follows:
the line voltage cascade type triple converter can be equivalent to a switching circuit, wherein the equivalent direct current bus voltage Udc，eqEqual to twice Uav，UavThe average value of the DC bus voltage corresponding to the three groups of power units is 2U for each SVPWM generating unitavAnd 3, as the module length of the coordinate axis in the space vector coordinate system, the control system obtains a reference voltage vector U according to the equivalent rear switch circuitrefAnd the three-phase modulated wave is multiplied by 1/2 to be used as a given reference voltage vector of each SVPWM generating unit, and then a group of three-phase modulated waves can be obtained.
The modulation mode effectively solves the problem of overlarge circuit current of the inter-unit connection loop caused by the traditional carrier phase-shifting SVPWM, removes a large number of non-ideal switching states, and reduces voltage spikes and harmonic waves on the alternating current side; the strategy keeps the direct current bus voltage utilization effect which can be achieved by SVPWM; meanwhile, the generated redundant switch state effectively reduces current harmonic waves by utilizing the carrier phase shift effect.
Drawings
FIG. 1: a line voltage cascade type triple converter topological diagram;
FIG. 2: the line voltage cascade type triple converter equivalent circuit;
FIG. 3: a carrier phase-shifting SVPWM modulated wave and a carrier map;
Detailed Description
The line voltage cascade type triple converter topology is shown in fig. 1. First, the unit number and the corresponding phase sequence number are defined. As shown in fig. 1, cell 1 corresponds to the three phases a1, b1, and c 1; cell 2 corresponds to three phases a2, b2 and c 2; cell 3 corresponds to three phases a3, b3 and c 3; l isfRepresenting the inductive load on the AC side, RloadRepresenting the resistive load on the AC side, LxRepresenting a current limiting inductance; i.e. iARepresenting the inverter output current, i, of phase A of the converterBRepresenting the B-phase inverted output current, i, of the converterCRepresenting the C-phase inverse output current of the converter; u shapedc1、Udc2And Udc3The dc supply voltages 1, 2 and 3, respectively.
Firstly, the a1 phase is the A phase of the triple converter, the B2 phase is the B phase of the triple converter, and the C3 phase is the C phase of the triple converter, and the three phases form the switch group 1. Similarly, the a2 phase bridge arm of the unit 2 is selected as the a phase of a new switch group, the B1 phase bridge arm of the unit 1 is the B phase of the new switch group, the C2 phase bridge arm of the unit 2 is the C phase of the new switch group, and the new switch group is defined as the switch group 2; the a3 phase bridge arm of the cell 3 is selected as the A phase of another new switch group, the B3 phase bridge arm of the cell 3 is the B phase of the another new switch group, the C1 phase bridge arm of the cell 1 is the C phase of the another new switch group, and the switch group is marked as the switch group 3.
Secondly, analyzing a circuit loop formed by the loop 1 in the figure 1, and writing kirchhoff voltage loop equations in parallel:
UAB＝Ua1b1+Ua2b2+Ub1a2＝(Rload+jωLf)(IA-IB) (1)
in the formula of UABIs the AC side A, B phase line voltage phasor of the triple convertera1b1Is the phase quantity of the line voltage between the alternating current sides a1 and b1 of the unit 1 in the triple converter, Ua2b2Is the AC side a2, b2 interphase voltage phasor, U of the unit 2 in the triple converterb1a2Is the voltage phasor across the current limiting inductance between unit 1 and unit 2; omega is the voltage vector rotation electrical angular velocity provided by the inverter power supply, and j represents an imaginary number unit; i isAIs the phase of the phase current, IBIs phase B current phasor. The same way can be used to obtain the voltage loop equations of the other two phases:
Figure GSB0000190322950000021
in the formula of UBCIs the AC side B, C phase line voltage phasor of the triple converterCAIs the phase line voltage phasor between the ac side C, A of the triplex converter; u shapeb2c2Is the alternating-current side b2 and c2 interphase voltage phasor, U of the unit 2 in the triple converterb3c3Is the alternating-current side b3 and c3 interphase voltage phasor U of the unit 3 in the triple converterc2b3Is a unit2, and 3, voltage phasor on a current-limiting inductor between the unit and the unit; u shapec3a3Is the alternating-current side c3 and a3 phase line voltage phasor U of the unit 3 in the triple converterc1a1Is the alternating-current side c1 and a1 interphase voltage phasor U of the unit 1 in the triple convertera3c1Is the voltage phasor across the current limiting inductance between unit 2 and unit 1; i isCIs the phase C phase current phasor.
From the above analysis, an equivalent three-phase switching circuit can be obtained, as shown in fig. 2. In the figure, LfxIs equivalent alternating-current side inductance, and the expression is
Figure GSB0000190322950000031
In the formula, kLIs LfAnd LxTo a ratio of (i) to (ii)
Figure GSB0000190322950000032
Because the voltage of the alternating-current side wire of the equivalent switch circuit is equal to the sum of the voltages of two adjacent cascaded VSC unit wires, the equivalent direct-current bus voltage Udc，eqEqual to twice Uav，UavRepresenting the mean value of 3 DC bus voltages, i.e.
Figure GSB0000190322950000033
The triple LVC-VSC adopts 3 SVPWM calculating units which are respectively named as an SVPWM calculating unit 1, an SVPWM calculating unit 2 and an SVPWM calculating unit 3; which correspond to switch set 1, switch set 2 and switch set 3, respectively. When the phase-shifting SVPWM is carried out for modulation, the equivalent direct current bus voltage U is generateddc，eqEqual to twice UavEach SVPWM generating unit adopts 2UavThe/3 is used as the module length of the coordinate axis in the space vector coordinate system, and the control system obtains the reference voltage vector UrefThen, 1/2 are multiplied to be used as a given reference voltage vector of each SVPWM generating unit,thereby obtaining a set of three-phase modulated waves.
In addition, the invention uses the idea of carrier phase shift, the SVPWM calculating unit 1 is marked as carrier 1, and the carrier phases corresponding to the SVPWM calculating unit 2 and the calculating unit 3 lag behind the carrier 11/3 carrier periods, namely Ts/3, carrier 2 is obtained, where TsIs the carrier period. The phase relationship between the modulated wave of the arm on the a-phase corresponding to each switch group and the 3 groups of carriers is shown in fig. 3. The digital control system can generate a corresponding SVPWM waveform according to the size relation between the modulation wave and the carrier wave.

Claims (1)

1. A carrier phase shift SVPWM modulation method suitable for a line voltage cascade type triple converter is characterized in that firstly, numbers and phase sequences corresponding to all constituent units in the line voltage cascade type triple converter are defined; three phases of unit 1 are defined as a1, b1 and c1 phases respectively, and are 120 degrees different from each other, three phases of unit 2 are a2, b2 and c2 phases respectively, and are 120 degrees different from each other, and three phases of unit 3 are a3, b3 and c3 phases respectively, and are 120 degrees different from each other; selecting an a1 phase bridge arm of a unit 1 as an A phase bridge arm of the overall triplex converter, a B2 phase bridge arm of a unit 2 as a B phase bridge arm of the overall triplex converter, and a C3 phase bridge arm of a unit 3 as a C phase bridge arm of the overall triplex converter, and regarding the three bridge arms as a switch group which is marked as a switch group 1; taking the a2 phase bridge arm of the unit 2 as the A phase of a new switch group, the B1 phase bridge arm of the unit 1 as the B phase of the new switch group, the C2 phase bridge arm of the unit 2 as the C phase of the new switch group, and defining the new switch group as the switch group 2; taking the a3 phase bridge arm of the cell 3 as the A phase of another new switch group, the B3 phase bridge arm of the cell 3 as the B phase of the another new switch group, the C1 phase bridge arm of the cell 1 as the C phase of the another new switch group, and the switch group is marked as the switch group 3;
secondly, the switch group 1 can be regarded as a set of three-phase two-level topological structure, and modulated by adopting a two-level SVPWM method, and marked as an SVPWM calculation unit 1; for the switch group 2, a two-level SVPWM modulation method is also adopted and is marked as an SVPWM calculation unit 2, the modulation wave of the SVPWM calculation unit 2 is the same as that used by the SVPWM calculation unit 1, but the carrier wave lags behind 1/3 switching cycles; for the switch group 3, an SVPWM modulation method is also adopted, which is marked as an SVPWM calculation unit 3, and the modulation wave of the SVPWM3 is the same as that used by the SVPWM calculation unit 1, but the carrier wave lags behind 1/3 switching cycles; the digital control system can generate a corresponding SVPWM waveform according to the size relation between the modulation wave and the carrier wave;
the method is influenced by the structural characteristics of the line voltage cascade type triple converter, wherein the method for acquiring the modulation wave in the two-level SVPWM is concretely as follows, the line voltage cascade type triple converter can be equivalent to a switching circuit, and the equivalent direct-current bus voltage Udc，eqEqual to twice Uav，UavThe average value of the DC bus voltage corresponding to the three groups of power units is 2U for each SVPWM generating unitavAnd 3, as the module length of the coordinate axis in the space vector coordinate system, the control system obtains a reference voltage vector U according to the equivalent rear switch circuitrefAnd the three-phase modulated wave is multiplied by 1/2 to be used as a given reference voltage vector of each SVPWM generating unit, and then a group of three-phase modulated waves can be obtained.
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CN102739086A (en) * 2012-06-18 2012-10-17 天津工业大学 Method for controlling triple line-voltage cascaded (LVC) converter based on equivalent circuit model
CN104270023A (en) * 2014-06-23 2015-01-07 中国矿业大学(北京) Harmonic optimization and modulation method of multi-level converter
CN105915089A (en) * 2016-05-06 2016-08-31 浙江大学 MMC capacitor voltage equalization control method based on driving signal logic processing

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CN104270023A (en) * 2014-06-23 2015-01-07 中国矿业大学(北京) Harmonic optimization and modulation method of multi-level converter
CN105915089A (en) * 2016-05-06 2016-08-31 浙江大学 MMC capacitor voltage equalization control method based on driving signal logic processing

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