CN109347326A - Primary side constant-current control device and compensating current signal extracting method - Google Patents
Primary side constant-current control device and compensating current signal extracting method Download PDFInfo
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- CN109347326A CN109347326A CN201811057681.XA CN201811057681A CN109347326A CN 109347326 A CN109347326 A CN 109347326A CN 201811057681 A CN201811057681 A CN 201811057681A CN 109347326 A CN109347326 A CN 109347326A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses primary side constant-current control device and compensating current signal extracting method, the primary side constant-current control device includes equivalent output current module；Equivalent output current module receives the signal of the transformer both ends winding voltage of reflection converter and the primary side resonance current signal of converter, generates the first resonance section average current signal Vpri1_avgWith compensating current signal Vpri2_avg, the first resonance section average current signal Vpri1_avgWith compensating current signal Vpri2_avgThe output current equivalence signal V of output reflection output current average after being addedIo_est；The present invention can eliminate optocoupler and secondary side feedback circuit, effectively increase the reliability of circuit.In addition, primary side constant-current control device can further be integrated into single-chip, circuit cost is further decreased.
Description
Technical field
The invention belongs to the switch power technologies in power electronics field, are related to a kind of suitable for LLC resonant transformation
The primary side constant-current control device of device or other type controlled resonant converters.
Background technique
In recent years, the features such as light emitting diode (LED) is with its high brightness, long-life, high efficiency, has been widely used in day
Often in life, to substitute traditional lighting apparatus: incandescent lamp, fluorescent lamp and metal halide lamp etc..However, LED belongs to directly
Flow pattern load, and its light emission luminance depends directly on the forward current for flowing through LED.Therefore, in order to guarantee LED light light emission luminance
Consistency generallys use constant-current source driving.
Based on the consideration of lighting apparatus safety, many LED lamps require LED driver that must have isolating device, with reality
The electrical isolation of existing power grid input and converter output.Therefore, in small power LED illumination equipment, low cost is generallyd use
The power circuit design of single-stage reverse exciting topological realization LED driver.Circuit of reversed excitation is not only able to achieve the conversion of alternating current-direct current energy, together
When can realize the electrical isolation of transformer primary vice-side winding.The high-power field in, then generally use the topological structure of two-stage type.
As shown in Figure 1, prime generallys use boosting (Boost) circuit as PFC, to realize the conversion of alternating current-direct current energy simultaneously
Export stable DC voltage；Rear class improves the output electric current of LED light using efficient LLC half bridge resonant, and realizes
The electrical isolation of LED lamp equipment.
However, traditional LLC resonant converter generallys use optocoupler and samples to output to realize that stablizing for electric current exports
Carry out feedback control.Fig. 2 describes the control block diagram of traditional optocoupler negative-feedback, by being sampled to outlet side LED current, with
The current reference value adjusted in ring moulds block is compared, and output closed-loop adjustment signal is simultaneously transmitted to LLC resonant transformation by optocoupler
The drive control module of device primary side, the switching frequency by changing LLC resonant converter realize constant current output.But it is
Realize isolation feedback use optocoupler there are problem of aging, influence the stability of circuit, and reduce equipment electrically every
From intensity.
Therefore, research the primary side constant-current control device based on LLC resonant converter be one very have practical significance and
The work of challenge.
Summary of the invention
The purpose of the present invention is in view of the deficiencies of the prior art, propose a kind of primary side suitable for LLC resonant converter
Constant-current control device.The present invention to LLC resonant converter work continuous mode (Continuous Conduction Mode,
Abbreviation CCM) and be applicable in when discontinuous mode (Discontinuous Conduction Mode, abbreviation DCM) simultaneously, pass through primary side
Current constant control exports constant, high-precision secondary current.
Primary side constant-current control device of the present invention includes: equivalent output current module, adjusts ring moulds block, drive control module.
Equivalent output current module receives the signal and converter of the transformer both ends winding voltage of reflection converter
Primary side resonance current signal generates the first resonance section average current signal Vpri1_avgWith compensating current signal Vpri2_avg, first
Resonance section average current signal Vpri1_avgWith compensating current signal Vpri2_avgOutput reflection output current average after being added
Output current equivalence signal VIo_est。
First resonance section average current signal Vpri1_avgBy the primary side resonance current signal in the first resonance section
It is obtained by the modes such as shaping, average.
The compensating current signal Vpri2_avgPass through shaping according to the primary side resonance current signal in the second resonance section, put down
The second resonance section average current signal that impartial mode obtainsReflect the transformer winding electricity in the first resonance section
Press the signal of average amplitudeWith the signal of the transformer winding average voltage amplitude in the second resonance section of reflectionBy
Corresponding relationshipIt obtains.
When the secondary side rectifying tube conducting of first resonance section correspondent transform device, the resonant inductance and resonant capacitance of primary side
The section of resonance occurs, which all exists in continuous current mode and discontinuous conduct mode；Second resonance section is corresponding
When converter pair side rectifying tube turns off, the area of resonance occurs for resonant inductance, resonant capacitance and the static exciter inductance of primary side
Between, which only exists under discontinuous conduct mode.
Wherein, under continuous current mode, first resonance section average current signal Vpri1_avgEquivalent it can reflect defeated
Current average out, the compensating current signal Vpri2_avgIt is zero；Under discontinuous conduct mode, first resonance section is average
Current signal Vpri1_avgApproximation reflection output current average, the compensating current signal Vpri2_avgReflect first resonance
Section average current signal Vpri1_avgWith the error amount between equivalent output electric current.
Preferably, first resonance section and the second resonance section can reflect transformer both ends winding voltage by detection
Signal obtain.
Preferably, the equivalent output current module receives the letter of the transformer winding both end voltage information of reflection converter
Number and sampling primary side resonance current signal；According to transformer winding polarity of voltage to the primary side resonance current signal of sampling into
Row shaping: primary current sampled signal is directly transmitted in transformer winding positive polarity section, and by it in transformation
Device winding voltage negative polarity section carries out polarity upset, and the signal after above-mentioned direct transmission and polarity upset obtains after reconfiguring
Obtain primary current reshaping signal；Thereafter primary current reshaping signal is resolved by the first resonance section electric current letter according to time interval
Number and the second resonance section current signal；It is flat that the first resonance section of acquisition is averaging processing to the first resonance section current signal
Equal current signal Vpri1_avg；Second resonance section current signal is averaging processing and obtains the second resonance section average current letter
Number Vpri2_avg。
Preferably, the equivalent output current module receives the letter of the transformer winding both end voltage information of reflection converter
Number and sampling primary side resonance current signal；The primary side resonance current signal is resolved into the first resonance according to time interval
Section current signal and the second resonance section current signal；The first resonance section electric current is believed according to transformer winding polarity of voltage
Number carry out shaping: the first resonance section current signal is directly transmitted in transformer winding positive polarity section, and incite somebody to action
First resonance section current signal carries out polarity upset in transformer winding voltage negative polarity section；Above-mentioned direct transmission and polarity
Waveform after overturning reconfigure and be averaging processing or average treatment after be added that obtain the first resonance section average again
Current signal Vpri1_avg；Shaping is carried out to the second resonance section current signal according to transformer winding polarity of voltage: humorous by second
Vibration section current signal is directly transmitted in transformer winding positive polarity section, and the second resonance section current signal is existed
Transformer winding voltage negative polarity section carries out polarity upset；Signal after above-mentioned direct transmission and polarity upset reconfigures
And be averaging processing or average treatment after be added again obtain the second resonance section average current signal Vpri2_avg。
Preferably, the primary side constant-current control device further includes adjusting ring moulds block, is adjusted described in the input termination of ring moulds block
The output end of equivalent output current module, for exporting current equivalence signal V based on the receivedIo_estWith its internal base being arranged
Standard relatively, and generates error amplification signal V after the amplification of compensated networkcomp。
Preferably, the primary side constant-current control device further includes drive control module, the input termination of drive control module
The output end for adjusting ring moulds block, for generating its output frequency by VcompThe duty ratio of control close to 50%, two-by-two it is complementary,
There are the multichannel complementary drive signals of certain dead time.
Preferably, the equivalent output current module includes comparison module, sample rate current Shaping Module, winding voltage rectification
Module, the second resonance interval time detection module, the first resonance section current draw and averaging module, compensating proportion calculate mould
Block compensates current calculation module and adder.
The input terminal of comparison module receives the voltage signal of the transformer T winding voltage information of reflection LLC resonant converter
Vaux, output reflection VauxThe pulse signal V in positive-negative polarity sectionpAnd Vn。
The first input end of sample rate current Shaping Module receives the primary current sampled signal V of LLC resonant converterir,
Second input terminal and third input terminal connect the first output end and second output terminal of the comparison module, sample rate current overturning respectively
Module is first according to reflection VauxThe pulse signal V in positive-negative polarity sectionpAnd Vn, by primary current sampled signal VirIn VauxAnode
The waveform in property section is directly transmitted, and by it in VauxThe polarity of wave in negative polarity section is overturn, to obtain primary current
Sampled signal VirSignal V after shapingir_rec。
The input terminal of winding voltage rectification module receives LLC resonant converter transformer T auxiliary winding WaIt sends
Voltage signal Vaux, the second input terminal and third input terminal connect the first output end of the comparison module and second respectively and export
End, for VauxWaveform rectified, export VauxSignal V after rectificationaux_rec。
The input of second resonance interval time detection module terminates the output end of the winding voltage rectification module, output
Hold output pulse signal Vg_DCM.Second resonance interval time detection module is for detecting the second resonance interval time, pulse signal
Vg_DCMHigh level reflect the second resonance interval time.
The output of the first input end of first resonance section current draw and averaging module reception sample rate current flip module
Signal, the second input terminal receive the pulse signal V of the second resonance interval time detection module outputg_DCM, export the first resonance region
Between average current signal Vpri1_avg.Under continuous current mode, first resonance section average current signal Vpri1_avgIt can wait
Effect reflection output current average, under discontinuous conduct mode, first resonance section average current signal Vpri1_avgIt is approximate
Reflection output current average, there is a certain error for the two.
The first input end of compensating proportion computing module connects the output end of the second resonance interval time detection module, and second
The output end of input termination winding voltage rectification module, reflects the pulse signal V of the second resonance interval time based on the receivedg_DCM
With the signal V after transformer auxiliary winding voltage signal rectificationaux_recObtain compensating proportion pulse signal Vg_com。
The first input end of compensation current calculation module connects the output end of sample rate current Shaping Module, the second input termination
The output end of second resonance interval time detection module, the output end of third input termination compensating proportion computing module, according to
Received primary current sampled signal VirSignal V after shapingir_rec, reflection the second resonance interval time pulse signal Vg_DCM
With compensating proportion pulse signal Vg_comObtain compensating current signal Vpri2_avg.The compensating current signal Vpri2_avgFor compensating
In the first resonance section average current signal Vpri1_avgWith output current average between error, under continuous current mode,
Due to Vir_rec2Equal to zero, compensating current signal Vpri2_avgEqual to zero.
The first input end of adder connects the output end of first resonance section current draw and averaging module, and second
The output end of the input termination compensation current calculation module, is used for the first resonance section average current signal Vpri1_avgWith benefit
Repay current signal Vpri2_avgIt is overlapped, the output current equivalence signal V of output reflection average eguivalent output electric currentIo_est。
Preferably, the similar structures of the integrated control chip of the prior art can be used in drive control module, realize to switch
The pulse frequency of pipe controls and increases switch driving capability, belongs to this professional skill field well-known technique.
Preferably, the primary side constant-current control device can constitute primary side constant-current device with converter, and the converter is to pass
LLC half bridge resonant, full-bridge LLC resonant converter or the other types of controlled resonant converter of system.
A kind of compensating current signal extracting method comprising the steps of:
1) the primary side resonance current signal V of oversampled converterir；
2) shaping is carried out according to primary side resonance current signal of the transformer winding polarity of voltage of converter to sampling: will be former
Side current sampling signal VirWaveform in transformer winding positive polarity section is directly transmitted, and by its transformer around
The polarity of wave overturning in group voltage negative polarity section, primary current sampled signal are directly transmitted with the waveform of polarity upset again
The signal V after shaping is obtained after combinationir_rec；
3) according to the signal V after shapingir_recObtain its signal V being within the second resonance sectionir_rec2；
4) signal V is obtainedir_rec2Average value
5) signal of the transformer winding voltage of extraction reflection converter in the average amplitude in the first resonance sectionAnd
Signal of the transformer winding voltage of reflection converter in the average amplitude in the second resonance section
6) according to formulaObtain compensating current signal Vpri2_avg。
A kind of compensating current signal extracting method, the method comprise the steps of:
1) the primary side resonance current signal V of oversampled converterir；
2) primary side resonance current signal V is obtainedirSignal V within the second resonance sectionir2；
3) according to the transformer winding polarity of voltage of converter to the signal V of samplingir2Carry out shaping: by signal Vir2Becoming
The waveform in depressor winding voltage positive polarity section is directly transmitted, and by its wave in transformer winding voltage negative polarity section
Shape polarity upset, the directly waveform of transmission and polarity upset obtain the signal V after shaping after reconfiguringir_rec2；
4) signal V is obtainedir_rec2Average value
5) signal of the transformer winding voltage of extraction reflection converter in the average amplitude in the first resonance sectionAnd
Signal of the transformer winding voltage of reflection converter in the average amplitude in the second resonance section
6) according to formulaObtain compensating current signal Vpri2_avg。
Preferably, the step of compensating current signal extracting method and on-fixed, some of sequence of steps can be adjusted
Whole or exchange.
The beneficial effects of the present invention are: primary side constant-current control device proposed by the present invention is not necessarily to optocoupler and secondary side feedback
The high-precision output constant current control of LLC resonant converter can be realized in circuit.Primary side constant-current control device of the invention is fitted simultaneously
For LLC resonant converter work under CCM and DCM mode, the scope of application is unrestricted.Therefore traditional LLC resonance is compared
Convertor device such as LLC LED driver, the present invention can eliminate optocoupler and secondary side feedback circuit, and effectively increase circuit can
By property.In addition, primary side constant-current control device can further be integrated into single-chip, circuit cost is further decreased.
Detailed description of the invention
Fig. 1 is traditional AC-DC two-stage type LED driver that rear class uses LLC half bridge resonant；
Fig. 2 is control block diagram of the LLC half bridge resonant using secondary side light-coupled isolation negative-feedback；
Fig. 3 is primary current waveform when LLC resonant converter is applied under the symmetrical continuous current mode of current waveform；
Fig. 4 is primary current waveform when LLC resonant converter is applied under the symmetrical discontinuous conduct mode of current waveform；
Fig. 5 is that the primary side constant current that primary side constant-current control device of the invention and a kind of LLC half bridge resonant are constituted fills
Set control block diagram；
Fig. 6 is a specific embodiment based on primary side constant-current control device control block diagram of the invention shown in fig. 5；
Fig. 7 is a specific embodiment of primary side constant-current control device of the invention shown in fig. 6 in the continuous situation of electric current
Under main waveform；
Fig. 8 is a specific embodiment of primary side constant-current control device of the invention shown in fig. 6 in discontinuous current situation
Under main waveform；
Fig. 9 is primary side constant-current control device of the invention and the primary side constant current dress that a kind of full-bridge LLC resonant converter is constituted
Set specific embodiment schematic diagram.
Specific embodiment
The present invention realizes the output constant current control of LLC resonant converter using primary side feedback control technology, for converter
Work is all applicable under the conditions of continuous current mode or discontinuous mode, the continuous current mode of the LLC resonant converter or disconnected
Discontinuous Conduction mode belongs to well-known technique for this professional skill field.Embodiment of the present invention is suitable for LLC resonant converter electric current
The case where waveform symmetry or near symmetrical.
The principle of the primary side constant current of LLC resonant converter proposed by the present invention is analyzed first.
When LLC resonant converter is applied under the symmetrical continuous current mode of current waveform, primary current waveform such as Fig. 3
It is shown.Under the symmetrical continuous mode of current waveform, since the waveform of every half of switch periods is identical, it can be opened with half
The pass period is analyzed
According to output electric current IoRelationship between primary side resonance current can do following derivation:
Wherein, niFor transformer T primary side winding WpWith vice-side winding WsThe ratio between the number of turns；TsFor the switch periods of switching tube,
ir_rec(t) and im_rec(t) be primary side resonance current and exciting current overturn through the half period after waveform.
In conjunction with Fig. 3 and formula (1) it is found that in half of switch periods, electric current I is exportedoWith ir_recAnd im_recDifference it is flat
Mean value is directly proportional.In actual circuit, ir_recIt can directly sample and overturn to obtain through logic circuit, im_recIt but can not be direct
It obtains.
As shown in figure 3, when the work of LLC topology is in the case where stablizing output condition, im_recHave in half of switch periods symmetrical
Starting point current value-ImWith terminal current value Im, i.e.-im_rec(0)=im_rec(Tr/2).Therefore right in half of switch periods
The dash area S answeredm1And Sm2Area having the same, i.e. Sm1=Sm2.Further, according to integral principle:
It in conjunction with formula (1) and (2), can finally obtain under continuous mode, export the expression formula of electric current:
Therefore under the symmetrical continuous current mode of current waveform, due to exciting current i in LLC resonant convertermPair
Claim characteristic, the exciting current i in half of switch periodsmPositive and negative area can cancel out each other, so can by sampling LLC primary side it is humorous
Shake electric current ir, reflection output electric current I can be obtained by being overturn to the signal sampled and extracting average valueoThe signal of variation.
When the present invention be applied to the symmetrical discontinuous conduct mode of current waveform under the conditions of when, primary current waveform and auxiliary around
Group waveform VauxAs shown in Figure 4.Resonance current waveform variation in half of switch periods is included as two parts:
(1) first resonance section [0, Tr/2]∪[Ts/ 2, Ts/2+Tr/ 2]: resonance current irWith exciting current imWork shape
It is consistent under the conditions of state and continuous mode.
(2) second resonance section [Tr/ 2, Ts/2]∪[Tr/2+Ts/ 2, Ts]: output diode disconnects, resonant inductance LrWith
Magnetizing inductance LmWith resonant capacitance CrResonance, exciting current i occursmSlope change with respect to the first resonance section, resonance electricity
Flow irWith exciting current imIt is equal.
Wherein, TrFor resonant inductance LrWith resonant capacitance CrCorresponding harmonic period.Under current waveform symmetric case,
Since the waveform of every half of switch periods is identical, can be analyzed with half of switch periods.
Export electric current IoRelationship between primary current can be indicated with equation (4).
According to auxiliary winding voltage VauxWaveform, can effectively extract the first resonance section [0, Tr/ 2] primary current
Waveform.But im_recInitial current and TrThe current amplitude at/2 moment is no longer equal, i.e.-im_rec(0)≠im_rec(Tr/2).Cause
This, the i in half of harmonic periodm_recAverage value is no longer zero.
Further, if vacation im_recIn TrCurrent changing rate, which remains unchanged, after/2 moment continues growing, in Tr/2+T1When
Reach maximum value I quarterm, i.e. im_rec(Tr/2+T1)=Im.As shown in Figure 4, im_recAverage value is not zero in the first resonance section
The reason of be to have lacked [Tr/ 2, Tr/2+T1] section area S1。S1Average value such as formula (5) institute in half of switch periods
Show:
im_recIn the second resonance section [Tr/ 2, Ts/ 2] the area S in2In half of switch periods average value such as formula (6) institute
Show:
Wherein, T2=Ts/2-Tr/2.Equation (7) can be further derived in conjunction with formula (5) and (6):
In the first resonance section [0, Tr/ 2], full-wave rectification diode D is exported1And D2Conducting, primary side winding WpBoth end voltage
It is clamped at niVo.In the second resonance section [Tr/ 2, Ts/ 2], full-wave rectification diode D is exported1And D2Conducting shutdown, transformer
Magnetizing inductance Lm, resonant inductance LrAnd resonant capacitance CrResonance, static exciter inductance LmBoth end voltage is transformer primary side
Winding WpBoth end voltage, transformer primary winding WpBoth end voltage is lower than niVo.Since this interval time is shorter, corresponding transformation
Device primary side winding voltage change is smaller, therefore approximate the transformer primary winding average voltage in the section can be taken as this area
Between voltage value.With reference to Fig. 4, ignore the influence of transformer winding leakage inductance, further according to transformer magnetizing current imWith transformer around
The corresponding relationship of group voltage can obtain:
Wherein,WithRespectively transformer auxiliary winding WaBoth end voltage in the first resonance section [0, Tr/ 2] and
Second resonance section [Tr/ 2, Ts/ 2] average value in.By formula (7) and (8)) it can obtain:
Therefore, the average current value for needing to compensate in half of switch periods are as follows:
It may further obtain exporting electric current I under discontinuous operating modeoWith resonance current irRelational expression such as formula (11) institute
Show:
In summary it derives, combining target equation expression formula (3) and (11) are, it can be achieved that the LLC with asymmetrical current waveform
The current constant control of controlled resonant converter secondary side output electric current under continuous current mode and discontinuous mode.Further, according to above-mentioned right
The analysis of LLC resonant converter with asymmetrical current waveform, can it can be found that when converter works in continuous current mode
With by directly sample primary side resonance current waveform overturn and be averaged after obtain output current average information, and when change
Parallel operation works in discontinuous conduct mode, can pass through the exciting current i after the overturning in the second resonance section of extractionm_recTo direct
The primary side resonance current waveform of sampling, which is overturn and obtained after being averaged after output current average compensates, obtains output electricity
The information of levelling mean value.Based on above-mentioned thought, the invention proposes a kind of primary side constant-current control devices for realizing the change of LLC resonance
Parallel operation exports the constant control of electric current under continuous current mode and discontinuous mode.
The original that primary side constant-current control device of the invention and a kind of LLC half bridge resonant with reference to shown in Fig. 5 are constituted
Side constant-current device embodiment connection schematic diagram, the LLC half bridge resonant include: input capacitance Cin, primary side switch pipe Q1
And Q2, resonant inductance Lr, resonant capacitance Cr, transformer T, full-wave rectification output diode D1And D2And output capacitance Co, described
Transformer T includes at least a primary side winding Wp, the first vice-side winding Ws1, the second vice-side winding Ws2With auxiliary winding Wa, two
Vice-side winding has identical the number of turns.Input capacitance CinOne termination primary side switch bridge arm switching tube Q1Drain electrode, input capacitance Cin
An another end meet primary side switch bridge arm switching tube Q2Source electrode, primary side winding WpOne end and ground, primary side switch bridge arm switching tube Q1
Source electrode meet primary side switch bridge arm switching tube Q2Drain electrode and resonant inductance LrOne end, primary side switch bridge arm switching tube Q1With open
Close pipe Q2Grid meet driving signal V respectivelyg1And Vg2, resonant inductance LrAnother termination resonant capacitance CrOne end, resonance electricity
Hold CrAnother termination primary side winding WpThe other end, auxiliary winding WaOne end output reflection primary side winding voltage change letter
Number Vaux, auxiliary winding WaAnother termination primary side, vice-side winding WsOne termination output diode D1Anode, vice-side winding
WsAnother termination output diode D2Anode, vice-side winding WsCentre cap meet output capacitance CoOne end and secondary side,
Output diode D1Cathode meet output diode D2Cathode and output capacitance CoThe other end.
100 block diagram of primary side constant-current control device of the invention referring to shown in Fig. 5, primary side constant-current control device of the invention
100 include: equivalent output current module 101, adjusting ring moulds block 102, drive control module 103.
Equivalent output current module 101 receives the signal of the both ends winding voltage of the transformer T of reflection LLC resonant converter
And the primary side resonance current sampled signal of LLC resonant converter, the output electric current etc. of output reflection average eguivalent output electric current
Imitate signal VIo_est。
The output end for adjusting the input termination equivalent output current module 101 of ring moulds block 102, for based on the received
Export current equivalence signal VIo_estCompared with its internal benchmark being arranged, and error amplification is generated after the amplification of compensated network
Signal Vcomp。
The input termination output end for adjusting ring moulds block 102 of drive control module 103, for generating its output frequency
By VcompThe duty ratio of control close to 50%, two-by-two it is complementary, there are the multichannel complementary drive signals of certain dead time.
Further, the equivalent output current module 101 include comparison module 1011, sample rate current Shaping Module 1012,
Winding voltage rectification module 1013, the second resonance interval time detection module 1014, the first resonance section current draw and average
Module 1015, compensating proportion computing module 1016 compensate current calculation module 1017 and adder 1018.
In the present embodiment, the input terminal of comparison module 1011 receives the transformer T auxiliary winding W of LLC resonant convertera
The voltage signal V of transmissionaux, output reflection VauxThe pulse signal V in positive-negative polarity sectionpAnd Vn。
The first input end of sample rate current Shaping Module 1012 receives the primary current sampled signal of LLC resonant converter
Vir, the second input terminal and third input terminal connect the first output end and second output terminal of the comparison module 101, sampling respectively
Current shaping module 1012 is first according to reflection VauxThe pulse signal V in positive-negative polarity sectionpAnd Vn, by primary current sampled signal
VirIn VauxThe waveform in positive polarity section is directly transmitted, and by it in VauxThe polarity of wave in negative polarity section is overturn, thus
Obtain primary current sampled signal VirSignal V after shapingir_rec。
The input terminal of winding voltage rectification module 1013 receives LLC resonant converter transformer T auxiliary winding WaIt transmitted
The voltage signal V comeaux, the second input terminal and third input terminal connect the first output end and of the comparison module 101 respectively
Two output ends, for VauxWaveform rectified, export VauxSignal V after rectificationaux_rec。
The input of second resonance interval time detection module 1014 terminates the output of the winding voltage rectification module 1014
End, output end output pulse signal Vg_DCM.Second resonance interval time detection module 1014 is for detecting the second resonance section
Time, pulse signal Vg_DCMHigh level reflect the second resonance interval time.
The first input end of first resonance section current draw and averaging module 1015 receives sample rate current flip module
1012 output signal, the second input terminal receive the pulse signal V of the second resonance interval time detection module 1014 outputg_DCM,
Export the first resonance section average current signal Vpri1_avg.Under continuous current mode, first resonance section average current
Signal Vpri1_avgCan equivalent reflection export current average, under discontinuous conduct mode, first resonance section average current
Signal Vpri1_avgApproximation reflection output current average, there is a certain error for the two.
The first input end of compensating proportion computing module 1016 connects the output of the second resonance interval time detection module 1014
End, the output end of the second input termination winding voltage rectification module 1013, reflects the second resonance interval time based on the received
Pulse signal Vg_DCMWith the signal V after transformer auxiliary winding voltage signal rectificationaux_recObtain compensating proportion pulse signal
Vg_com, compensating proportion pulse signal Vg_comDuty ratio and equation (10) inWithThe ratio between voltage is equivalent.
The first input end of compensation current calculation module 1017 connects the output end of sample rate current Shaping Module 1012, and second
The output end of input the second resonance interval time detection module 1014 of termination, third input termination compensating proportion computing module
1016 output end, based on the received primary current sampled signal VirSignal V after shapingir_rec, reflection the second resonance section when
Between pulse signal Vg_DCMWith compensating proportion pulse signal Vg_comObtain compensating current signal Vpri2_avg.The compensation electric current letter
Number Vpri2_avgFor compensating in the first resonance section average current signal Vpri1_avgWith output current average between error,
Under continuous current mode, due to Vir_rec2Equal to zero, compensating current signal Vpri2_avgEqual to zero.
The first input end of adder 1018 connects the output of first resonance section current draw and averaging module 1015
End, the output end of the second input termination compensation current calculation module 1017, is used for the first resonance section average current
Signal Vpri1_avgWith compensating current signal Vpri2_avgIt is overlapped, the output electric current etc. of output reflection average eguivalent output electric current
Imitate signal VIo_est。
Fig. 6 is a specific embodiment based on primary side constant-current control device control block diagram of the invention shown in Fig. 5, Fig. 7
It is respectively the main waveform with embodiment under continuous current mode and discontinuous conduct mode with Fig. 8.Due to nothing under continuous mode
Feedback signal need to be compensated, the value that associated portion waveshape changes over time is zero, therefore to the waveform in Fig. 7 into
Simplification is gone.
The specific embodiment with reference to shown in Fig. 6, in which:
Comparison module 1011 is by comparator Uc1With phase inverter Un1Composition；Wherein comparator Uc1Normal phase input end receive LLC
Controlled resonant converter transformer T auxiliary winding WaThe voltage signal V sentaux, comparator Uc1Anti-phase input terminate primary side
Ground, comparator Uc1Output end output pulse signal Vp, phase inverter Un1Input terminate comparator Uc1Output end, phase inverter
Un1Output end output pulse signal Vn。
Sample rate current Shaping Module 1012 includes four switch Si1~Si4Level reverse circuit, the operational amplifier U of compositionop1
With resistance R1~R4The differential amplifier circuit and sampling holding capacitor C of composition1.Wherein switch Si1One end and switch Si3One
End receives the primary current sampled signal V that LLC resonant converter is sentir, switch Si1Another termination switch Si2One
End, capacitor C1One end and resistance R2One end, switch Si1Control terminal receive comparison module 1011 output pulse signal
Vp；Switch Si2Another termination Si4One end and primary side, switch Si2Control terminal receive comparison module 1011 export pulse
Signal Vn；Switch Si3Another termination switch Si4The other end, capacitor C1The other end and resistance R3One end, switch Si3Control
End processed receives the pulse signal V of the output of comparison module 1011n；Switch Si4Control termination comparison module 1011 output arteries and veins
Rush signal Vp；Resistance R2Another terminating resistor R1One end and operational amplifier Uop1Normal phase input end；Resistance R1It is another
With terminating primary side；Resistance R3Another terminating resistor R4One end and operational amplifier Uop1Inverting input terminal；Operational amplifier
Uop1Output terminating resistor R4The other end, export primary current sampled signal VirSignal V after shapingir_rec.With reference to Fig. 7 and
The waveform of Fig. 8, four switch Si1~Si4The level reverse circuit of composition can be achieved in switch periods to primary current sampled signal
VirIn VauxThe waveform in positive polarity section is directly transmitted and in VauxThe polarity of wave in negative polarity section is overturn.
Winding voltage rectification module 1013 includes four switch Sv1~Sv4Form level reverse circuit, capacitor C7And operation is put
Big device Uop3With resistance R7~R10Form differential amplifier circuit.Switch Sv1One termination switch Sv3One end, and receive LLC
Controlled resonant converter transformer T auxiliary winding WaThe voltage signal V sentaux, switch Sv1Another termination switch Sv2One
End, capacitor C7One end and resistance R9One end, switch Sv1Control terminal receive comparison module 1011 the first output end it is defeated
Signal V outp；Switch Sv2Another termination switch Sv4One end, switch Sv2Control terminal receive the second defeated of comparison module 1011
The output signal V of outletn；Switch Sv3Another termination capacitor C7The other end, switch Sv4The other end and resistance R10One end,
Switch Sv3Control terminal receive comparison module 1011 second output terminal output signal Vn；Switch Sv4Control terminal reception compare mould
The output signal V of first output end of block 101p；Resistance R9Another terminating resistor R8One end and operational amplifier Uop3Just
Phase input terminal；Resistance R8Another termination primary side；Operational amplifier Uop3Anti-phase input terminating resistor R10The other end and electricity
Hinder R7One end, operational amplifier Uop3Output terminating resistor R7The other end and export auxiliary winding rectification after voltage signal
Vaux_rec.Four switch Sv1~Sv4The level reverse circuit of composition can be achieved in switch periods to auxiliary winding voltage signal Vaux
The overturning of positive part directly transmitted with reversed part, the voltage signal V after being overturnaux_recAs shown in figure 8, the progressive die
Formula is without compensation deals therefore is not drawn into.
Second resonance interval time detection module 1014 is by comparator Uc1With reference voltage source Vaux_refComposition.Comparator Uc1
Anti-phase input termination winding voltage rectification module 1013 output end, comparator Uc1Normal phase input end connect reference voltage source
Vaux_refAnode, reference voltage source Vaux_refCathode with connecing primary side, comparator Uc1Output end output reflection the second resonance
Section [Tr/ 2, Ts/ 2] the pulse signal V of timeg_DCM。
First resonance section current draw and averaging module 1015 include switch S1, phase inverter Un2, resistance R5And R6, amplifier
Uop2, capacitor C4.Wherein, switch S1One termination sample rate current Shaping Module 1012 output end, switch S1Another termination electricity
Hinder R5One end and amplifier Uop2Positive input terminal, switch S1Control terminal meet phase inverter Un2Output end, phase inverter Un2Input
Terminate the output end of the second resonance interval time detection module 1014, resistance R5The other end ground connection, amplifier Uop2Negative input end
It is connected with output end and is connected to resistance R6One end, resistance R6Another termination capacitor C4One end and as the first resonance section
The output end of current draw and averaging module 1015, capacitor C4The other end ground connection；Wherein, switch S1With resistance R5Constitute signal
Network is extracted, according to pulse signal Vg_DCMIt will be from switch S2The signal V that one end obtainsir_recExtract its first resonance section
Part Vir_rec1；Amplifier Uop2Constitute voltage follower, resistance R6With capacitor C4Low-pass filter is constituted, signal V is obtainedir_rec1's
Average value signal Vpri1_avg。
Compensating proportion computing module 1016 includes switch Sh1, resistance Rh1, capacitor Ch1, comparator Uch1, phase inverter Unt, switch
Sc1, resistance Rc1, capacitor Cc1, capacitor Cc2, constant-current source Idc, switch Sc2With comparator Uch2.Switch Sc1One termination winding voltage it is whole
The output end of flow module 1013 receives the signal V of its outputaux_rec, switch Sc1Another terminating resistor Rc1One end, phase inverter
UntInput termination the second resonance interval time detection module 1014 output end, receive its output pulse signal Vg_DCM, instead
Phase device UntOutput terminate switch Sc1Control terminal, resistance Rc1Another termination capacitor Cc2One end and comparator Uch2Bear it is defeated
Enter end, capacitor Cc2The other end ground connection, constant-current source IdcA termination capacitor Cc1One end, switch Sc2One end and comparator Uch2
Positive input terminal, constant-current source IdcThe other end, switch Sc2The other end and capacitor Cc1The other end ground connection, comparator Uch2It is defeated
Switch S is terminated outc2Control terminal；Phase inverter Unt, switch Sc1, resistance Rc1, capacitor Cc1Switch averaging network is constituted, is obtained
Vaux_recAverage value in the first resonance sectionCapacitor Cc1, constant-current source Idc, switch Sc2With comparator Uch2Constitute sawtooth
Wave producer generates a peak value and is equal toSawtooth signal Vsaw；Switch Sh1One termination winding voltage rectification module 1013
Output end, receive its output signal Vaux_rec, switch Sh1Another terminating resistor Rh1One end, resistance Rh1The other end
Meet capacitor Ch1One end and comparator Uch1Positive input terminal, switch Sh1Control terminate the second resonance interval time detection module
1014 output end receives the pulse signal V of its outputg_DCM, capacitor Ch1The other end ground connection, comparator Uch1Negative input end
Meet comparator Uch2Negative input end；Switch Sh1, resistance Rh1With capacitor Ch1Switch averaging network is constituted, V is obtainedaux_recSecond
Average value in resonance sectionThe average valueWith sawtooth signal VsawIt is compared, in comparator Uch2Output
End output compensated pulse signal Vg_com.Since the peak value of sawtooth wave isTherefore comparator Uch2Output compensated pulse letter
Number Vg_comDuty ratio be equal toWithThe ratio between.
Compensating current calculation module 1017 includes switch Sw1, resistance Rw1, amplifier Uopw1, resistance Rw2, capacitor Cw1, switch Sw2、
Switch Sw3, phase inverter Unw1, amplifier Uopw2, resistance Rw3With capacitor Cw2, switch Sw1One termination sample rate current Shaping Module 1012
Output end, receive its output signal Vir_rec, switch Sw1Another terminating resistor Rw1One end and amplifier Uopw1Positive input
End, resistance Rw1The other end ground connection, switch Sw1Control termination the second resonance interval time detection module 1014 output end,
Receive the pulse signal V of its outputg_DCM, switch Sw1With resistance Rw1Signal extraction network is constituted, according to pulse signal Vg_DCMIt will be from
Switch S2The signal V that one end obtainsir_recExtract the part V in its second resonance sectionir_rec2；Amplifier Uopw1Negative input termination
Its output end constitutes arc in phase follower；Resistance Rw2One termination amplifier Uopw1Output end, resistance Rw2Another termination electricity
Hold Cw1One end and switch Sw2One end, capacitor Cw1The other end ground connection, resistance Rw2With capacitor Cw1Low-pass filter is constituted, it is right
Signal Vir_rec2It is averaged；Switch Sw2Another termination switch Sw3One end and amplifier Uopw2Positive input terminal, switch Sw3's
Other end ground connection, switch Sw3Control terminal meet phase inverter Unw1Output end, phase inverter Unw1Input termination compensating proportion calculate
The output end of module 1016 is simultaneously connected to switch Sw2Control terminal, receive its output pulse signal Vg_com, switch Sw2With switch Sw3
Constitute signal gating network；Amplifier Uopw2Negative input end connect its output end, constitute in-phase voltage follower；Amplifier Uopw2's
Output end connects resistance Rw3One end, resistance Rw3The other end connect capacitor Cw2One end, capacitor Cw2The other end ground connection, electricity
Hinder Rw3With capacitor Cw2Low-pass filter is constituted, so that the output compensating current signal V of compensation current calculation module 1017pri2_avg
It is equal toAs it can be seen that compensation current calculation module 1017 realizes the function of formula (10), to reach benefit
The effect repaid.
The first input end of adder 1018 connects the output of first resonance section current draw and averaging module 1015
End receives the average value signal V of its outputpri1_avg, the second input termination compensation current calculation module of adder 102
1017 output end receives the compensating current signal V of its outputpri2_avg, reflect after output compensation after the two signal is added
Export the output current equivalence signal V of average currentIo_est, to realize the function of formula (11).
Adjusting ring moulds block 102 includes feedback resistance Rf, capacitor Cf, operational amplifier UfWith reference voltage source VIo_ref.Feedback
Resistance RfOne termination adder 1018 output end, feedback resistance RfAnother termination capacitor CfOne end and operational amplifier
UfInverting input terminal；Operational amplifier UfNormal phase input end meet reference voltage source VIo_refAnode, reference voltage source VIo_ref
Another termination primary side；Operational amplifier UfOutput termination capacitor CfThe other end and export loop adjustment signal Vcomp。
The input termination output end for adjusting ring moulds block 103 of drive control module 103, the output of the first output end are driven
Dynamic signal Vg1, second output terminal output drive signal Vg2。
Present invention can apply to LLC half bridge resonants, can also should use full-bridge LLC resonant converter.Fig. 9
The circuit theory frame of the primary side constant-current device of primary side constant-current control device of the present invention and full-bridge LLC resonant converter composition is shown
Figure.Wherein, the concrete operating principle of each module and realization process can be with specific reference to half-bridge LLC specific embodiments.Corresponding LLC drives
Dynamic 103 output drive signal V of control moduleg1、Vg2、Vg3And Vg4For driving full-bridge LLC resonant converter primary side four switches
Pipe.
The output rectification of LLC resonant converter is using full-wave rectification structure in Fig. 5 and embodiment shown in Fig. 9,
It can be using other output rectifier structure such as full-bridge rectification structures, voltage multiplying rectifier structure and current-doubling rectifier etc., the present invention
Primary side constant-current control device be equally applicable.
The LLC type controlled resonant converter such as three of primary side constant-current control device of the invention and the equally applicable other structure changes of thought
Level LLC resonance inverter etc. and other types of controlled resonant converter.
The primary side resonance current sampling module of LLC resonant converter in embodiment of the present invention, can be using sampling electricity
Resistance acquisition, can also be acquired using Hall current sensor.
Vaux voltage signal in embodiment of the present invention is obtained by transformer auxiliary winding, can also pass through transformation
Device primary side winding is obtained by potential-divider network or differential networks.
The error amplifier U in adjusting ring moulds block 102 in embodiment of the present inventionfCurrent mode error can also be used
Amplifier, the output of the corresponding termination of compensation network one error amplifier, another termination primary side.
The embodiment of equivalent output current module 101 is not limited to the side provided in embodiment in the embodiment of the present invention
Formula can also be adjusted acquisition effect same, such as optionally embodiment is as follows for another kind: equivalent output current module
101 receive the primary side resonance current signal of the signal of the transformer winding both end voltage information of reflection converter and sampling；Institute
It states primary side resonance current signal and the first resonance region is resolved into according to time interval in a switch periods or half of switch periods
Between current signal and the second resonance section current signal；Thereafter according to transformer winding polarity of voltage to the first resonance section electric current
Signal carries out shaping, and the first resonance section current signal is directly transmitted in transformer winding positive polarity section, and
First resonance section current signal is subjected to polarity upset, above-mentioned direct transmission and pole in transformer winding voltage negative polarity section
Property overturning after waveform reconfigure and be averaging processing or average treatment after be added that obtain the first resonance section flat again
Equal current signal Vpri1_avg；Shaping is carried out to the second resonance section current signal according to transformer winding polarity of voltage, by second
Resonance section current signal is directly transmitted in transformer winding positive polarity section, by the second resonance section current signal
Polarity upset is carried out in transformer winding voltage negative polarity section, it is later, further humorous first according to transformer winding voltage
Amplitude information, the transformer winding voltage in vibration section are believed in the amplitude information in the second resonance section and the second resonance interval time
Breath obtains compensating current signal Vpri2_avg；By first resonance section average current signal Vpri1_avgWith the compensation electric current
Signal Vpri2_avgThe output current equivalence signal V of reflection output current average is generated after being addedIo_est；Above-mentioned function is same
It can be realized by physical circuit, not repeated here.
Drive control module 103 in embodiment of the present invention belongs to the common and known of LLC resonant converter control
Technology can be realized using the pulse frequency modulated (PFM) and drive control of the prior art.
According to foregoing invention content, the present invention proposes a kind of compensating current signal extracting method:
1) the primary side resonance current signal V of oversampled converterir；
2) shaping is carried out according to primary side resonance current signal of the transformer winding polarity of voltage of converter to sampling: will be former
Side current sampling signal VirWaveform in transformer winding positive polarity section is directly transmitted, and by its transformer around
The polarity of wave overturning in group voltage negative polarity section, primary current sampled signal are directly transmitted with the waveform of polarity upset again
The signal V after shaping is obtained after combinationir_rec；
3) according to the signal V after shapingir_recObtain its signal V being within the second resonance sectionir_rec2；
4) signal V is obtainedir_rec2Average value
5) signal of the transformer winding voltage of extraction reflection converter in the average amplitude in the first resonance sectionAnd
Signal of the transformer winding voltage of reflection converter in the average amplitude in the second resonance section
6) according to formulaObtain compensating current signal Vpri2_avg。
According to foregoing invention content, the present invention proposes a kind of compensating current signal extracting method:
1) the primary side resonance current signal V of oversampled converterir；
2) primary side resonance current signal V is obtainedirSignal V within the second resonance sectionir2；
3) according to the transformer winding polarity of voltage of converter to the signal V of samplingir2Carry out shaping: by signal Vir2Becoming
The waveform in depressor winding voltage positive polarity section is directly transmitted, and by its wave in transformer winding voltage negative polarity section
Shape polarity upset, the directly waveform of transmission and polarity upset obtain the signal V after shaping after reconfiguringir_rec2；
4) signal V is obtainedir_rec2Average value
5) signal of the transformer winding voltage of extraction reflection converter in the average amplitude in the first resonance sectionWith
And the transformer winding voltage of reflection converter is in the signal of the average amplitude in the second resonance section
6) according to formulaObtain compensating current signal Vpri2_avg。
The step of above-mentioned compensating current signal extracting method and on-fixed, but adjustment or exchange sequentially can be carried out
Obtain identical effect.
Specific module those skilled in the art by the invention can have more under the premise of without prejudice to its spirit
Kind embodiment, or different specific embodiments is formed by a variety of different combinations, it is not detailed herein.
It is no matter described above how detailed, it can also there is many ways in which the implementation present invention, it is described in the specification to be
Several specific embodiments of the invention.It is all any equivalent transformation or modification made according to the spirit of the present invention, should all cover
Within protection scope of the present invention.
The above-mentioned detailed description of the embodiment of the present invention not exhaustion or for limiting the present invention to it is above-mentioned clear
It is formal.It is above-mentioned the particular embodiment of the present invention and embodiment are illustrated with schematic purpose while, those skilled in the art
Member will appreciate that carries out various equivalent modifications within the scope of the invention.
Description above describe the particular embodiment of the present invention and while describe anticipated optimal set mode, no matter
Above occur how being described in detail, also can be implemented in numerous ways the present invention.Foregoing circuit structure and its control mode
Details carried out in details at it and can carry out considerable variation, however it is still contained in the present invention disclosed herein
In.
It should be noted that used specific term is not when illustrating certain features or scheme of the invention as described above
It should be used to indicate to redefine the term herein to limit certain certain features of the invention relevant to the term, feature
Or scheme.In short, will should not be construed to limit the invention to illustrate in term used in appended claims
Specific embodiment disclosed in book, unless above-mentioned detailed description part explicitly defines these terms.Therefore, reality of the invention
Border range not only includes the disclosed embodiments, further include be practiced or carried out under claims it is of the invention all etc.
Efficacious prescriptions case.
Claims (11)
1. primary side constant-current control device, it is characterised in that: the primary side constant-current control device includes equivalent output current module；
Equivalent output current module receives the signal of the transformer both ends winding voltage of reflection converter and the primary side resonance of converter
Current signal generates the first resonance section average current signal Vpri1_avgWith compensating current signal Vpri2_avg, the first resonance section
Average current signal Vpri1_avgWith compensating current signal Vpri2_avgThe output electricity of output reflection output current average after being added
Flow equivalent signal VIo_est；
First resonance section average current signal Vpri1_avgPassed through by the primary side resonance current signal in the first resonance section
The modes such as shaping, average obtain；
The compensating current signal Vpri2_avgThe shaped, average mode according to the primary side resonance current signal in the second resonance section
The second obtained resonance section average current signalReflect the transformer winding average voltage width in the first resonance section
The signal of valueWith the signal of the transformer winding average voltage amplitude in the second resonance section of reflectionBy corresponding relationshipIt obtains；
When the secondary side rectifying tube conducting of first resonance section correspondent transform device, the resonant inductance and resonant capacitance of primary side occur
The section of resonance, the section all exist in continuous current mode and discontinuous conduct mode；Second resonance section correspondent transform
When device pair side rectifying tube turns off, the section of resonance occurs for resonant inductance, resonant capacitance and the static exciter inductance of primary side, should
Section only exists under discontinuous conduct mode.
2. primary side constant-current control device as described in claim 1, it is characterised in that:
Under continuous current mode, first resonance section average current signal Vpri1_avgEquivalent reflection output electric current is average
Value, the compensating current signal Vpri2_avgIt is zero；Under discontinuous conduct mode, first resonance section average current signal
Vpri1_avgApproximation reflection output current average, the compensating current signal Vpri2_avgReflect that first resonance section is average
Current signal Vpri1_avgWith the error amount between equivalent output electric current.
3. primary side constant-current control device as described in claim 1, it is characterised in that:
First resonance section and the second resonance section are obtained by the signal of detection reflection transformer both ends winding voltage.
4. primary side constant-current control device as described in claim 1, it is characterised in that:
The equivalent output current module receives signal and the sampling of the transformer winding both end voltage information of reflection converter
Primary side resonance current signal；Shaping is carried out according to primary side resonance current signal of the transformer winding polarity of voltage to sampling: will
Primary current sampled signal is directly transmitted in transformer winding positive polarity section, and by it in transformer winding voltage
Negative polarity section carries out polarity upset, and the signal after above-mentioned direct transmission and polarity upset obtains primary current after reconfiguring
Reshaping signal；Thereafter primary current reshaping signal is being resolved by the first resonance section current signal and second according to time interval
Resonance section current signal；First resonance section current signal is averaging processing and obtains the first resonance section average current letter
Number Vpri1_avg；Second resonance section current signal is averaging processing and obtains the second resonance section average current signal
Vpri2_avg。
5. primary side constant-current control device as described in claim 1, it is characterised in that:
The equivalent output current module receives signal and the sampling of the transformer winding both end voltage information of reflection converter
Primary side resonance current signal；The primary side resonance current signal is resolved into the first resonance section electric current letter according to time interval
Number and the second resonance section current signal；
Shaping is carried out to the first resonance section current signal according to transformer winding polarity of voltage: the first resonance section electric current is believed
It number is directly transmitted in transformer winding positive polarity section, and by the first resonance section current signal in transformer winding
Voltage negative polarity section carries out polarity upset；Waveform after above-mentioned direct transmission and polarity upset is reconfigured and is averaged
It is added again after processing or average treatment and obtains the first resonance section average current signal Vpri1_avg；
Shaping is carried out to the second resonance section current signal according to transformer winding polarity of voltage: the second resonance section electric current is believed
It number is directly transmitted in transformer winding positive polarity section, by the second resonance section current signal in transformer winding electricity
Negative polarity section is pressed to carry out polarity upset；Signal after above-mentioned direct transmission and polarity upset reconfigures and carries out average place
It is added again after reason or average treatment and obtains the second resonance section average current signal Vpri2_avg。
6. primary side constant-current control device as described in claim 1, it is characterised in that: the primary side constant-current control device also wraps
It includes:
Ring moulds block is adjusted, the input for adjusting ring moulds block terminates the output end of equivalent output current module, based on the received etc.
It imitates output current signal and generates error amplification signal Vcomp。
7. primary side constant-current control device as described in claim 1, it is characterised in that: the primary side constant-current control device also wraps
It includes:
Drive control module, the input termination output end for adjusting ring moulds block of the drive control module are defeated for generating
Frequency is by error amplification signal V outcompThe driving signal of control.
8. primary side constant-current control device as described in claim 1, it is characterised in that:
The equivalent output current module includes comparison module, and sample rate current Shaping Module, winding voltage rectification module, second is humorous
Shake interval time detection module, the first resonance section current draw and averaging module, and compensating proportion computing module compensates galvanometer
Calculate module and adder；
The input terminal of comparison module receives the voltage signal V of the transformer T winding voltage information of reflection converteraux, output reflection
VauxThe pulse signal V in positive-negative polarity sectionpAnd Vn；
The primary current sampled signal V of the first input end receiving transducer of sample rate current Shaping Moduleir, the second input terminal and
Third input terminal connects the first output end and second output terminal of the comparison module, sample rate current flip module basis first respectively
Reflect VauxThe pulse signal V in positive-negative polarity sectionpAnd Vn, by primary current sampled signal VirIn VauxThe waveform in positive polarity section
Directly transmitted, and by it in VauxThe polarity of wave in negative polarity section is overturn, to obtain primary current sampled signal VirIt is whole
Signal V after shapeir_rec；
The input terminal receiving transducer transformer T auxiliary winding W of winding voltage rectification moduleaThe voltage signal V sentaux,
Its second input terminal and third input terminal connect the first output end and second output terminal of the comparison module respectively, for Vaux
Waveform rectified, export VauxSignal V after rectificationaux_rec；
The input of second resonance interval time detection module terminates the output end of the winding voltage rectification module, and output end is defeated
Pulse signal V outg_DCM；Second resonance interval time detection module is for detecting the second resonance interval time, pulse signal Vg_DCM
High level reflect the second resonance interval time；
The first input end of first resonance section current draw and averaging module receives the output signal of sample rate current flip module,
Second input terminal receives the pulse signal V of the second resonance interval time detection module outputg_DCM, the first resonance section of output is averaged
Current signal Vpri1_avg；Under continuous current mode, first resonance section average current signal Vpri1_avgEquivalent it can reflect
Export current average, under discontinuous conduct mode, first resonance section average current signal Vpri1_avgApproximation reflection is defeated
Current average out, there is a certain error for the two；
The first input end of compensating proportion computing module connects the output end of the second resonance interval time detection module, the second input
The output end for terminating winding voltage rectification module, reflects the pulse signal V of the second resonance interval time based on the receivedg_DCMAnd change
Signal V after depressor auxiliary winding voltage signal rectificationaux_recObtain compensating proportion pulse signal Vg_com；
The first input end of compensation current calculation module connects the output end of sample rate current Shaping Module, the second input termination second
The output end of resonance interval time detection module, the output end of third input termination compensating proportion computing module, according to reception
Primary current sampled signal VirSignal V after shapingir_rec, reflection the second resonance interval time pulse signal Vg_DCMAnd benefit
Repay proportional pulse signal Vg_comObtain compensating current signal Vpri2_avg；The compensating current signal Vpri2_avgFor compensating the
One resonance section average current signal Vpri1_avgWith output current average between error, under continuous current mode, due to
Vir_rec2Equal to zero, compensating current signal Vpri2_avgEqual to zero；
The first input end of adder connects the output end of first resonance section current draw and averaging module, the second input
The output end for terminating the compensation current calculation module, is used for the first resonance section average current signal Vpri1_avgWith compensation electricity
Flow signal Vpri2_avgIt is overlapped, the output current equivalence signal V of output reflection average eguivalent output electric currentIo_est。
9. primary side constant-current control device according to claims 1-8, it is characterised in that:
The primary side constant-current control device and converter constitute primary side constant-current device, and the converter is LLC resonant converter.
10. the compensating current signal extracting method of primary side constant-current control device as described in claim 1, it is characterised in that: institute
The method of stating comprises the steps of:
1) sampling obtains the primary side resonance current signal V of converterir；
2) shaping is carried out according to primary side resonance current signal of the transformer winding polarity of voltage of converter to sampling: by primary side electricity
Flow sampled signal VirWaveform in transformer winding positive polarity section is directly transmitted, and by it in transformer winding electricity
The polarity of wave overturning in negative polarity section is pressed, primary current sampled signal is reconfigured through the directly waveform of transmission and polarity upset
The signal V after shaping is obtained afterwardsir_rec；
3) according to the signal V after shapingir_recObtain its signal V being within the second resonance sectionir_rec2；
4) signal V is obtainedir_rec2Average value
5) signal of the transformer winding voltage of acquisition reflection converter in the average amplitude in the first resonance sectionAnd reflection
Signal of the transformer winding voltage of converter in the average amplitude in the second resonance section
6) according to formulaObtain compensating current signal Vpri2_avg。
11. the compensating current signal extracting method of primary side constant-current control device as described in claim 1, it is characterised in that: institute
The method of stating comprises the steps of:
1) sampling obtains the primary side resonance current signal V of converterir；
2) primary side resonance current signal V is extractedirSignal V within the second resonance sectionir2；
3) according to the transformer winding polarity of voltage of converter to the signal V of samplingir2Carry out shaping: by signal Vir2In transformer
The waveform in winding voltage positive polarity section is directly transmitted, and by its transformer winding voltage negative polarity section waveform pole
Property overturning, directly transmission and polarity upset waveform reconfigure after obtain shaping after signal Vir_rec2；
4) signal V is obtainedir_rec2Average value
5) signal of the transformer winding voltage of acquisition reflection converter in the average amplitude in the first resonance sectionAnd reflection
Signal of the transformer winding voltage of converter in the average amplitude in the second resonance section
6) according to formulaObtain compensating current signal Vpri2_avg。
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110277922A (en) * | 2019-05-17 | 2019-09-24 | 杭州电子科技大学 | A kind of LLC primary side constant-current control device and compensating current signal extracting method |
| CN112928924A (en) * | 2021-02-01 | 2021-06-08 | 杭州电子科技大学 | Resonant flyback converter controller |
| CN113659838A (en) * | 2021-07-16 | 2021-11-16 | 杭州电子科技大学 | Secondary side current extraction circuit realized by LLC converter primary side without current sampling |
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Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110277922A (en) * | 2019-05-17 | 2019-09-24 | 杭州电子科技大学 | A kind of LLC primary side constant-current control device and compensating current signal extracting method |
| CN112928924A (en) * | 2021-02-01 | 2021-06-08 | 杭州电子科技大学 | Resonant flyback converter controller |
| CN112928924B (en) * | 2021-02-01 | 2022-03-01 | 杭州电子科技大学 | Resonant flyback converter controller |
| CN113659838A (en) * | 2021-07-16 | 2021-11-16 | 杭州电子科技大学 | Secondary side current extraction circuit realized by LLC converter primary side without current sampling |
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