CN109031429B - Absorption phase difference detection method and system - Google Patents
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Abstract
The invention provides a method and a system for detecting absorption phase difference, wherein the method comprises the following steps that a transmitting end transmits two signals with different phases, a receiving end samples after receiving the signals, the received electric signals are converted into digital signals and stored in a data buffer area, and when the stored data in a storage area reach more than a preset number, phase calculation is carried out on a first digital signal sequence from the data buffer area. The method solves the phase calculation problem of multiple detection signals after passing through different geological environment media.
Description
Technical Field
The invention relates to the field of mining geological detection instruments, in particular to a method and a system capable of measuring phase variation after passing through a medium.
Background
The tunnel radio wave perspective method (also called tunnel penetration method) is a geophysical prospecting method for researching and determining the position, shape, size and physical parameters of a target body by using the electrical property difference between the detected target and the surrounding medium. When radiation field electromagnetic waves emit specific frequency electromagnetic waves from a transmitter on one side of a roadway, the electromagnetic waves encounter target bodies with different electrical properties, the phenomena of wave reflection, wave refraction, wave transmission, wave edge diffraction, wave absorption and the like are generated, the change of magnetic field intensity is uneven, the distribution of the field is changed, a receiver measures the intensity of the field through a receiving antenna, the distribution condition of the field is obtained through a related algorithm, and various geological abnormal bodies such as faults, collapse columns, fold curves, coal seam thickness changes, coal seam breakage and the like are inversely presumed according to the distribution of the field and related geological data. For the fineness of the result, the electromagnetic wave needs to be transmitted near a straight line, and the diffraction is less, so that the frequency needs to be in a middle frequency range. Radio waves need to penetrate through the thickness of a coal seam of hundreds of meters, and water accumulation, faults, collapse columns, breakage and the like exist in the coal seam, so that the radio waves are suitable for penetrating about 50 KHZ-2 MHZ, and common high-frequency antennas cannot be used for transmitting and receiving the frequency of the frequency band, so that the transmission and the reception of signals are mainly realized through an RLC (radio link control) resonant circuit in the market at present.
In the current radio underground tunnel perspective instrument in the market, in the underground construction process of a mine, a transmitter transmits signals at fixed frequency, fixed power and fixed phase, the amplitude and the phase of the signals can change in the process that the signals penetrate through a working surface, a receiver can only extract the amplitude of the signals when receiving the signals, in addition, in the construction process, metal such as an anchor net and the like is arranged in a tunnel at some places, so that the signals of radio waves are shielded, the attenuation of the signals is caused, the phase difference between the transmission and the reception after the transmission and the reception of the signals penetrating through a medium cannot be measured in the prior art, and the phase absorption difference of different media needs to be calculated by a precise method.
Disclosure of Invention
The invention aims to solve the technical problem of providing a novel mining tunnel detection phase calculation method, and solving the phase calculation problem of multiple detection signals after passing through different geological environment media.
The invention is realized by the following steps: a method for detecting absorbed phase difference includes such steps as emitting two signals with different phases by emitting end, sampling by receiving end, converting the received electric signals to digital signals, storing them in data buffer, phase calculating the first digital signal sequence from data buffer, phase calculating the second digital sequence, shifting the first digital signal sequence by two data, shifting the second digital signal sequence by two data, and comparing the two data sequences without changing length, until the phase calculation results of the first digital signal sequence and the second digital signal sequence are different,
and when the phase calculation results of the first digital signal sequence and the second digital signal sequence are different, performing a step, taking the phase calculation result of the first digital signal sequence as a first phase value, taking the last item of the second digital signal sequence as a starting point, taking the data buffer area signal with the integer period length to perform DSPD calculation to obtain a second phase value, and subtracting the two signal phases transmitted by the transmitting end from the first phase value or the second phase value to finally obtain an absorption phase value.
An absorption phase difference detection system comprises a transmitting end and a receiving end,
the system is used for enabling a transmitting terminal to transmit two signals with different phases, a receiving terminal samples after receiving the signals, the received electric signals are converted into digital signals, the digital signals are stored in a data buffer area, when the stored data in a storage area reach more than a preset number, phase calculation is carried out on a first digital signal sequence from the data buffer area, phase calculation is carried out on a second digital sequence, the length of the first digital signal sequence is equal to that of the second signal sequence, the first item of the sequence is adjacent, the phase calculation results of the first digital signal sequence and the second digital signal sequence are compared, if the first digital signal sequence and the second digital signal sequence are the same, the step is carried out, the first item of the first digital signal sequence is shifted backwards by two data, the first item of the second digital signal sequence is shifted backwards by two data, the lengths of the two groups of sequences are unchanged, the phase is recalculated and the result is compared until the phase calculation results of the first digital signal sequence and the second digital signal sequence,
and the DSPD calculation is carried out by taking the data buffer area signal with the integer period length as a starting point to obtain a second phase value, and the first phase value or the second phase value is subtracted from the two signal phases transmitted by the transmitting end to finally obtain an absorption phase value.
The invention has the following advantages: the conversion node is found out by transmitting two groups of electric signals with different phases, and the absorbed phase difference is calculated by the characteristic that the phase difference of the two absorbed electric signals is equal to the phase difference of the original signal, so that the problem of calculating the phase difference of the electric signals in tunnel perspective in the prior art is solved.
Drawings
Fig. 1 is a diagram of a radio underground tunnel scenograph according to an embodiment of the present invention;
FIG. 2 is a schematic diagram of a full bridge driving circuit according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a full bridge driving circuit according to an embodiment of the present invention;
FIG. 4 is a schematic diagram of a multi-turn coil design according to an embodiment of the present invention;
fig. 5 is a schematic diagram of a multi-frequency resonant circuit according to an embodiment of the invention;
FIG. 6 is a flow chart of a wireless pit penetration detection method according to an embodiment of the present invention;
FIG. 7 is a schematic diagram of signal linear propagation in a medium according to an embodiment of the present invention;
FIG. 8 is an absorption voltage arithmetic map according to an embodiment of the present invention;
fig. 9 is a flowchart of an absorption phase difference detection method according to an embodiment of the present invention.
Detailed Description
In order to explain technical contents, structural features, and objects and effects of the present invention in detail, the following detailed description is given with reference to the accompanying drawings in conjunction with the embodiments.
Referring to fig. 1, a radio underground tunnel scenograph is disclosed, which includes a frequency synthesizer, a digital-to-analog conversion module, a forward amplifier, a reverse amplifier, a voltage generation module, a full bridge driving circuit, and a multi-frequency resonance circuit;
the frequency synthesizer is connected with a digital-to-analog conversion module, the digital-to-analog conversion module is connected with a forward amplifier and a reverse amplifier, the forward amplifier, the reverse amplifier and the voltage generation module are connected with a full-bridge drive circuit, and the full-bridge drive circuit is connected with the multi-frequency resonant circuit;
the frequency synthesizer is used for generating multi-amplitude and multi-phase digital signals, and the full-bridge driving circuit is used for amplifying input signals of the forward amplifier and the reverse amplifier; the multi-frequency resonance circuit can switch different resonance frequencies and transmit input signals of the full-bridge driving circuit.
The frequency synthesizer is used for generating digital signals with adjustable amplitude and adjustable phase, such as sine waves, square waves, triangular waves and the like, and the functional components of the existing frequency synthesizer, such as frequency synthesizers designed by various patents such as patents 201110146684.2 and 201080014836.1 and the like can be adopted to achieve the effect of simply generating the digital signals. In a preferred embodiment, a multifunctional DDS (Direct Digital Synthesizer) can be built inside an independently designed FPGA (Field Programmable Gate Array), and has the performance of real-time adjustment of amplitude and phase, so that different Digital signals can be sent out according to the requirements and operation changes of a user. Then, the signal generated by the DDS is converted from a digital signal to an analog signal through the DAC to form an analog signal corresponding to a voltage value, and then the analog signal from the DAC passes through a forward amplifier respectively to generate an analog signal with a larger voltage value and a positive voltage value; generating an analog signal with a larger voltage value and a negative voltage value through an inverting amplifier; the voltage generating module is connected to the full-bridge driving circuit and is used for controlling the operation of the full-bridge driving circuit according to the voltage which is selected to output the corresponding voltage value.
In the embodiment shown in fig. 2, the full-bridge driving circuit includes transistors Q5, Q6, Q8, and Q10,
the forward amplifier is connected with bases of Q5 and Q6, the reverse amplifier is connected with bases of Q8 and Q10, collectors of Q5 and Q8 are connected with the voltage generation module, an emitter of Q5 is connected with a collector of Q6, and an emitter of Q5 is further connected with the multi-frequency resonance circuit; the emitter of Q8 is connected to the collector of Q10, and the emitter of Q8 is also connected to the multi-frequency resonant circuit. Through the design, the output of the forward amplifier and the output of the reverse amplifier can be amplified to different degrees according to different voltage value signals sent by the voltage generation module, so that the output of a lower-level circuit can be output.
In a further embodiment as shown in fig. 3, the full bridge driving circuit comprises fets Q1, Q2, Q3, Q4,
the forward amplifier is connected with the gates of Q1 and Q3, the reverse amplifier is connected with the gates of Q2 and Q4, the source electrodes of Q1 and Q3 are connected with the voltage generation module, the drain electrode of Q1 is connected with the source electrode of Q2, and the drain electrode of Q1 is also connected with the multi-frequency resonance circuit; the drain of Q3 is connected to the source of Q4, and the drain of Q3 is also connected to the multi-frequency resonant circuit. Through the design, the output of the forward amplifier and the output of the reverse amplifier can be amplified to different degrees according to different voltage value signals sent by the voltage generation module, so that the output of a lower-level circuit can be output. In fig. 3, we can also see a driving chip of the MOS transistor, and we control the switching of the MOS transistor through the driving chip, so as to achieve the effect of amplifying the signal better.
In the embodiment shown in fig. 4 and 5, a modeling structure of the multi-frequency resonant circuit is shown, wherein the multi-frequency resonant circuit comprises a capacitor, a resistor and an inductor; in fig. 4, a design of a multi-turn coil is shown, where the inductor includes a plurality of turns of coil, different taps are set at different positions in the coils with different turns to lead out wires, the different taps are connected to a multi-way switch selector, and the multi-way switch selector is used to connect the inductor to an oscillator circuit, thereby implementing the transmitting function of signals with different frequencies. In the preferred embodiment, the capacitance in the RLC is also optionally a variable capacitance.
In the embodiment shown in fig. 6, a wireless pit-through detection method is included, including the steps of S600 absorbing voltage difference detection, S602 absorbing phase difference detection;
the absorbed voltage difference detection specifically comprises the following steps: when the transmitting terminal does not work, the receiving terminal detects and receives a first voltage value; the transmitting end transmits two signals of high voltage and low voltage, the transmitting end transmits a high voltage signal, the receiving end starts to continuously record until the signal is stable after detecting the signal higher than the first voltage value, the voltage value after recording the stability is a second voltage value, the transmitting end transmits a low voltage signal, the receiving end continuously records until the signal is stable after detecting the signal lower than the second voltage value and higher than the first voltage value, and then the voltage value after recording the stability is a third voltage value; calculating the difference between the third voltage value and the second voltage value as an absorption voltage difference;
and (3) absorption phase difference detection: the transmitting end sends two signals with different phases, the initial phase difference of the two signals is recorded as a first phase difference, the phase difference of the two groups of signals received by the receiving end is recorded as a second phase difference, and the difference value between the first phase difference and the second phase difference is obtained as an absorption phase difference;
s604 replaces the positions of the transmitting end and the receiving end, and repeats steps S600 and S602, the absorbed voltage difference detection and the absorbed phase difference detection are performed to obtain the absorbed voltage difference and the absorbed phase difference data of the positions of the plurality of transmitting ends and the plurality of receiving ends, and S606 draws an absorbed voltage equal difference map or an absorbed phase equal difference map according to the data to calculate the gradient change of the equal difference line in the map.
In a particular embodiment, the method may be applied to the multimode radioscopy transmitting device shown in the previous embodiments. Of course, in other embodiments, it is only necessary to be able to realize real-time adjustment of the amplitude and phase of the signal at the transmitting end. The receiving end extracts the amplitude and the phase of the received signal in real time, or the amplitude and the phase may be set to be performed by different sets of transmitting end and receiving end, respectively, that is, the above steps S600 and S602 may be performed by different transmitting end and receiving end, respectively. The transmitting end signal continuously transmits high voltage transmission and low voltage in a set time, the voltage received by the receiving end is VH and VL respectively, the voltage difference between the VH and VL is equal to VH-VL, and the Δ V can be determined to be caused by abnormal body absorption.
Simultaneously, a signal at a transmitting end continuously and alternately transmits signals with the same frequency and amplitude and phi 1 and phi 2 phases in a set time, a receiving end receives the corresponding signals and obtains corresponding phi 11 and phi 22 phases, and finally a phase difference delta phi is obtained as phi 1-phi 11 or as delta phi 2-phi 22;
in the preferred embodiment, the procedure is resumed to combine the information Δ V and Δ Φ at the same frequency for processing, and fig. 7 is a simplified diagram showing the signal propagation in a nearly straight line in a medium, where the medium is the detected object, F1 … Fn is the transmission point, S1 … Sn is the receiving point, and since the radio wave of high frequency propagates in the medium in a nearly straight line, the path from F- > S is referred to as ray. Thus the corresponding rays (F1, S1), (F2, S2), … (Fn, Sn). When abnormal media exist, regularity of amplitude and phase absorption is broken, and therefore the method further comprises the steps of drawing an absorption voltage equal difference map or an absorption phase equal difference map according to absorption voltage difference and absorption phase difference data, connecting places with the same absorption values in receiving ends arranged at different geographic positions, and forming an equal absorption value curve similar to a geographic class contour line drawing map, wherein the absorption voltage equal difference map with the absorption voltage difference on a plane is shown in figure 8, a red line represents a signal propagation direction, namely a connecting line between the receiving end and a transmitting end, the transmitting end and the receiving end change to the next position for recording again after recording data, and specific position setting only needs to enable the connecting line to penetrate through a geological layer according to geological setting to be detected. After the completion of the equal difference map, no matter the voltage or the phase, the steps can be carried out again, the gradient of the equal difference line is calculated in the map, and the place with high gradient change is the position of the abnormal geological medium body.
In other embodiments, the following steps may be included: 1. the transmitting end constructs a multifunctional DDS which has sine wave signals with adjustable amplitude and adjustable phase in real time; 2. the receiving end constructs an ADC module for collecting the received signal in real time and a module for solving the phase and amplitude in real time; 3. before construction, a transmitting end and a receiving end need to stipulate the time point of each transmission; 4. as soon as the appointed transmission time point of each site is reached, the receiver enters an acquisition state in advance, the receiver records a corresponding voltage value V1, and at the moment, the value is changed because the transmitter does not transmit signals and V1 is a random noise value; 5. when a certain transmitting time point is reached, a signal at a transmitting end continuously transmits high-voltage transmission within a set time, at the moment, a receiver continuously calculates a corresponding receiving voltage value, records that the voltage value at the moment is V2 after the voltage value is stabilized, because V2 is larger than V1 at the moment, the receiver can judge that the transmitter is in a transmitting state, when the transmitting end transmits a low-voltage signal, the receiver continuously calculates a corresponding voltage value, records that the voltage value at the moment is V3 after the voltage value is stabilized, because the transmitting environment and the receiving environment including peripheral interference environments are kept unchanged and only the transmitting voltage of the transmitting end is changed when the transmitter transmits the high-voltage signal and the low-voltage signal, the influence of other factors can be eliminated, and the difference between the delta V3 and the V2 is caused by abnormal body absorption; 6. the signal of the transmitting end continuously and alternately transmits signals with the same frequency and amplitude within a set time, the phases of the signals are phi 1 and phi 2 respectively, the receiving end determines the position where the waveform phase of the received signal changes through a related algorithm, namely the point is the starting point for transmitting signals with different phases, the data of the different phases after the point is intercepted, the phases phi 1- & gt, phi 2- & gt of the signals are obtained, as the transmitting environment, the receiving environment and the medium are fixed and unchanged, the received phase difference is equal to the transmitted phase difference phi 1- & ltphi 2 & gt, namely phi 1- & ltphi 2 & gt, and finally the transmitted and received phase difference delta phi is obtained because of abnormal body absorption.6. the transmitting position or the receiving position is moved, and the steps 4, 5 and 6 are repeated, so that a series of delta V and delta phi are obtained; 7. according to the attenuation degree of the specific frequency signal penetrating different media and the difference of the phase deviation, corresponding two-dimensional information of delta V and delta phi is combined for processing, and therefore the position of the abnormal body is obtained.
The method for measuring the phase difference can be achieved by using the prior art, such as the radio phase difference calculation methods disclosed in the patent publications 201410818506.3, 201110143841.4, etc., which are directly applied to complex, or require high cost and cannot be well adapted to variable environments, or by using the following general method:
assuming that the transmitting end transmits a voltage Vf with a frequency f and a phase Φ, the signal can be expressed as x (t) ═ Vf sin (2 ═ pi × f × t + Φ)
If the voltage received by the receiving terminal is Vs and the phase is Φ', the signal can be expressed as: x '(t) ═ Vs × sin (2 × pi × f × t + Φ'), then its fast fourier expression:
eit＝cos(t)+i*sin(t) (2)
e-it＝cos(t)-i*sin(t) (3)
from (1), (2), (3), the real part Re and imaginary part Im of x (k) can be obtained:
the amplitude and phase obtained finally are:
in a preferred embodiment, as shown in fig. 9, the present invention provides a new absorption phase difference detection method suitable for wireless penetration, including the steps of S900 transmitting two signals with different phases at a transmitting end, S902 receiving end sampling after receiving the signals, converting the received electrical signals into digital signals, storing the digital signals in a data buffer, when the stored data in the storage area reaches a preset number, where the two signals are transmitted alternately for several cycles, the preset number of the stored data is designed according to the number of cycles, for example, the transmitting end transmits 1 cycle of data alternately, and the sampling rate of the receiving end is 20 groups per cycle, the preset number can be set to 40, that is, it is ensured that at least 1 cycle of the lowest data number is received by two groups of signals. Then, step S904 is performed to perform phase calculation on the first digital signal sequence and perform phase calculation on the second digital sequence from the data buffer, where the lengths of the first digital signal sequence and the second digital signal sequence are equal, and the first terms of the sequences are adjacent. S906 compares the phase calculation results of the first digital signal sequence and the second digital signal sequence, if the phase calculation results are the same, the steps are carried out, the first item of the first digital signal sequence is shifted backwards by two data, the first item of the second digital signal sequence is shifted backwards by two data, the lengths of the two groups of sequences are unchanged, the phase is calculated again, and the results are compared until the phase calculation results of the first digital signal sequence and the second digital signal sequence are different,
when the phase calculation results of the first digital signal sequence and the second digital signal sequence are different, a step of dividing the last item of the second digital signal sequence into different signals may be determined, S908 uses the phase calculation result of the first digital signal sequence as a first phase value, uses the last item of the second digital signal sequence as a starting point, and takes the data buffer signal with an integer period length to perform DSPD calculation to obtain a second phase value, where the first phase value or the second phase value is compared with the phases of two signals transmitted by a transmitting end, and finally obtains an absorption phase value. The method can obtain the absorption phase difference value between the transmitting end and the receiving end under the complex radio tunnel perspective application scene, and the phase difference absorption value between the transmitting end and the receiving end cannot be accurately obtained due to the fact that the starting point and the starting point of the signal are not known in the general technology. The problem of tunnel perspective appearance to the survey of absorbing the phase difference is solved.
In a specific comprehensive example, the method comprises the following steps that 1, a transmitting end alternately transmits sine wave signals with the same frequency and amplitude and phi 1 and phi 2 phases respectively, and the transmitting time of each phase is 5 whole cycle numbers; 2. the receiving end converts the induced magnetic field signal into an electric field signal through a receiving coil; 3. the ADC sampling rate is assumed to be N (N is more than or equal to 20) times of the transmission frequency, namely the number of samples of the electric signal in each period is more than 20; 4. the electric field signal is converted into a digital sequence corresponding to the voltage one by one after passing through the ADC, and the digital sequence is stored in an AD data buffer area; 5. when the number of data in the AD data buffer area reaches more than 10 × N +6, the MCU controls a DMA (direct memory access) to start to move the data, the initial moving address is M (1-10 × N), M is 1 initially, the addresses of the AD data buffer area are moved into a DSPD-1 data buffer area from the data of M-N + M, the addresses of the AD data buffer area are moved into a DSPD-2 data buffer area from the data of M + 1-N + M +1, and the windowing size of the operation data is N at the moment; 6. when the number of data in the DSPD-1 data buffer area and the DSPD-2 data buffer area reaches N, the DSPD-1 calculation module and the DSPD-2 calculation module start to calculate to respectively obtain corresponding amplitude and phase information; 7. comparing the amplitude and phase information obtained by DSPD-1 and DSPD-2, wherein the amplitude and phase of the amplitude and phase are equal, which indicates that the phase is not changed, continuously comparing, and recording the corresponding phase values phi 1 and phi 2, wherein the phase information is not the phase information of the transmission signal after being changed by the medium because the transmission and the reception are not synchronous; 7. moving the window to enable M to be 3, 5, 7, … … repeating steps 5 and 6, obtaining a series of phase values phi 3, phi 4, phi 5 … …, when phi n is not equal to phi n +1, indicating that the newly added sampling data causes phase change, namely the newly entered data point is the starting point for transmitting signals with different phases, and the previously stable equal phase value is phi 1-; 8. and intercepting data of an integer period after the new data point of the last step is started, wherein the data can be selected as 5 period data, sending the data to a DSPD-1 calculation module to obtain corresponding phase information phi 2, and obtaining the offset of the phase of the transmission signal after the transmission signal passes through the medium by correspondingly subtracting the front phase data and the rear phase data because the phase of the transmission signal is known, such as phi 1 and phi 2.
The DPSD algorithm is a conventional algorithm, and is described as follows:
as described above:
is a measured signal, cos (wn), sin (wn) is a reference signal given by a known system
Suppose that:
wherein e1(n) is that various interference signals in the measuring circuit include DC bias signal, thermal noise, electromagnetic noise, etc., A is the amplitude of the measured signal, s (n) is the reference signal given by the system, s (n) and
making a cross-correlation Rxy(n):
Due to e1(n) is not related to cos (wn), sin (wn) given by the system, so Rxie1(n) ≈ 0, thereby:
further obtaining:
wherein:
is the amplitude of the signal under test,
is the phase of the signal under test.
The above description is only an embodiment of the present invention, and not intended to limit the scope of the present invention, and all modifications of equivalent structures and equivalent processes, which are made by using the contents of the present specification and the accompanying drawings, or directly or indirectly applied to other related technical fields, are included in the scope of the present invention.
Claims (2)
1. A method for detecting absorbed phase difference is characterized by comprising the following steps that a transmitting end transmits two signals with different phases, a receiving end samples after receiving the signals, converts the received electric signals into digital signals, stores the digital signals into a data buffer area, when the stored data in a storage area reach more than a preset number, phase calculation is carried out on a first digital signal sequence from the data buffer area, phase calculation is carried out on a second digital sequence, the length of the first digital signal sequence is equal to that of the second digital signal sequence, the first terms of the sequences are adjacent, the phase calculation results of the first digital signal sequence and the second digital signal sequence are compared, if the first terms of the first digital signal sequence and the second digital signal sequence are the same, the step is carried out, the first terms of the first digital signal sequence are shifted backwards by two data, the first terms of the second digital signal sequence are shifted backwards by two data, the lengths of the two sequences are not changed, and recalculate the phase and compare the results until the phase calculation results of the first digital signal sequence and the second digital signal sequence are different,
and when the phase calculation results of the first digital signal sequence and the second digital signal sequence are different, performing the step, taking the phase calculation result of the first digital signal sequence as a first phase value, taking the last item of the second digital signal sequence as a starting point, taking the data buffer area signal with the integer period length to perform DPSD calculation to obtain a second phase value, and subtracting the phases of the two signals transmitted by the transmitting end from the first phase value or the second phase value correspondingly to obtain an absorption phase value finally.
2. An absorption phase difference detection system is characterized by comprising a transmitting end and a receiving end,
the system is used for enabling a transmitting terminal to transmit two signals with different phases, a receiving terminal samples after receiving the signals, the received electric signals are converted into digital signals, the digital signals are stored in a data buffer area, when the stored data in a storage area reach more than a preset number, phase calculation is carried out on a first digital signal sequence from the data buffer area, phase calculation is carried out on a second digital sequence, the length of the first digital signal sequence is equal to that of the second signal sequence, the first item of the sequence is adjacent, the phase calculation results of the first digital signal sequence and the second digital signal sequence are compared, if the first digital signal sequence and the second digital signal sequence are the same, the step is carried out, the first item of the first digital signal sequence is shifted backwards by two data, the first item of the second digital signal sequence is shifted backwards by two data, the lengths of the two groups of sequences are unchanged, the phase is recalculated and the result is compared until the phase calculation results of the first digital signal sequence and the second digital signal sequence,
and the method is also used for performing steps when the phase calculation results of the first digital signal sequence and the second digital signal sequence are different, taking the phase calculation result of the first digital signal sequence as a first phase value, taking the last item of the second digital signal sequence as a starting point, taking the data buffer area signal with the length of an integer period to perform DPSD calculation to obtain a second phase value, and subtracting the phases of the two signals transmitted by the transmitting end from the first phase value or the second phase value correspondingly to obtain an absorption phase value.
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| CN101397907A (en) * | 2008-10-20 | 2009-04-01 | 中国海洋石油总公司 | Method and apparatus for eliminating directly coupling signal of induction logging tool |
| CN102508032A (en) * | 2011-11-04 | 2012-06-20 | 上海神开石油化工装备股份有限公司 | Method for measuring attenuation and phase shift of detection signal |
| CN103941294A (en) * | 2014-05-07 | 2014-07-23 | 资阳金贝机电有限公司 | High-power frequency spectrum excited electricity detection system |
| CN204028377U (en) * | 2014-07-30 | 2014-12-17 | 桂林电子科技大学 | Synchronous clock phase difference measurements system |
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