CN108768324B - Substrate modulation common mode feedback circuit applied to output stage with inverter structure - Google Patents
Substrate modulation common mode feedback circuit applied to output stage with inverter structure Download PDFInfo
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- CN108768324B CN108768324B CN201711456405.6A CN201711456405A CN108768324B CN 108768324 B CN108768324 B CN 108768324B CN 201711456405 A CN201711456405 A CN 201711456405A CN 108768324 B CN108768324 B CN 108768324B
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/45—Differential amplifiers
- H03F3/45071—Differential amplifiers with semiconductor devices only
- H03F3/45479—Differential amplifiers with semiconductor devices only characterised by the way of common mode signal rejection
- H03F3/45928—Differential amplifiers with semiconductor devices only characterised by the way of common mode signal rejection using IC blocks as the active amplifying circuit
- H03F3/45932—Differential amplifiers with semiconductor devices only characterised by the way of common mode signal rejection using IC blocks as the active amplifying circuit by using feedback means
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/68—Combinations of amplifiers, e.g. multi-channel amplifiers for stereophonics
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
- H03F2203/45—Indexing scheme relating to differential amplifiers
- H03F2203/45074—A comparator circuit compares the common mode signal to a reference before controlling the differential amplifier or related stages
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Abstract
The substrate modulation common mode feedback circuit comprises a common mode feedback circuit connected with a first operational amplifier and a second operational amplifier and a feedback loop generating substrate modulation voltage, wherein the feedback loop comprises a first charge pump circuit, a second charge pump circuit, a first operational amplifier, a second operational amplifier and a circuit, the circuit comprises a first field effect transistor, a second field corresponding transistor connected with the first field corresponding transistor and a third field effect transistor connected with the second field effect transistor, the common mode output of the two-stage operational amplifier is adjusted by the common mode feedback circuit of the first operational amplifier and the second operational amplifier which are connected with the output voltage generated by the feedback loop in a matched mode, and the second stage of the first operational amplifier and the second operational amplifier adopts an inverter structure.
Description
Technical Field
The invention relates to a common mode feedback circuit, in particular to a substrate modulation common mode feedback circuit which is applied to an output stage and has an inverter structure.
Background
The common mode voltage at the output end of the differential input/output operational amplifier usually cannot reach the expected voltage value in the production process due to process deviation or other factors, and a common mode feedback circuit is required to adjust the average value of the output differential signals, namely the common mode voltage, to the expected voltage.
Two-stage operational amplifiers usually employ a common-mode feedback circuit for each stage to stabilize the output common-mode level of the stage. Meanwhile, the output stage of the operational amplifier is generally required to be capable of providing a large output range, but as the power supply voltage is gradually reduced, the voltage output range is reduced by cascading more MOS transistors in the output stage. The second stage of the operational amplifier adopts an inverter structure, so that the output stage of the operational amplifier can be cascaded with fewer MOS (metal oxide semiconductor) tubes, and the operational amplifier can still be in a normal working state in a low power supply voltage structure to achieve a larger output range.
In a conventional two-stage operational amplifier, each operational amplifier stage has a separate common-mode feedback circuit for adjusting the common mode of the output of the operational amplifier stage, and each common-mode feedback circuit needs to input a common-mode level, which is an ideal level to which the output of the operational amplifier stage needs to be adjusted and stabilized finally, so that the conventional structure needs two specifically generated levels. Meanwhile, because the output of the first stage needs to provide bias for the input tube of the second stage, the first stage needs to output a specific voltage, so that the current generated by the input tube is equal to the current provided by the tail current tube. However, in an actual design or production process, the common-mode level output by the first stage cannot be accurately provided, so that the current of the second-stage input tube is not equal to the current of the tail current tube, and finally, under the adjustment of the second-stage operational amplifier common-mode feedback circuit, the current provided by the tail current tube of the second-stage operational amplifier approaches to the current of the input tube and deviates from the expected current during design.
Disclosure of Invention
The technical problem to be solved by the invention is as follows: the substrate modulation common mode feedback circuit applied to the structure of the inverter at the output stage is provided, the circuit structure is improved, and only one-stage common mode feedback is adopted, so that the number of circuits generating specific voltage is reduced, and the circuit structure is optimized; meanwhile, the second-stage common mode adjusting end of the operational amplifier is changed, and the second-stage bias current is guaranteed to be stabilized near the expected ideal current.
The technical solution of the invention is as follows: the substrate modulation common mode feedback circuit applied to the structure with the inverter as the output stage comprises: a feedback loop connecting the common mode feedback circuit of the first and second operational amplifiers to generate the substrate modulation voltage, wherein:
the feedback loop comprises a charge pump 1 circuit, a charge pump 2 circuit, an operational amplifier 1, an operational amplifier 2 and a circuit 3, wherein the circuit 3 comprises a first field-effect tube P1, a second field-effect tube P2 connected with the first field-effect tube and a third field-effect tube N1 connected with the second field-effect tube, the common-mode output of the two-stage operational amplifier is adjusted by the common-mode feedback circuit that the output voltages V _ UP and V _ DN generated by the feedback loop are matched and connected with the operational amplifier 1 and the operational amplifier 2, and the second stage of the operational amplifier 1 and the operational amplifier 2 adopts an inverter structure.
The circuit 3 comprises two input ends Vp and Vn and two output ends Vop and Von, the amplifier 1 comprises a positive input end Vp1, a negative input end Vn1 and an input end Vout1, the amplifier 2 comprises a positive input end Vp2, a negative input end Vn2 and an input end Vout2, the charge pump 1 realizes the voltage multiplication 2 function and comprises an input end Vup and an output end V _ UP, and the charge pump realizes the multiplication-1 function and comprises an input end Vdn and an output end V _ DN.
The inverter operational amplifier corresponding to the output voltages V _ UP and V _ DN comprises a fourth field effect transistor P3, a fifth field effect transistor P4, a sixth field effect transistor N2, a seventh field effect transistor P5 and an eighth field effect transistor N3.
The source of the fourth field effect transistor P3 is connected with a power supply, the grid is connected with bias voltage provided by the outside, the drain is connected with the sources of the fifth field effect transistor P4 and the seventh field effect transistor P5, the grid of the fifth field effect transistor P4 is connected with the grid of the sixth field effect transistor N2, the drain is connected with the drain of the sixth field effect transistor N2, the source of the sixth field effect transistor N2 is grounded, the grid of the seventh field effect transistor P5 is connected with the grid of the eighth field effect transistor N3, the drain is connected with the drain of the eighth field effect transistor N3, and the source of the eighth field effect transistor N3 is grounded.
The circuit 3 comprises a first field effect transistor P1, a second field effect transistor P2 and a third field effect transistor P3; the source of the first field corresponding tube P1 is connected with the power supply voltage, the grid is connected with the bias voltage provided by the outside, and the drain is connected with the source of the second field effect tube P2; the grid of the second field effect transistor P2 is connected with the drain and is connected with the drain of the third field effect transistor N1; the grid of the third field effect transistor is connected with the drain, and the source is grounded.
The input end Vp inputs voltage quantity, the substrate of the second field effect transistor P2 is connected, the input end Vn inputs voltage quantity, the substrate of the third field effect transistor N1 is connected, the drain of the first field effect transistor P1 is connected with the output end Vop to provide output voltage quantity, and the drain of the second field effect transistor P2 is connected with the output end Von to provide output voltage quantity.
The V _ UP of the charge pump 1 is connected with the Vp of the circuit 3, the V _ DN of the charge pump 2 is connected with the Vn of the circuit 3, the Vop of the circuit 3 is connected with the Vm1 of the operational amplifier 1, the Von of the circuit 3 is connected with the Vm2 of the operational amplifier 2, the Vp1 of the operational amplifier 1 is connected with an external input constant level Vb1, the Vp2 of the operational amplifier 2 is connected with an external input constant level Vb2, the Vout1 of the operational amplifier 1 is connected with the Vup of the charge pump 1, the Vout2 of the operational amplifier 2 is connected with the Vdn of the charge pump 2, wherein the V _ UP and the V _ DN serve as the output of the whole feedback loop and are output to the inverter structure of the second stage of the operational amplifier as a substrate modulation voltage.
The input constant level Vb1 is a level expected to be reached by the drain terminal of the fourth field effect transistor P3 in the second-stage inverter structure of the operational amplifier 1, and the input constant level Vb2 is a level expected to be reached by the output common mode of the second-stage inverter structure of the operational amplifier 2.
The feedback circuit connected with the first and second operational amplifiers is used for detecting the common-mode output of the second operational amplifier, comparing the common-mode output with an ideal common mode, generating a control signal and adjusting the common-mode output voltage of the first operational amplifier.
Compared with the prior art, the invention has the advantages that:
(1) according to the invention, only one common mode feedback circuit is connected between the first and second operational amplifiers, so that compared with the traditional common mode feedback structure of two-stage operational amplifiers, the common mode feedback circuit has the advantage of small complexity of the main structure of the common mode feedback circuit;
(2) compared with the traditional structure in which the feedback regulation end is arranged at the grid end of the tail current source of each stage of operational amplifier, the feedback regulation end is arranged at the drain end of the tail current source of the first stage of operational amplifier, so that the regulation process is more stable when the common-mode level is regulated;
(3) according to the invention, by adding the substrate modulation module, the problem that only one common-mode feedback main circuit can be used for adjusting the common-mode output of the first-stage operational amplifier is solved, and when the common-mode output of the second-stage operational amplifier is stabilized near the expected value, the common-mode output of the first-stage operational amplifier can be stabilized near the expected value.
Drawings
FIG. 1 is a schematic diagram of a conventional common mode feedback circuit and its regulated two-stage operational amplifier configuration;
fig. 2 is a schematic diagram of a two-stage operational amplifier structure in which the common mode feedback circuit and the regulated output stage thereof are inverter structures according to the present invention.
Detailed Description
Aiming at the defects of the prior art, the invention provides a substrate modulation common mode feedback circuit applied to a bipolar operational amplifier with an output stage of a phase inverter structure, which comprises a common mode feedback circuit connected with a first operational amplifier and a second operational amplifier and a feedback loop generating substrate modulation voltage. The feedback loop that generates the substrate modulation voltage includes a charge pump 1 circuit, a charge pump 2 circuit, an operational amplifier 1, an operational amplifier 2, and a circuit 3. Wherein the circuit 3 comprises a first fet P1, a second fet P2 connected to the first fet, and a third fet N1 connected to the second fet.
The common-mode output of the two-stage operational amplifier is adjusted by the output voltages V _ UP and V _ DN generated by the feedback loop and the common-mode feedback circuit connected with the first-stage operational amplifier and the second-stage operational amplifier.
The second stage of the operational amplifier adopts an inverter structure, so that the output stage of the operational amplifier can be cascaded with fewer MOS (metal oxide semiconductor) tubes, and the operational amplifier can still be in a normal working state in a low power supply voltage structure to achieve a larger output range.
In a conventional two-stage operational amplifier, each operational amplifier stage has a separate common-mode feedback circuit for adjusting the common mode of the output of the operational amplifier stage, and each common-mode feedback circuit needs to input a common-mode level, which is an ideal level to which the output of the operational amplifier stage needs to be adjusted and stabilized finally, so that the conventional structure needs two specifically generated levels. Meanwhile, because the output of the first stage needs to provide bias for the input tube of the second stage, the first stage needs to output a specific voltage, so that the current generated by the input tube is equal to the current provided by the tail current tube. However, in an actual design or production process, the common-mode level output by the first stage cannot be accurately provided, so that the current of the second-stage input tube is not equal to the current of the tail current tube, and finally, under the adjustment of the second-stage operational amplifier common-mode feedback circuit, the current provided by the tail current tube of the second-stage operational amplifier approaches to the current of the input tube and deviates from the expected current during design.
Compared with the traditional common mode feedback structure of two-stage operational amplifier, the invention only needs one common mode feedback circuit connected with the first and second two-stage operational amplifiers of the operational amplifier, thus only needing one specific voltage generating circuit to generate a common mode level and reducing the circuit complexity of the common mode feedback module. Meanwhile, the feedback regulation end is not arranged at the grid of the tail current tube of the second-stage operational amplifier, so that the second stage can be stabilized near the expected ideal bias current and cannot be changed greatly. The process of the present invention is explained and illustrated in detail below with reference to the accompanying drawings.
Fig. 1 is a schematic diagram of a conventional common mode feedback circuit and a two-stage operational amplifier structure adjusted by the conventional common mode feedback circuit, and fig. 2 is a schematic diagram of a two-stage operational amplifier structure in which the common mode feedback circuit and an output stage adjusted by the common mode feedback circuit are in an inverter structure, wherein a preferred embodiment of the common mode feedback circuit of the present invention comprises: a mode feedback circuit connected with the first and second-stage operational amplifiers and a feedback loop for generating substrate modulation voltage, wherein the feedback loop comprises a charge pump 1 circuit, a charge pump 2 circuit, an operational amplifier 1, an operational amplifier 2 and a circuit 3, the circuit 3 comprises a first field effect transistor P1, a second field effect transistor P2 connected with the first field effect transistor, and a third field effect transistor N1 connected with the second field effect transistor.
1) The specific connection relationship of the circuit is as follows
In the operational amplifier second-stage inverter structure circuit, the source of a fourth field effect transistor P3 is connected with a power supply, the grid of the fourth field effect transistor P3 is connected with bias voltage provided by the outside, and the drain of the fourth field effect transistor P4 is connected with the source of a seventh field effect transistor P5; the grid of the fifth field effect transistor P4 is connected with the grid of the sixth field effect transistor N2, and the drain is connected with the drain of the sixth field effect transistor N2; the source level of the sixth field effect transistor N2 is grounded; the grid of the seventh field effect transistor P5 is connected with the grid of the eighth field effect transistor N3, and the drain is connected with the drain of the eighth field effect transistor N3; the source of the eighth fet N3 is grounded.
In the circuit 3, the source of the first field corresponding tube P1 is connected with the power voltage, the grid thereof is connected with the bias voltage provided by the outside, and the drain thereof is connected with the source of the second field effect tube P2; the grid of the second field effect transistor P2 is connected with the drain and is connected with the drain of the third field effect transistor N1; the grid of the third field effect transistor is connected with the drain, and the source is grounded.
Inside the feedback loop, the V _ UP of the charge pump 1 is connected with the Vp of the circuit 3, the V _ DN of the charge pump 2 is connected with the Vn of the circuit 3, the Vop of the circuit 3 is connected with the Vm1 of the amplifier 1, the Von of the circuit 3 is connected with the Vm2 of the amplifier 2, the Vp1 of the amplifier 1 is connected with an external input constant level Vb1, the Vp2 of the amplifier 2 is connected with an external input constant level Vb2, the Vout1 of the amplifier 1 is connected with the Vup of the charge pump 1, and the Vout2 of the amplifier is connected with the Vdn of the charge pump 2, so that a feedback loop is formed, wherein the V _ UP and the V _ DN serve as the output of the whole feedback loop and are output to an inverter structure of the second stage of the operational amplifier as a substrate modulation voltage.
2) The type of field effect transistor in this circuit is shown in the figure: the first field-effect tube P1, the second field-effect tube P2, the fourth field-effect tube P3, the fifth field-effect tube P4 and the seventh field-effect tube P5 are P-type MOS tubes; the third field effect transistor N1, the sixth field effect transistor N2 and the eighth field effect transistor N3 are N-type MOS transistors.
3) The configuration needs to satisfy the following conditions: the P1 gate voltage is the same as the P3 gate voltage.
Assuming that the width-to-length ratios of P1, P2, P3, P4, P5, N1, N2, and N3 are KP1, KP2, KP3, KP4, KP5, KN1, KN2, and KN3, respectively, the width-to-length ratios thereof should satisfy the following conditions: KP3 ═ 2m × KP1, KP4 ═ KP5 ═ m × KP2, and KN2 ═ KN3 ═ m × KN 1. Wherein m is an integer.
4) See fig. 2.
5) The working principle of the circuit is as follows
NMOS threshold voltage of
Vthn＝Vth0+Υ(|2ΦF+VSB|1/2-|2ΦF|1/2)
From the above formula, the threshold voltage of the NMOS increases with the decrease of the substrate voltage; similarly, the threshold voltage of the PMSO increases with increasing substrate voltage.
The gate of the P1 in the circuit 3 is connected to a constant voltage Vb supplied from the outside, and a constant bias current is generated.
The expected ideal level that the output terminal Von needs to reach is the input level Vb2 of the positive input terminal of the amplifier, if Von > Vb2, Vout2 decreases to a small value, the output level V _ DN of the charge pump also increases correspondingly (V _ DN is-Vout 2), the substrate level input to the second fet N1 increases, the corresponding threshold voltage thereof decreases, Vgs of N1 decreases to ensure that the flowing current does not change, because Vs does not change, Vg decreases, that is, Von. Similarly, when the output Von is lower than the ideal level, Von will rise through the adjustment of the feedback loop.
The expected ideal level that the output end Vop needs to reach is the input level Vb1 of the positive input end of the amplifier, if Vop > Vb1, Vout1 is reduced to a small value, the output level V _ UP of the charge pump is correspondingly reduced, the substrate level input to the second field effect transistor P2 is reduced, the threshold voltage thereof is correspondingly reduced, and | Vgs | of P2 is reduced to ensure that the flowing current is unchanged, and Vs is Vop because Vg is unchanged, so that Vs is reduced. Similarly, when the output Vop is lower than the ideal level, Vop will increase through the adjustment of the feedback loop.
From the above analysis, it can be seen that Vop is stabilized around Vb1 and Von is stabilized around Vb2 by the adjustment of the feedback loop.
When Von and Vop are stable, the gates of the second fet P2 and the third fet N3 are also stable at Vb2, that is, the condition for stabilizing the output common-mode voltage at Vb2 is: the current V _ DN and V _ UP are input as the substrate voltage of the input tube of the operational amplifier of the inverter, and the grid input level is Vb 2.
If the output stage is stable at Vb2 under the substrate bias condition of the current V _ DN and V _ UP, the common mode feedback connecting the first and second stage operational amplifiers will adjust the output common mode of the first stage to Vb2, thereby adjusting the output common mode of the second stage to Vb 2.
The circuit can stabilize each stage of output of the two-stage operational amplifier to a reasonable and same common mode level only through one-stage common mode feedback.
Claims (6)
1. The substrate modulation common mode feedback circuit applied to the output stage with the inverter structure is characterized by comprising the following components: a feedback loop connecting the common mode feedback circuit of the first and second operational amplifiers to generate the substrate modulation voltage, wherein:
the feedback loop comprises a charge pump 1 circuit, a charge pump 2 circuit, an operational amplifier 1, an operational amplifier 2 and a circuit 3, wherein the circuit 3 comprises a first field-effect tube P1, a second field-effect tube P2 connected with the first field-effect tube and a third field-effect tube N1 connected with the second field-effect tube, the common-mode output of the two-stage operational amplifier is adjusted by the common-mode feedback circuits of the operational amplifier 1 and the operational amplifier 2 which are matched and connected with the output voltages V _ UP and V _ DN generated by the feedback loop, and the second stage of the operational amplifier 1 and the operational amplifier 2 adopts an inverter structure;
the circuit 3 comprises two input ends Vp and Vn and two output ends Vop and Von, the operational amplifier 1 comprises a positive input end Vp1, a negative input end Vn1 and an output end Vout1, the operational amplifier 2 comprises a positive input end Vp2, a negative input end Vn2 and an output end Vout2, the charge pump 1 realizes the function of voltage multiplication 2 and comprises an input end Vup and an output end V _ UP, and the charge pump 2 realizes the function of multiplication-1 and comprises an input end Vdn and an output end V _ DN;
the inverter operational amplifier corresponding to the output voltages V _ UP and V _ DN comprises a fourth field effect transistor P3, a fifth field effect transistor P4, a sixth field effect transistor N2, a seventh field effect transistor P5 and an eighth field effect transistor N3;
the circuit 3 comprises a first field effect transistor P1, a second field effect transistor P2 and a third field effect transistor P3; the source electrode of the first field effect transistor P1 is connected with power voltage, the grid electrode is connected with bias voltage provided by the outside, and the drain electrode is connected with the source electrode of the second field effect transistor P2; the grid electrode and the drain electrode of the second field effect transistor P2 are connected and connected with the drain electrode of the third field effect transistor N1; the grid electrode of the third field effect transistor is connected with the drain electrode, and the source electrode is grounded.
2. The substrate modulation common mode feedback circuit applied to an output stage of an inverter structure according to claim 1, wherein: the source electrode of the fourth field effect transistor P3 is connected with a power supply, the grid electrode is connected with bias voltage provided by the outside, the drain electrode is connected with the source electrodes of the fifth field effect transistor P4 and the seventh field effect transistor P5, the grid electrode of the fifth field effect transistor P4 is connected with the grid electrode of the sixth field effect transistor N2, the drain electrode is connected with the drain electrode of the sixth field effect transistor N2, the source electrode of the sixth field effect transistor N2 is grounded, the grid electrode of the seventh field effect transistor P5 is connected with the grid electrode of the eighth field effect transistor N3, the drain electrode is connected with the drain electrode of the eighth field effect transistor N3, and the source electrode of the eighth field effect transistor N3 is grounded.
3. The substrate modulation common mode feedback circuit applied to an output stage of an inverter structure as claimed in claim 2, wherein: the input end Vp inputs voltage quantity, the substrate of the second field effect transistor P2 is connected, the input end Vn inputs voltage quantity, the substrate of the third field effect transistor N1 is connected, the drain electrode of the first field effect transistor P1 is connected with the output end Vop to provide output voltage quantity, and the drain electrode of the second field effect transistor P2 is connected with the output end Von to provide output voltage quantity.
4. The substrate modulation common mode feedback circuit applied to an output stage of an inverter structure according to claim 3, wherein: the V _ UP of the charge pump 1 is connected with the Vp of the circuit 3, the V _ DN of the charge pump 2 is connected with the Vn of the circuit 3, the Vop of the circuit 3 is connected with the Vm1 of the operational amplifier 1, the Von of the circuit 3 is connected with the Vm2 of the operational amplifier 2, the Vp1 of the operational amplifier 1 is connected with an external input constant level Vb1, the Vp2 of the operational amplifier 2 is connected with an external input constant level Vb2, the Vout1 of the operational amplifier 1 is connected with the Vup of the charge pump 1, the Vout2 of the operational amplifier 2 is connected with the Vdn of the charge pump 2, wherein the V _ UP and the V _ DN serve as the output of the whole feedback loop and are output to an inverter structure of the second stage of the operational amplifier as a substrate modulation voltage.
5. The substrate modulation common mode feedback circuit applied to an output stage of an inverter structure according to claim 4, wherein: the input constant level Vb1 is a level expected to be reached by the drain terminal of the fourth field effect transistor P3 in the second-stage inverter structure of the operational amplifier 1, and the input constant level Vb2 is a level expected to be reached by the output common mode of the second-stage inverter structure of the operational amplifier 2.
6. The substrate modulation common mode feedback circuit applied to an output stage of an inverter structure according to claim 5, wherein: the common mode feedback circuit connected with the first and second operational amplifiers is used for detecting the common mode output of the second operational amplifier, comparing the common mode output with an ideal common mode, generating a control signal and adjusting the common mode output voltage of the first operational amplifier.
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Citations (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6563377B2 (en) * | 2001-10-09 | 2003-05-13 | Evenstar, Inc. | Class D switching audio amplifier |
| CN1477788A (en) * | 2002-08-22 | 2004-02-25 | 联发科技股份有限公司 | differential electric charge pump |
| CN101515802A (en) * | 2007-09-14 | 2009-08-26 | 英特尔公司 | A phase/frequency detector and charge pump architecture for referenceless clock and data recovery applications |
| EP2466745A1 (en) * | 2010-12-17 | 2012-06-20 | Dialog Semiconductor GmbH | Amplifier common-mode control methods |
| CN102545805A (en) * | 2010-12-27 | 2012-07-04 | 无锡华润上华半导体有限公司 | Operational amplifier |
| CN104467713A (en) * | 2013-09-18 | 2015-03-25 | 成都英力拓信息技术有限公司 | Pre-amplification circuit with high common mode rejection ratio for biological myoelectricity data acquisition system |
| CN104579235A (en) * | 2015-01-21 | 2015-04-29 | 复旦大学 | Low power consumption transconductor capacitor (Gm-C) dual secondary structure filter |
| CN106330104A (en) * | 2016-10-14 | 2017-01-11 | 湘潭芯力特电子科技有限公司 | Fully differential amplifier circuit with high accuracy and high dynamic range |
| CN107070426A (en) * | 2017-03-17 | 2017-08-18 | 中国科学院微电子研究所 | A kind of amplifier and its implementation |
| CN107112963A (en) * | 2014-12-15 | 2017-08-29 | 北欧半导体公司 | Difference amplifier |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7750737B2 (en) * | 2007-09-05 | 2010-07-06 | Texas Instruments Incorporated | Common mode stabilization in a fully differential amplifier |
| US8686789B2 (en) * | 2011-12-19 | 2014-04-01 | Broadcom Corporation | Transient signal suppression for a class-D audio amplifier arrangement |
-
2017
- 2017-12-28 CN CN201711456405.6A patent/CN108768324B/en active Active
Patent Citations (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6563377B2 (en) * | 2001-10-09 | 2003-05-13 | Evenstar, Inc. | Class D switching audio amplifier |
| CN1477788A (en) * | 2002-08-22 | 2004-02-25 | 联发科技股份有限公司 | differential electric charge pump |
| CN101515802A (en) * | 2007-09-14 | 2009-08-26 | 英特尔公司 | A phase/frequency detector and charge pump architecture for referenceless clock and data recovery applications |
| EP2466745A1 (en) * | 2010-12-17 | 2012-06-20 | Dialog Semiconductor GmbH | Amplifier common-mode control methods |
| CN102545805A (en) * | 2010-12-27 | 2012-07-04 | 无锡华润上华半导体有限公司 | Operational amplifier |
| CN104467713A (en) * | 2013-09-18 | 2015-03-25 | 成都英力拓信息技术有限公司 | Pre-amplification circuit with high common mode rejection ratio for biological myoelectricity data acquisition system |
| CN107112963A (en) * | 2014-12-15 | 2017-08-29 | 北欧半导体公司 | Difference amplifier |
| CN104579235A (en) * | 2015-01-21 | 2015-04-29 | 复旦大学 | Low power consumption transconductor capacitor (Gm-C) dual secondary structure filter |
| CN106330104A (en) * | 2016-10-14 | 2017-01-11 | 湘潭芯力特电子科技有限公司 | Fully differential amplifier circuit with high accuracy and high dynamic range |
| CN107070426A (en) * | 2017-03-17 | 2017-08-18 | 中国科学院微电子研究所 | A kind of amplifier and its implementation |
Non-Patent Citations (2)
| Title |
|---|
| "CCD高精度模拟信号处理前端关键集成技术";刘术彬;《中国博士学位论文全文数据库 信息科技辑》;20141215;I135-25 * |
| "Dual-Gate HFET with Closely Spaced Electrodes on InP";L. Lee等;《proceedings ieee/cornell conference on advanced concepts in high speed semiconductor devices and circuits》;20020806;522-531 * |
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