CN108549074B - Broadband chaotic radar device based on optical simulation correlation receiver - Google Patents
Broadband chaotic radar device based on optical simulation correlation receiver Download PDFInfo
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- CN108549074B CN108549074B CN201810307557.8A CN201810307557A CN108549074B CN 108549074 B CN108549074 B CN 108549074B CN 201810307557 A CN201810307557 A CN 201810307557A CN 108549074 B CN108549074 B CN 108549074B
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S13/50—Systems of measurement based on relative movement of target
- G01S13/58—Velocity or trajectory determination systems; Sense-of-movement determination systems
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S13/06—Systems determining position data of a target
Abstract
The invention discloses a broadband chaotic radar device based on an optical analog correlation receiver. The device consists of a signal transmitter, a signal receiver and a broadband antenna. The wide band chaotic signal source generates chaotic signal, the peak-to-average power ratio of the output signal is maintained to be 2 through the peak-to-average power ratio regulator, then the signal is divided into two paths through the power divider, one path is subjected to frequency conversion amplification and then is transmitted by the antenna, the other path is used as a reference signal, and after the reference signal is delayed through the delay line, the reference signal is subjected to correlation operation with the echo signal which is received by the receiving antenna and subjected to frequency conversion at the acousto-optic correlator. The acousto-optic modulator realizes acousto-optic interaction, and finally realizes time integration at the CCD through diaphragm filtering and lens imaging. And finally, displaying the result by the data processing and displaying module. The method has the greatest characteristic that the cross-correlation result of two paths of analog signals is calculated by using an optical method, so that the traditional digital calculation mode is replaced, and the method has the advantages of high calculation speed, simple structure and the like.
Description
Technical Field
The invention relates to the field of broadband radar design, in particular to a broadband chaotic radar device based on an optical simulation related receiver, which can be applied to the fields of remote sensing, investigation, geophysical exploration and the like.
Background
An Ultra-wideband (UWB) radar belongs to a radar of a new system, has the characteristics of strong anti-stealth capability, small detection blind area, high range resolution, strong anti-interference and anti-multipath capability and the like due to very wide signal bandwidth (the fractional bandwidth is more than 0.25), and is widely applied to military and civil fields. According to the difference of radar transmitting waveforms, common ultra-wideband radars can be divided into a plurality of systems such as impulse radar, linear frequency modulation continuous wave radar, stepping frequency modulation continuous wave radar, random noise radar and the like.
The broadband chaotic radar is a novel ultra-wideband radar appearing in recent years. Compared with other ultra-wideband radars, the broadband chaotic radar has the typical characteristic of generating a transmitting signal with extremely high bandwidth; therefore, the system radar has more ideal distance resolution (up to millimeter level). In addition, the transmitted signal has the white noise-like characteristic, so that the broadband chaotic radar also has stronger anti-electromagnetic interference capability and anti-detection performance. At present, research on broadband chaotic radars becomes a new hotspot in the field of domestic and foreign radar research.
The broadband chaotic radar is generally composed of three parts: an ultra-wideband antenna, a signal transmitter and a signal receiver. When the radar works, a signal transmitter generates a wide-spectrum chaotic electromagnetic wave signal, the chaotic electromagnetic wave signal is radiated into a free space through an ultra-wideband antenna, the electromagnetic wave transmitted at the light speed forms reflection when encountering an object (a target body) positioned in an antenna beam, a weak echo signal is received through the ultra-wideband antenna, then a signal receiver performs cross-correlation calculation, the two-way travel time tau of the electromagnetic wave between the antenna and the target body is extracted, and then the position of the target body is calculated by using a distance formula.
The signal receiver of the broadband chaotic radar is used as a processing device of echo signals, and the core function of the signal receiver is to realize the cross-correlation processing of two paths of signals of transmitting and echo signals, or called as matched filtering processing; therefore, the signal receiver of the broadband chaotic radar is also called a correlation receiver or a matched filtering correlation receiver. At present, in a broadband chaotic radar system, a digital correlation receiver is generally used, and the working principle is as follows: the radar analog signal is firstly converted into a digital signal by using an analog-to-digital converter (ADC), and then cross-correlation calculation is completed on the radar signal by using a digital signal processor (comprising a DSP or a CPU and the like). At present, the digital correlation receiver used by the broadband chaotic radar has the biggest defects of low signal processing speed, long time spent in calculating the distance of a target body and incapability of reflecting the real-time motion state and position of a moving object particularly when the moving object is measured.
In addition, the signal transmitter currently used for broadband chaotic radar signals generally transmits chaotic signals generated by a signal source directly or simply modulates and transmits the chaotic signals by utilizing a sinusoidal carrier; under the condition, the problem that the Peak-to-Average power Ratio (PAPR) of a radar signal is high generally exists, and because the dynamic range of a power amplifier in the radar is limited, the high PAPR not only can cause the chaotic radar to be incapable of fully utilizing the efficiency of a transmitter, but also can cause the radar signal to easily enter a nonlinear area of the power amplifier, so that the radar signal generates nonlinear distortion, obvious spectrum spreading interference and in-band signal distortion are caused, and the performance of the whole radar system is seriously reduced. The high peak-to-average power ratio has become a main technical obstacle of the broadband chaotic radar.
Disclosure of Invention
Aiming at the defects of the broadband chaotic radar in a signal transmitter and a signal receiver, the invention provides a broadband chaotic radar system based on an optical simulation related receiver. Firstly, the broadband chaotic radar signal transmitter can generate a radar signal with an ideal peak-to-average power ratio (PAPR 2), so that the efficiency of the radar transmitter is improved, and the problem of nonlinear distortion of the radar signal is avoided; secondly, the broadband chaotic radar signal receiver of the invention utilizes the optical diffraction principle to realize the high-speed cross-correlation calculation of the broadband chaotic radar signal, shortens the radar data processing time to the sub-microsecond level (the highest is 0.24 mu s), and can accurately measure the position and the speed of a high-speed moving object in real time.
The invention is realized by adopting the following technical scheme: a broadband chaotic radar device based on an optical analog correlation receiver comprises a correlation receiver part and a signal generation and signal receiving part; the signal generating part comprises a broadband chaotic signal source, a peak-to-average power ratio regulator connected with a signal output end of the broadband chaotic signal source, a first broadband power divider connected with a signal output end of the peak-to-average power ratio regulator and a first electric delay line connected with one signal output end of the first broadband power divider; the signal receiving and transmitting part comprises a local vibration source, a second broadband power divider connected with a signal output end of the local vibration source, and a first frequency mixer and a second frequency mixer which are respectively connected with two signal output ends of the second broadband power divider; one signal input end of the first mixer is connected with the second broadband power divider, the other signal input end of the first mixer is connected with the other signal output end of the first broadband power divider, the signal output end of the first mixer is connected with a broadband power amplifier, and the signal output end of the broadband power amplifier is connected with a broadband horn transmitting antenna; one signal input end of the second mixer is connected with the second broadband power divider, and the other signal input end of the second mixer is connected with a broadband horn receiving antenna; the related receiver part comprises a programmable attenuator, a laser, a collimating lens, an acousto-optic modulator, a first imaging lens, a second imaging lens, a diaphragm, a charge-coupled device and a data processing and displaying module; the signal input end of the programmable attenuator is connected with the first electric delay line, and the signal output end of the programmable attenuator is connected with the modulation port of the laser; the collimating lens, the acousto-optic modulator, the first imaging lens, the diaphragm, the second imaging lens and the charge coupling device are sequentially positioned on an emergent light path of the laser; the signal output end of the charge coupling device is connected with the signal input end of the data processing and display module; and the signal output end of the second mixer is connected with the modulation port of the acousto-optic modulator.
The signal transmitter generates a chaotic signal (-10dB bandwidth is more than 500MHz) by a broadband chaotic signal source, the chaotic signal is input into a peak-to-average power ratio regulator to regulate the peak-to-average power ratio, and an output signal of the peak-to-average power ratio regulator is divided into two paths by a first broadband power divider: one path is used as a reference signal S after being delayed by a first electric delay line and attenuated by a programmable attenuator1(t); the other path of the signal is used as a detection signal, and is mixed with one path of high-frequency sinusoidal signal generated by the local vibration source through the second broadband power divider in the mixer, and the high-frequency sinusoidal signal is converted into a high-frequency signal. The high-frequency signal is amplified by the broadband power amplifier and then transmitted by the broadband horn transmitting antenna.
The acousto-optic modulator realizes multiplication calculation of two paths of signals in a Bragg diffraction mode, and then obtains a signal correlation result through time integration to obtain position information of a correlation peak.
And radar echo signals reflected by the target body are received by the broadband horn antenna and input into the second frequency mixer. In the second mixer, the high-frequency radar echo signal is mixed with another high-frequency sinusoidal signal generated by the local vibration source through the second broadband power divider, and the mixed signal is converted into an intermediate-frequency signal S2(t)。S2(t) driving a piezoelectric oscillator in the acousto-optic modulator to convert the electromagnetic wave signal into a sound wave signal, the sound wave elastically deforming the lithium niobate crystal in the acousto-optic modulator to form a diffraction grating, and any laser signal passing through the grating is equivalent to the intermediate frequency signal S2(t) is modulated. Using reference signal S1(t) modulating the laser so that the output light intensity is: i is1(t)＝S1(t)。I1(t) is collimated by a lens and then enters a crystal grating of an acousto-optic modulator and is reflected by S2(t), since the modulation can be equivalent to a mathematical multiplication operation, the output light intensity of the acousto-optic modulator can be expressed as: i is2(t)＝S1(t)S2(t+τ)。I2And (t) focusing the light to a diaphragm through a lens, filtering out non-diffracted light (zero-order light) through the diaphragm, focusing the rest first-order diffracted light to a Charge Coupled Device (CCD) through the lens, and realizing time integration on the CCD. The output result of the charge coupled device CCD is: i isa(τ)＝∫S1(t)S2(t + τ) dt. In the formula Ia(τ) is the reference signal S1(t) and radar echo signal S2(t) cross-correlation function ofaThe maximum peak value of (tau) appears at the position (nth pixel) on the charge coupled device CCD, and the double-travel time tau of the radar detection signal can be calculated according to the fitting relation tau-k-n + d, wherein the parameters k and d are obtained through experiments. And the data processing and displaying module reads the parameter tau from the CCD, calculates the position L and the movement speed v of the target body by using a radar distance and speed formula and displays the position L and the movement speed v on a terminal.
Furthermore, the peak-to-average power ratio adjuster is composed of a broadband comparator, a D trigger, an inverter,a second electrical delay line and an exclusive or logic gate. The concrete connection mode is as follows: the output end of the broadband chaotic signal source is connected with the positive input end (+) of the broadband comparator, the negative input end (-) of the broadband comparator is inputted with a reference voltage Vref, the Vref is continuously tunable between 0 and Vcc, and Vcc is the power supply voltage of the broadband comparator. The output end of the broadband comparator is connected to the signal input end of the D trigger, the clock input end of the D trigger inputs a clock signal, and the frequency of the clock signal is continuously tunable between 0GHz and 10 GHz. The positive output end Q of the D trigger is connected with one input end of the exclusive-OR logic gate, and the negative output end of the D trigger
And the output end of the phase inverter is connected with the input end of the second electric delay line, and the output end of the electric delay line is connected with the other input end of the exclusive-OR logic gate. The method comprises the steps that a broadband chaotic signal generated by a broadband chaotic signal source is input into a peak-to-average power ratio regulator for regulation, the PAPR value of the chaotic signal output by the peak-to-average power ratio regulator reaches an ideal value of 2, the chaotic signal is up-converted to high frequency by a first mixer so as to be transmitted conveniently, and then the received high-frequency signal is down-converted to the original frequency band by a second mixer. The peak-to-average power ratio can enable the broadband power amplifier to play the best amplification effect, and the problem of nonlinear distortion of radar signals is avoided.
Furthermore, a feedback signal output end of the data processing and displaying module is connected with a control input end of the programmable attenuator.
The data processing and display module can also judge whether the CCD is in a saturated state or not by reading the output of the CCD, and if the CCD is saturated, the data processing and display module controls the programmable attenuator to adjust the modulation current of the laser so as to prevent the CCD from being saturated and even damaged due to overhigh light intensity.
The radar system has extremely high response speed, and a measurement result graph is shown in figure 3. The test signal is a pulse signal, and the response signal is a CCD receiving signal. Fig. 3 shows that after 0.24 μ s, the pulse signal reaches the data processing module from the signal transmitter through the broadband antenna and the signal receiver, so that the response time of the radar system is 0.24 μ s, while the response time of the conventional digital radar receiver varies from seconds to several minutes according to the processing speed and the signal quantity of the digital processor, so that the response time of the radar receiver is shortened to about one millionth.
Drawings
FIG. 1 is a schematic diagram of the structure of the device of the present invention.
Fig. 2 is a schematic diagram of the structure of the peak-to-average power ratio adjuster of the present invention.
Fig. 3 is a response time measurement of a radar system according to the present invention.
In fig. 1, 1-broadband chaotic signal source, 2-peak-to-average power ratio adjuster, 3 a-first broadband power divider, 3 b-second broadband power divider, 4-local vibration source, 5 a-first mixer, 5 b-second mixer, 6-broadband power amplifier, 7 a-broadband horn transmitting antenna, 7 b-broadband horn receiving antenna, 8-first electric delay line, 9-programmable attenuator, 10-laser, 11-collimating lens, 12-acousto-optic modulator, 13 a-first imaging lens, 13 b-second imaging lens, 14-diaphragm, 15-charge coupled device, 16-data processing and display module.
In fig. 2, 2 a-wideband comparator, 2b-D flip-flop, 2 c-inverter, 2D-second electrical delay line, 2 e-exclusive or logic gate.
Detailed Description
The following detailed description of embodiments of the invention refers to the accompanying drawings.
As shown in fig. 1, the broadband chaotic radar system based on the optical analog correlation receiver includes a signal transmitter, a signal receiver and a broadband antenna.
The signal transmitter generates a chaotic signal (-10dB bandwidth is more than 500MHz) by a broadband chaotic signal source 1, the chaotic signal is input into a peak-to-average power ratio regulator 2 to regulate the peak-to-average power ratio, and an output signal of the peak-to-average power ratio regulator 2 is divided into two paths by a first broadband power distributor 3 a: one path is delayed by a first electric delay line 8 and attenuated by a programmable attenuator 9 to be used as a reference signal S1(t); the other path is used as a detection signal and is connected with a local vibration source4, one path of high-frequency sinusoidal signals generated by the second broadband power divider 3b is mixed in the first mixer 5a and converted into high-frequency signals. The high-frequency signal is amplified by a broadband power amplifier 6 and then transmitted by a broadband horn transmitting antenna 7 a.
The broadband chaotic signal source 1 can be a circuit system or a photoelectric hybrid system, and specifically can be one of a boolean chaotic circuit, an optical feedback semiconductor chaotic laser or an improved Colpitts oscillator.
As shown in fig. 2, the peak-to-average power ratio adjuster 2 comprises a broadband comparator 2a (with a bandwidth of 0.5 to 10GHz), a D flip-flop 2b, an inverter 2c, a second electrical delay line 2D, and an exclusive or logic gate 2 e. The specific connection mode is as follows: the output end of the broadband chaotic signal source 1 is connected with the positive input end (+) of the broadband comparator 2a, the negative input end (-) of the broadband comparator 2a is input with a reference voltage Vref, the Vref is continuously tunable between 0 and Vcc, and Vcc is the power supply voltage of the broadband comparator 2 a. The output end of the broadband comparator 2a is connected to the signal input end of the D flip-flop 2b, and the clock input end clock of the D flip-flop 2b inputs a clock signal, and the frequency of the clock signal is continuously tunable between 0GHz and 10 GHz. The positive output end Q of the D flip-flop 2b is connected with one input end of the exclusive-OR logic gate 2e, and the negative output end of the D flip-flop 2b
Is connected to an input terminal of the inverter 2c, an output terminal of the inverter 2c is connected to an input terminal of the second electrical delay line 2d, and an output terminal of the second electrical delay line 2d is connected to another input terminal of the xor logic gate 2 e. The broadband chaotic signal generated by the broadband chaotic signal source 1 is input into the peak-to-average power ratio regulator 2 for regulation, and the PAPR value of the output signal of the peak-to-average power ratio regulator 2 reaches an ideal value 2.
In the signal receiver, the radar echo signal reflected by the target is received by the broadband horn receiving antenna 7b and input into the second mixer 5 b. In the second mixer 5b, the high-frequency radar echo signal is mixed with another high-frequency sinusoidal signal generated by the local vibration source 4 through the second broadband power divider 3b, and converted into an intermediate-frequency signal S2(t)。S2(t) Driving Acousto-optic modulationAnd a diffraction grating is formed inside the device 12. Using reference signals S1(t) modulating the laser 10 so that its output light intensity is: i is1(t)＝S1(t)。I1(t) after being collimated by the collimating lens 11, the collimated light passes through an acousto-optic modulator (AOM)12 and is modulated by a diffraction grating in the AOM, and the output light intensity is as follows: i is2(t)＝S1(t)S2(t+τ)。I2(t) is focused by the first imaging lens 13a, and then the undiffracted light (zero-order light) is filtered by the diaphragm 14, so that the first-order diffracted light is focused on a Charge Coupled Device (CCD)15 through the second imaging lens 13b, and time integration is realized on the Charge Coupled Device (CCD). The output of the Charge Coupled Device (CCD)15 is: i isa(τ)＝∫S1(t)S2(t + τ) dt. In the formula Ia(τ) is the reference signal S1(t) and radar echo signal S2(t) cross-correlation function ofaThe maximum peak of (τ) is at the pixel location on the Charge Coupled Device (CCD)15, i.e., is the two-way travel time τ of the radar signal. The data processing and display module 16 reads the output of the Charge Coupled Device (CCD)15 and uses the formula:
and
and (5) calculating the position L and the movement speed v of the target body, and finishing display. Meanwhile, the data processing and display module 16 also judges whether the Charge Coupled Device (CCD)15 is in a saturated state by reading the output of the CCD, and if the Charge Coupled Device (CCD)15 is saturated, the programmable attenuator 9 is controlled to adjust the modulation current of the laser 10, so that the Charge Coupled Device (CCD)15 is prevented from being saturated and even damaged due to overhigh light intensity.
Claims (3)
1. A broadband chaotic radar device based on an optical analog correlation receiver is characterized by comprising a correlation receiver part and a signal generation and signal receiving and transmitting part; the signal generating part comprises a broadband chaotic signal source (1), a peak-to-average power ratio regulator (2) connected with a signal output end of the broadband chaotic signal source (1), a first broadband power divider (3a) connected with a signal output end of the peak-to-average power ratio regulator (2) and a first electric delay line (8) connected with one signal output end of the first broadband power divider (3 a); the signal receiving and transmitting part comprises a local vibration source (4), a second broadband power divider (3b) connected with a signal output end of the local vibration source (4), and a first frequency mixer (5a) and a second frequency mixer (5b) which are respectively connected with two signal output ends of the second broadband power divider (3 b); one signal input end of the first mixer (5a) is connected with the second broadband power divider (3b), the other signal input end of the first mixer (5a) is connected with the other signal output end of the first broadband power divider (3a), the signal output end of the first mixer (5a) is connected with a broadband power amplifier (6), and the signal output end of the broadband power amplifier (6) is connected with a broadband horn transmitting antenna (7 a); one signal input end of the second mixer (5b) is connected with the second broadband power divider (3b), and the other signal input end of the second mixer (5b) is connected with a broadband horn receiving antenna (7 b); the related receiver part comprises a programmable attenuator (9), a laser (10), a collimating lens (11), an acousto-optic modulator (12), a first imaging lens (13a), a second imaging lens (13b), a diaphragm (14), a charge-coupled device (15) and a data processing and display module (16); the signal input end of the programmable attenuator (9) is connected with the first electric delay line (8), and the signal output end of the programmable attenuator (9) is connected with the modulation port of the laser (10); the collimating lens (11), the acousto-optic modulator (12), the first imaging lens (13a), the diaphragm (14), the second imaging lens (13b) and the charge-coupled device (15) are sequentially positioned on an emergent light path of the laser (10); the signal output end of the charge coupling device (15) is connected with the signal input end of the data processing and display module (16); the signal output end of the second mixer (5b) is connected with the modulation port of the acousto-optic modulator (12);
the peak-to-average power ratio adjuster (2) consists of a broadband comparator (2a), a D trigger (2b), an inverter (2c), a second electric delay line (2D) and an exclusive-OR logic gate (2 e); the output end of the broadband chaotic signal source (1) is connected with the positive input end (+) of the broadband comparator (2a), the negative input end (-) of the broadband comparator (2a) is input with a reference voltage Vref, and the Vref is continuously between 0 and VccTuning, wherein Vcc is the power supply voltage of the broadband comparator (2 a); the output end of the broadband comparator (2a) is connected to the signal input end of the D trigger (2b), the clock input end clock of the D trigger (2b) inputs a clock signal, and the frequency of the clock signal is continuously tunable between 0GHz and 10 GHz; the positive output end Q of the D flip-flop (2b) is connected with one input end of the exclusive-OR logic gate (2e), and the negative output end of the D flip-flop (2b)
And the output end of the inverter (2c) is connected with the input end of a second electric delay line (2d), and the output end of the second electric delay line (2d) is connected with the other input end of the exclusive-OR logic gate (2 e).
2. The wide-band chaotic radar device based on the optical analog correlation receiver as claimed in claim 1, wherein the signal generated by the wide-band chaotic signal source (1) is adjusted to a peak-to-average ratio of 2 by the peak-to-average power ratio adjuster (2).
3. The wide-band chaotic radar device based on the optical analog correlation receiver as claimed in claim 1, wherein the feedback signal output terminal of the data processing and display module (16) is connected to the control input terminal of the programmable attenuator (9).
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