CN108512413B - Conversion circuit and control method thereof - Google Patents

Conversion circuit and control method thereof Download PDF

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Publication number
CN108512413B
CN108512413B CN201810196044.4A CN201810196044A CN108512413B CN 108512413 B CN108512413 B CN 108512413B CN 201810196044 A CN201810196044 A CN 201810196044A CN 108512413 B CN108512413 B CN 108512413B
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China
Prior art keywords
mos tube
power supply
direct current
current power
conversion
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CN201810196044.4A
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CN108512413A (en
Inventor
李伦全
周涛
郑车晓
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Shenzhen Boyn Electric Co ltd
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Shenzhen Boyn Electric Co ltd
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The conversion circuit comprises a first DC power supply, a third DC power supply, a first capacitor, a third capacitor, a fifth capacitor, a sixth capacitor, a seventh capacitor, an eighth MOS tube, a driving module, a control module, an equivalent inductor and a filter, wherein the first DC power supply, the first capacitor and the third capacitor are respectively connected in series between a positive bus and a negative bus, a contact between the first DC power supply and the third DC power supply is connected with a contact between the first capacitor and the third capacitor, a third MOS tube source electrode and a fifth MOS tube drain electrode, the fifth MOS tube source electrode is connected with a seventh MOS tube drain electrode, the first MOS tube source electrode is connected with a third MOS tube drain electrode and a sixth MOS tube drain electrode, the first MOS tube drain electrode is connected with a positive bus, the sixth MOS tube source electrode is connected with an eighth MOS tube drain electrode, the seventh MOS tube source electrode and the eighth MOS tube source electrode are connected with a negative bus, the first MOS tube grid electrode, the third MOS tube grid electrode, the fifth MOS tube grid electrode and the eighth MOS tube grid electrode are respectively connected with the driving module, the contact between the fifth MOS tube and the seventh MOS tube is connected with one input end of the filter, and the contact between the sixth MOS tube is connected with the other input end of the filter through the equivalent inductor. The circuit can reduce the switching loss of the switching tube.

Description

Conversion circuit and control method thereof
Technical Field
The present invention relates to switching power supply circuits, and more particularly, to a switching power supply circuit and a control method thereof.
Background
In the existing direct current conversion application occasions, such as a medium-high voltage inverter, a power amplifier and the like, the loss of a power switch tube is large. Therefore, how to design a new conversion circuit, which effectively reduces the switching loss of the switching tube in the switching power supply conversion circuit, is a problem to be solved by the existing switching power supply conversion circuit.
Disclosure of Invention
The invention mainly aims to overcome the defects of the prior art and provide a conversion circuit and a control method thereof, and the switching loss of a switching tube can be greatly reduced by using the conversion circuit.
In order to achieve the above purpose, the present invention adopts the following technical scheme:
in the 1 st aspect of the present invention, the conversion circuit includes a first dc power supply, a third dc power supply, a first capacitor, a third capacitor, a first MOS transistor, a third MOS transistor, a fifth MOS transistor, a sixth MOS transistor, a seventh MOS transistor, an eighth MOS transistor, a driving module, a control module, an equivalent inductor, and a filter, wherein the first dc power supply, the third dc power supply, the first capacitor, and the third capacitor are respectively connected in series between a positive bus and a negative bus, a connection point between the first dc power supply and the third dc power supply is connected to a connection point between the first capacitor and the third capacitor, a source of the third MOS transistor, a drain of the fifth MOS transistor is connected to a drain of the seventh MOS transistor, a source of the first MOS transistor is connected to a drain of the third MOS transistor and a drain of the sixth MOS transistor, a source of the sixth MOS transistor is connected to the positive bus, a drain of the eighth MOS transistor is connected to a drain of the seventh MOS transistor, a connection point between the fifth MOS transistor and the eighth MOS transistor is connected to a drain of the eighth MOS transistor, and the fifth MOS transistor is connected to a connection point between the fifth MOS transistor and the fifth MOS transistor, and the fifth MOS transistor is connected to the drain of the fifth MOS transistor.
In the 2 nd aspect of the present invention, a conversion circuit includes a first dc power supply, a second dc power supply, a first capacitor, a second MOS transistor, a fourth MOS transistor, a fifth MOS transistor, a sixth MOS transistor, a seventh MOS transistor, an eighth MOS transistor, a driving module, a control module, an equivalent inductor, and a filter, wherein the first dc power supply and the second dc power supply, the first capacitor and the second capacitor are respectively connected in series between a positive bus and a negative bus, a connection point between the first dc power supply and the second dc power supply is connected with a connection point between the first capacitor and the second capacitor, a drain of the fourth MOS transistor, a source of the seventh MOS transistor is connected with a source of the fifth MOS transistor, a drain of the second MOS transistor is connected with a negative bus, a drain of the second MOS transistor is connected with a source of the fourth MOS transistor, a drain of the eighth MOS transistor is connected with a source of the eighth MOS transistor, a drain of the eighth MOS transistor is connected with a connection point between the fifth MOS transistor, a drain of the fifth MOS transistor is connected with a connection point between the fifth MOS transistor and the fifth MOS transistor, a drain of the fifth MOS transistor is connected with a connection point of the fifth MOS transistor, and the fifth MOS transistor is connected with a drain of the fifth MOS transistor, and the fifth MOS transistor is connected with a connection point of the fifth MOS transistor.
In the 3 rd aspect of the present invention, a conversion circuit includes a first dc power supply, a second dc power supply, a third dc power supply, a first capacitor, a second capacitor, a third capacitor, a first MOS transistor, a second MOS transistor, a third MOS transistor, a fourth MOS transistor, a fifth MOS transistor, a sixth MOS transistor, a seventh MOS transistor, an eighth MOS transistor, a driving module, a control module, an equivalent inductor, and a filter, wherein the second dc power supply, the first dc power supply, the third dc power supply, the second capacitor, the first capacitor, and the third capacitor are sequentially connected in series between a negative bus and a positive bus, respectively, a connection point between the first dc power supply and the third dc power supply is connected with a connection point between the first capacitor and the third capacitor, a source electrode of the third MOS transistor, a drain electrode of the fifth MOS transistor, a source electrode of the fifth MOS transistor is connected with a drain electrode of the seventh MOS transistor, the source electrode of the first MOS tube is connected with the drain electrode of the third MOS tube and the drain electrode of the sixth MOS tube, the drain electrode of the first MOS tube is connected with a positive bus, the source electrode of the sixth MOS tube is connected with the drain electrode of the eighth MOS tube, the source electrode of the seventh MOS tube and the drain electrode of the fourth MOS tube are connected with the first direct current power supply, the connection point between the second direct current power supply and the connection point between the first capacitor and the second capacitor, the source electrode of the eighth MOS tube is connected with the source electrode of the fourth MOS tube and the drain electrode of the second MOS tube, the source electrode of the second MOS tube is connected with a positive bus, the gates of the first MOS tube, the second MOS tube, the third MOS tube, the fourth MOS tube, the fifth MOS tube, the sixth MOS tube, the seventh MOS tube and the eighth MOS tube are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube and the seventh MOS tube is connected with one input end of the filter, and the connection point between the sixth MOS tube and the eighth MOS tube is connected with the other input end of the filter through the equivalent inductor.
In a fourth aspect of the present invention, a conversion circuit includes a first dc power supply, a second dc power supply, a first capacitor, a second capacitor, a first MOS transistor, a third MOS transistor, a fifth MOS transistor, a sixth MOS transistor, a seventh MOS transistor, an eighth MOS transistor, a driving module, a control module, an isolation transformer circuit, and a secondary side circuit, wherein the first dc power supply and the second dc power supply, the first capacitor and the second capacitor are connected in series between a positive bus and a negative bus, a connection point between the first dc power supply and the second dc power supply is connected to a connection point between the first capacitor and the second capacitor, a source of the third MOS transistor, a drain of the fifth MOS transistor is connected to a drain of the seventh MOS transistor, a source of the first MOS transistor is connected to a drain of the third MOS transistor and a drain of the sixth MOS transistor, a drain of the first MOS transistor is connected to a positive bus, a source of the sixth MOS transistor is connected to a connection point between the seventh MOS transistor and the secondary side of the transformer circuit, a connection point between the source of the eighth MOS transistor and the eighth MOS transistor is connected to a source of the eighth MOS transistor, a connection point between the fifth MOS transistor and a primary side of the transformer circuit is connected to the eighth MOS transistor, and the drain of the seventh MOS transistor is connected to the drain of the fifth MOS transistor.
Further, the secondary side circuit is a full-bridge or half-bridge or full-wave rectifying circuit.
In a fifth aspect of the present invention, a conversion circuit includes a first dc power supply, a second dc power supply, a first capacitor, a second MOS transistor, a fourth MOS transistor, a fifth MOS transistor, a sixth MOS transistor, a seventh MOS transistor, an eighth MOS transistor, a driving module, a control module, an isolation transformer circuit, and a secondary side circuit, wherein the first dc power supply and the second dc power supply are connected in series between a positive bus and a negative bus, a connection point between the first dc power supply and the second dc power supply is connected to a connection point between the first capacitor and the second capacitor, a drain of the fourth MOS transistor is connected to a source of the seventh MOS transistor, a source of the second MOS transistor is connected to a negative bus, a drain of the second MOS transistor is connected to a source of the fourth MOS transistor, a drain of the eighth MOS transistor is connected to a drain of the fifth MOS transistor is connected to a connection point between the fifth MOS transistor and a secondary side of the isolation transformer circuit, a connection point between the fifth MOS transistor and the fifth MOS transistor is connected to a drain of the fifth MOS transistor, and a source of the seventh MOS transistor is connected to a drain of the fifth MOS transistor.
Further, the secondary side circuit is a full-bridge or half-bridge or full-wave rectifying circuit.
In the 6 th aspect of the invention, a conversion circuit includes a first dc power supply, a second dc power supply, a third dc power supply, a first capacitor, a second capacitor, a third capacitor, a first MOS transistor, a second MOS transistor, a third MOS transistor, a fourth MOS transistor, a fifth MOS transistor, a sixth MOS transistor, a seventh MOS transistor, an eighth MOS transistor, a driving module, a control module, an isolation transformer circuit, and a secondary side circuit, wherein the second dc power supply, the first dc power supply, the third dc power supply, the second capacitor, the first capacitor, and the third capacitor are sequentially connected in series between a negative bus and a positive bus, respectively, a connection point between the first dc power supply and the third dc power supply is connected with a connection point between the first capacitor and the third capacitor, a source electrode of the third MOS transistor, a drain electrode of the fifth MOS transistor is connected with a drain electrode of the seventh MOS transistor, the source electrode of the first MOS tube is connected with the drain electrode of the third MOS tube and the drain electrode of the sixth MOS tube, the drain electrode of the first MOS tube is connected with a positive bus, the source electrode of the sixth MOS tube is connected with the drain electrode of the eighth MOS tube, the source electrode of the seventh MOS tube and the drain electrode of the fourth MOS tube are connected with the first direct current power supply, the connection point between the second direct current power supply and the connection point between the first capacitor and the second capacitor, the source electrode of the eighth MOS tube is connected with the source electrode of the fourth MOS tube and the drain electrode of the second MOS tube, the source electrode of the second MOS tube is connected with a positive bus, the gates of the first MOS tube, the second MOS tube, the third MOS tube, the fourth MOS tube, the fifth MOS tube, the sixth MOS tube, the seventh MOS tube and the eighth MOS tube are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube and the seventh MOS tube is connected with the first end of the primary of the isolation transformer circuit, the connection point between the sixth MOS tube and the eighth MOS tube is connected with the second end of the primary, and the secondary of the isolation transformer circuit is connected with the secondary side circuit.
Further, the secondary side circuit is a full-bridge or half-bridge or full-wave rectifying circuit.
Further, the conversion circuit is configured to have a bidirectional conversion function.
In the control method for controlling the conversion circuit according to the 1-2 or 4-5 aspect of the present invention, when performing dc-to-ac conversion or high frequency isolation type dc-to-dc conversion, the corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply on the input side, or the corresponding switching tube combination is turned on to form a conversion circuit corresponding to the second dc power supply/the third dc power supply on the input side, or the corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply and the second dc power supply/the first dc power supply and the third dc power supply on the input side, so as to achieve the effect of multi-level conversion.
In the control method for controlling the conversion circuit according to the 1-2 or 4-5 aspect of the present invention, when performing ac-dc conversion or high-frequency isolated dc-dc conversion, a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the second dc power supply/the third dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply and the second dc power supply/the first dc power supply and the third dc power supply on the output side, so as to achieve the effect of multi-level conversion.
In the control method for controlling the conversion circuit according to aspects 3 and 6 of the present invention, when performing dc-to-ac conversion or high frequency isolation type dc-to-dc conversion, a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply on the input side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the second dc power supply on the input side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the third dc power supply on the input side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply and the second dc power supply on the input side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply, the second dc power supply and the third dc power supply on the input side, so as to achieve a multi-level conversion effect.
In the control method for controlling the conversion circuit according to aspects 3 and 6 of the present invention, when performing ac-dc conversion or high-frequency isolated dc-dc conversion, a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the second dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the third dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply and the second dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply and the third dc power supply on the output side, or a corresponding switching tube combination is turned on to form a conversion circuit corresponding to the first dc power supply, the second dc power supply and the third dc power supply on the output side, so as to achieve a multi-level conversion effect.
The switching loss of the switching tube of the switching power supply is greatly reduced by using the conversion circuit of the invention to carry out corresponding control, and the switching loss is far superior to that of a single two-level power supply.
Drawings
Fig. 1 is a block diagram of a conversion circuit (non-isolated) according to embodiment 1 of the present invention;
FIG. 2 is a waveform diagram of the voltage output of the conversion circuit shown in FIG. 1;
FIG. 3 is a graph showing a comparison of a voltage output waveform of the conversion circuit shown in FIG. 1 and a control timing of a switching tube;
fig. 4 is a block diagram of a conversion circuit (non-isolated) according to embodiment 2 of the present invention;
FIG. 5 is a waveform diagram of the voltage output of the conversion circuit shown in FIG. 4;
FIG. 6 is a graph showing a comparison of a voltage output waveform of the conversion circuit shown in FIG. 4 and a control timing of a switching tube;
fig. 7 is a block diagram of a conversion circuit (non-isolated) according to embodiment 3 of the present invention;
FIG. 8 is a waveform diagram of the voltage output of the conversion circuit shown in FIG. 7;
FIG. 9 is a graph comparing voltage output waveforms of the conversion circuit shown in FIG. 7 with control timings of the switching transistors;
fig. 10 is a block diagram of a conversion circuit (isolation type) of embodiment 4 of the present invention;
fig. 11 is a block diagram of a conversion circuit (isolation type) according to embodiment 5 of the present invention;
fig. 12 is a block diagram of a conversion circuit (isolation type) according to embodiment 6 of the present invention;
Fig. 13 is an equivalent modified circuit example diagram of the isolation transformer circuit in embodiments 4 to 6 of the present invention.
Detailed Description
The following describes embodiments of the present invention in detail. It should be emphasized that the following description is merely exemplary in nature and is in no way intended to limit the scope of the invention or its applications.
Example 1
Referring to fig. 1, a conversion circuit includes a first DC power DC1, a third DC power DC3, a first capacitor C1, a third capacitor C3, a first MOS transistor Q1, a third MOS transistor Q3, a fifth MOS transistor Q5, a sixth MOS transistor Q6, a seventh MOS transistor Q7, an eighth MOS transistor Q8, a driving module, a control module, an equivalent inductor L1, and a filter, wherein the first DC power DC1 and the third DC power DC3, the first capacitor C1 and the third capacitor C3 are respectively connected in series between a positive BUS +bus and a negative BUS-BUS, the connection point between the first DC power DC1 and the third DC power DC3 and the connection point between the first capacitor C1 and the third capacitor C3 and the drain of the third MOS transistor Q3 are connected, the source of the fifth MOS transistor Q5 is connected to the drain of the seventh MOS transistor Q7, the connection point between the first DC power DC1 and the third MOS transistor Q6 and the drain of the eighth MOS transistor Q7 are connected to the drain of the fifth MOS transistor Q7, the connection point between the fifth MOS transistor Q1 and the drain of the fifth MOS transistor Q7 is connected to the drain of the fifth MOS transistor Q6, and the drain of the fifth MOS transistor Q7 is connected to the drain of the fifth MOS transistor Q7, and the connection point between the drain of the fifth MOS transistor Q7 and the fifth MOS transistor Q5 is connected to the drain of the fifth MOS transistor Q5.
Working principle:
when the conversion circuit shown in fig. 1 is controlled to operate, for example, in an inversion mode, the first MOS transistor Q1, the sixth MOS transistor Q6, the fifth MOS transistor Q5, the eighth MOS transistor Q8, or the first MOS transistor Q1, the sixth MOS transistor Q6, and the seventh MOS transistor Q7 may be turned on to form a loop, so that the voltage of the first DC power supply DC1, the second DC power supply DC2, or the first DC power supply DC 1+the second DC power supply DC2 may be inverted, or the seventh MOS transistor Q7, the eighth MOS transistor Q8, or the fifth MOS transistor Q5, the third MOS transistor Q3, and the sixth MOS transistor Q6 may be turned on to enable freewheeling. Referring to fig. 2, the present circuit may operate with four loops, five levels, i.e., V1, V2, -V1, v1+v2, and "0". If DC1 = V1 = 150V, dc3 = V2 = 250, so DC1+ DC3 = V1+ V2 = 400V, the circuit shown in fig. 2 outputs a waveform with amplitude of 380V (i.e. less than 400V) at maximum, turns on the corresponding switching transistor to invert output, turns on the loop of the DC1 region in the 0-a1 (or a 2-0) interval to perform PWM mode operation, i.e. the seventh MOS transistor Q7 is turned on normally, the sixth MOS transistor Q6 is turned on in PWM mode, and the anti-parallel diodes of the third MOS transistor Q and the eighth MOS transistor Q8 are turned on or may perform synchronous rectification mode on as required. At this time, vout=v1×d1, and D1 is the duty ratio of PWM. At this time, the switching voltage born by the sixth MOS transistor Q6 and the eighth MOS transistor Q8 is V1, which is far lower than 400V; when in the interval a1-b1 (or b2-a 2), the corresponding switching tube is turned on to form chopping of V2 (DC 3), at the moment, the first MOS tube Q1 is started to work in a PWM mode, the sixth MOS tube Q6 is normally on, the anti-parallel diodes of the third MOS tube Q3 and the fifth MOS tube Q5 are conducted, or the synchronous rectification mode can be conducted according to the requirement. At this time vout=v2×d2, D2 is the duty cycle of PWM. Similarly, at this time, the switching voltage born by the first MOS transistor Q1 and the third MOS transistor Q3 is V2, which is far lower than 400V; when the voltage is in the interval b1-b2, the corresponding switching tube is turned on to form chopper of V1+V2 (DC 1+DC 3), at the moment, the first MOS tube Q1 is started to work in a PWM mode, the sixth MOS tube Q6 and the seventh MOS tube Q7 are normally on, then the anti-parallel diode of the third MOS tube Q3 is conducted for continuous current, or the synchronous rectification mode can be turned on according to the requirement. At this time, vout= (v1+v2) ×d3+v1dx, D3 is the duty cycle of PWM, and Dx is the on duty cycle of freewheel. Or, at this time, the seventh MOS transistor Q7 is turned on to perform PWM mode operation, the sixth MOS transistor Q6 and the first MOS transistor Q1 are turned on, and then the anti-parallel diode of the fifth MOS transistor Q5 is turned on for freewheeling, or the synchronous rectification mode can be turned on as required. At this time, vout= (v1+v2) ×d3+v1dx, D3 is the duty cycle of PWM, and Dx is the on duty cycle of freewheel. Similarly, at this time, the switching voltage borne by the first MOS transistor Q1, the third MOS transistor Q3, the seventh MOS transistor Q7, and the fifth MOS transistor Q5 is V2 or V1, which is far lower than 400V. Therefore, in the circuit, the switching loss of the switching tube is greatly reduced and is far better than that of a single two-level power supply. Meanwhile, the circuit also achieves the function that the conventional two-power supply (three-level) cannot realize.
The waveforms shown in fig. 3 show that the maximum output amplitude of the circuit is v1+v2, and if the maximum amplitude of the required output waveform only needs the V1 range or the V2 range, the corresponding switching tube is turned on to form a loop as described above. If the circuit is required to output negative waveforms, the working principle can be analogized, and the maximum amplitude can only be the maximum voltage in V1 and V2, so if the circuit is required to output waveforms with two-way equivalent amplitude, the maximum amplitude can only reach the maximum voltage in V1 or V2.
In the non-isolated embodiment of the present invention, the equivalent inductance L1 represents the equivalent inductance in the transformation circuit loop, and is not limited to or fixed to the inductance connected to one side or two sides. The invention also includes the case of equivalent inductances and filters provided by a load such as a generator (motor).
Example 2
Referring to fig. 4, a conversion circuit includes a first DC power DC1, a second DC power DC2, a first capacitor C1, a second capacitor C2, a second MOS transistor Q2, a fourth MOS transistor Q4, a fifth MOS transistor Q5, a sixth MOS transistor Q6, a seventh MOS transistor Q7, an eighth MOS transistor Q8, a driving module, a control module, an equivalent inductor L1, and a filter, the first DC power DC1 and the second DC power DC2, the first capacitor C1 and the second capacitor C2 are respectively connected in series between a positive BUS +buss and a negative BUS-s, a connection point between the first DC power DC1 and the second DC power DC2, a connection point between the first capacitor C1 and the second capacitor C2, and a drain electrode of the fourth MOS transistor Q4, a source electrode of the seventh MOS transistor Q7 are connected, a drain electrode of the seventh MOS transistor Q7 is connected to the fifth transistor Q5, a connection point between the second DC power DC1 and the second MOS transistor Q2 and the eighth MOS transistor Q8 is connected to the drain electrode of the fifth MOS transistor Q6, a connection point between the fifth MOS transistor Q2 and the drain electrode of the seventh MOS transistor Q7 is connected to the fifth MOS transistor Q6, and the drain electrode of the seventh MOS transistor Q7 is connected to the drain electrode of the fifth MOS transistor Q7, and the fifth MOS transistor Q7 is connected to the drain electrode of the fifth transistor Q7.
The difference between this embodiment and the previous embodiment is that the second DC power DC2 is at the negative side of the first DC power DC1, i.e. the symmetrical circuit is similar to the first embodiment.
Working principle:
referring to fig. 5, assuming that dc1=v1 and dc2=v2, similar to the previous embodiment, the circuit of this embodiment may have four loops, five levels, i.e., V1, -V2, - (v1+v2) and "0". Let dc1=v1=150v, dc2=v2=250, dc1+dc2=v1+v2=400V. The amplitude of the output waveform shown in fig. 5 is at most 380V (i.e. less than 400V), the corresponding switching tube is turned on for inversion output, the loop for turning on the DC1 region in the 0-a3 (or a 4-0) interval works in PWM mode, i.e. the fifth MOS tube Q5 is always on, the eighth MOS tube Q8 is turned on in PWM mode, the anti-parallel diodes of the fourth MOS tube Q4 and the sixth MOS tube Q6 are turned on or the synchronous rectification mode can be turned on as required. At this time, vout=v1×d1, and D1 is the duty ratio of PWM. At this time, the switching voltage born by the sixth MOS transistor Q6 and the eighth MOS transistor Q8 is V1, which is far lower than 400V; when in the interval a3-b3 (or b4-a 4), the corresponding switching tube is turned on to form chopping of V2 (DC 3), at the moment, the second MOS tube Q2 is turned on to work according to the PWM mode, the eighth MOS tube Q8 is turned on, the anti-parallel diode of the seventh MOS tube Q7 and the fourth MOS tube Q4 is turned on, or the synchronous rectification mode can be turned on according to the requirement. At this time, vo=v2×d2, and D2 is the duty cycle of PWM. Similarly, at this time, the switching voltage born by the second MOS transistor Q2 and the fourth MOS transistor Q4 is V2, which is far lower than 400V; when in the interval b3-b4, the corresponding switching tube is turned on to form chopping of V1+V2 (DC 1+DC 3), at the moment, the second MOS tube Q2 is turned on to work in a PWM mode, the eighth MOS tube Q8 and the fifth MOS tube Q5 are normally on, then the anti-parallel diode of the fourth MOS tube Q4 is conducted for continuous current, or the synchronous rectification mode can be turned on according to the requirement. At this time, vout= (v1+v2) ×d3+v1dx, D3 is the duty cycle of PWM, and Dx is the on duty cycle of freewheel. Or, at this time, the fifth MOS transistor Q5 is started to perform PWM mode operation, the eighth MOS transistor Q8 and the second MOS transistor Q2 are normally on, and then the anti-parallel diode of the seventh MOS transistor Q7 is conducted for continuous current, or the synchronous rectification mode can be started as required. At this time, vout= (v1+v2) ×d3+v1dx, D3 is the duty cycle of PWM, and Dx is the on duty cycle of freewheel. Similarly, at this time, the switching voltages borne by the second MOS transistor Q2, the fourth MOS transistor Q4, the seventh MOS transistor Q7, and the fifth MOS transistor Q5 are V2 or V1, which are far lower than 400V. Therefore, in the circuit, the switching loss of the switching tube is greatly reduced and is far better than that of a single two-level power supply. Meanwhile, the circuit also achieves the function that the conventional two-power supply (three-level) cannot realize.
Similarly, the waveforms shown in fig. 6 show that the circuit can output waveforms with the maximum amplitude of v1+v2, and if the maximum amplitude of the required output waveform only needs V1 or V2 range, the corresponding switching tube is turned on to form a loop as described above. If the circuit is required to output a forward waveform, the working principle can be analogized, and the maximum amplitude can only be the maximum voltage in V1 and V2, so if the circuit is required to output a waveform with the bidirectional equivalent amplitude, the maximum amplitude can only reach the maximum voltage in V1 or V2.
Example 3
Referring to fig. 7, a conversion circuit includes a first DC power supply DC1, a second DC power supply DC2, a third DC power supply DC3, a first capacitor C1, a second capacitor C2, a third capacitor C3, a first MOS transistor Q1, a second MOS transistor Q2, a third MOS transistor Q3, a fourth MOS transistor Q4, a fifth MOS transistor Q5, a sixth MOS transistor Q6, a seventh MOS transistor Q7, an eighth MOS transistor Q8, a driving module, a control module, an equivalent inductance L1, and a filter, where the second DC power supply DC2, the first DC power supply DC1, and the third DC power supply DC3 are sequentially connected in series between a negative BUS bar-BUS bar and a positive BUS bar +bus bar, respectively, a connection point between the first DC power supply DC1 and the third DC power supply DC3 is connected to a connection point between the first capacitor C1 and the third capacitor C3, and a connection point between the third capacitor C3 and a source electrode Q5 of the third capacitor C3, the source electrode of the fifth MOS tube Q5 is connected with the drain electrode of the seventh MOS tube Q7, the source electrode of the first MOS tube Q1 is connected with the drain electrode of the third MOS tube Q3 and the drain electrode of the sixth MOS tube Q6, the drain electrode of the first MOS tube Q1 is connected with a positive BUS +BUS, the source electrode of the sixth MOS tube Q6 is connected with the drain electrode of the eighth MOS tube Q8, the connection point between the source electrode of the seventh MOS tube Q7 and the drain electrode of the fourth MOS tube Q4 is connected with the first direct current power supply DC1 and the connection point between the second direct current power supply DC2 and the first capacitor C1 and the second capacitor C2, the source electrode of the eighth MOS tube Q8 and the source electrode of the fourth MOS tube Q4 are connected with the drain electrode of the second MOS tube Q2, the source electrode of the second MOS tube Q2 is connected with the positive BUS +S, the first MOS tube Q1, the second MOS tube Q2, the third MOS tube Q3 and the fourth MOS tube Q4 are connected with the drain electrode of the fourth MOS tube Q4, the grid electrodes of the fifth MOS tube Q5, the sixth MOS tube Q6, the seventh MOS tube Q7 and the eighth MOS tube Q8 are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube Q5 and the seventh MOS tube Q7 is connected with one input end of the filter, and the connection point between the sixth MOS tube Q6 and the eighth MOS tube Q8 is connected with the other input end of the filter through the equivalent inductor L1.
Working principle:
referring to fig. 8, assuming that DC 1=v1 and DC 2=dc3=v2, the present circuit just has the loops and the levels of the first and second embodiments, so there may be five loops, i.e., DC1, DC2, D3, dc1+dc2, dc1+dc3, and seven levels, i.e., +v1, V2 (DC 3), v1+v2, -V1, -V2 (DC 2), V1-V2, and "0". The use of the switching tubes in the circuit to form the aforementioned level loop has been described in the working principles of the first and second embodiments, and will not be described here. The relevant schematic waveforms are shown in fig. 9.
Meanwhile, the switching tube of the circuit in the foregoing embodiment has a reverse function, and when the AB access is reversed, and the corresponding reverse timing control is applied, the reverse power conversion function can be completed. Therefore, the circuits of the foregoing embodiments all have a bidirectional conversion function.
In addition, the circuit of the foregoing embodiment may be connected to an isolation circuit instead of a non-isolation circuit to perform forward conversion of the isolation power supply, and if the isolation power supply circuit has a reverse function, the entire circuit connected to the isolation circuit also has a bidirectional conversion function.
Example 4
The difference between this embodiment and embodiment 1 is that an isolation circuit is used.
As shown in fig. 10, the isolated secondary side circuit of the present embodiment has a bidirectional conversion function, and may be a full bridge, a half bridge, or a full wave circuit. The non-isolated inductor can be a single inductor or two inductors on two phases, and is equivalent to one inductor in a loop. The circuit is of four-level isolation type.
Referring to fig. 10, a conversion circuit includes a first DC power supply DC1, a second DC power supply DC2, a first capacitor C1, a second capacitor C2, a first MOS transistor Q1, a third MOS transistor Q3, a fifth MOS transistor Q5, a sixth MOS transistor Q6, a seventh MOS transistor Q7, an eighth MOS transistor Q8, a driving module, a control module, an isolation transformer circuit, and a secondary side circuit, where the first DC power supply DC1 and the second DC power supply DC2, the first capacitor C1 and the second capacitor C2 are respectively connected in series between a positive BUS + BUS and a negative BUS-BUS, a connection point between the first DC power supply DC1 and the second DC power supply DC2 is connected with a source of the first MOS transistor C1, a connection point between the second capacitor C2, a source of the third MOS transistor Q3, and a drain of the fifth MOS transistor Q5, a source of the fifth MOS transistor Q5 is connected with a drain of the seventh MOS transistor Q7, the source electrode of the first MOS tube Q1 is connected with the drain electrode of the third MOS tube Q3 and the drain electrode of the sixth MOS tube Q6, the drain electrode of the first MOS tube Q1 is connected with a positive BUS +BUS, the source electrode of the sixth MOS tube Q6 is connected with the drain electrode of the eighth MOS tube Q8, the source electrode of the seventh MOS tube Q7 and the source electrode of the eighth MOS tube Q8 are connected with a negative BUS-BUS, the grid electrodes of the first MOS tube Q1, the third MOS tube Q3, the fifth MOS tube Q5, the sixth MOS tube Q6, the seventh MOS tube Q7 and the eighth MOS tube Q8 are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube Q5 and the seventh MOS tube Q7 is connected with the first end of the primary of the isolation transformer circuit, the connection point between the sixth MOS tube Q6 and the eighth MOS tube Q8 is connected with the second end of the primary end of the isolation transformer circuit, a secondary of the isolation transformer circuit is connected to the secondary side circuit.
The working principle is referred to the working principle of embodiment 1 and will not be described here.
Example 5
As shown in fig. 11, the present embodiment is different from embodiment 2 in that an isolation circuit is employed. The circuit is another variation of the four-level isolation type.
Referring to fig. 11, a conversion circuit includes a first DC power supply DC1, a second DC power supply DC2, a first capacitor C1, a second capacitor C2, a second MOS transistor Q2, a fourth MOS transistor Q4, a fifth MOS transistor Q5, a sixth MOS transistor Q6, a seventh MOS transistor Q7, an eighth MOS transistor Q8, a driving module, a control module, an isolation transformer circuit, and a secondary side circuit, where the first DC power supply DC1 and the second DC power supply DC2, the first capacitor C1 and the second capacitor C2 are respectively connected in series between a positive BUS + BUS and a negative BUS-BUS, a connection point between the first DC power supply DC1 and the second DC power supply DC2 is connected with a connection point between the first capacitor C1 and the second capacitor C2, a drain electrode of the fourth MOS transistor Q4, a source electrode of the seventh MOS transistor Q7, a drain electrode of the seventh MOS transistor Q7 is connected with a source electrode of the fifth MOS transistor Q5, the source electrode of the second MOS tube Q2 is connected with a negative BUS-BUS, the drain electrode of the second MOS tube Q2 is connected with the source electrode of the fourth MOS tube Q4 and the source electrode of the eighth MOS tube Q8, the drain electrode of the eighth MOS tube Q8 is connected with the source electrode of the sixth MOS tube Q6, the drain electrode of the fifth MOS tube Q5 and the drain electrode of the sixth MOS tube Q6 are connected with a positive BUS +BUS, the grid electrodes of the second MOS tube Q2, the fourth MOS tube Q4, the fifth MOS tube Q5, the sixth MOS tube Q6, the seventh MOS tube Q7 and the eighth MOS tube Q8 are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube Q5 and the seventh MOS tube Q7 is connected with the first end of the primary of the isolation transformer circuit, the connection point between the sixth MOS tube Q6 and the eighth MOS tube Q8 is connected with the second end of the primary of the isolation transformer circuit, a secondary of the isolation transformer circuit is connected to the secondary side circuit. The secondary side circuit may be a full bridge or half bridge or full wave rectifying circuit.
The working principle is referred to the working principle of embodiment 2 and will not be described here.
Example 6
As shown in fig. 12, the present embodiment is different from embodiment 3 in that an isolation circuit is employed. The circuit is six-level isolation type.
Referring to fig. 12, a conversion circuit includes a first DC power supply DC1, a second DC power supply DC2, a third DC power supply DC3, a first capacitor C1, a second capacitor C2, a third capacitor C3, a first MOS transistor Q1, a second MOS transistor Q2, a third MOS transistor Q3, a fourth MOS transistor Q4, a fifth MOS transistor Q5, a sixth MOS transistor Q6, a seventh MOS transistor Q7, an eighth MOS transistor Q8, a driving module, a control module, an isolation transformer circuit, and a secondary side circuit, where the second DC power supply DC2, the first DC power supply DC1, and the third DC power supply DC3 are sequentially connected in series between a negative BUS bar-BUS bar and a positive BUS bar + BUS bar, respectively, a connection point between the first DC power supply DC1 and the third DC power supply DC3, a connection point between the first capacitor C1 and the third capacitor C3, and a connection point between the third capacitor C3, and a drain electrode Q5 of the third capacitor C3 are sequentially connected, the source electrode of the fifth MOS tube Q5 is connected with the drain electrode of the seventh MOS tube Q7, the source electrode of the first MOS tube Q1 is connected with the drain electrode of the third MOS tube Q3 and the drain electrode of the sixth MOS tube Q6, the drain electrode of the first MOS tube Q1 is connected with a positive BUS +BUS, the source electrode of the sixth MOS tube Q6 is connected with the drain electrode of the eighth MOS tube Q8, the connection point between the source electrode of the seventh MOS tube Q7 and the drain electrode of the fourth MOS tube Q4 is connected with the first DC power supply DC1 and the connection point between the second DC power supply DC2 and the first capacitor C1 and the second capacitor C2, the source electrode of the eighth MOS tube Q8 and the source electrode of the fourth MOS tube Q4 are connected with the drain electrode of the second MOS tube Q2, the source electrode of the second MOS tube Q2 is connected with the positive BUS +S, the first MOS tube Q1, the second MOS tube Q2 and the third MOS tube Q3 are connected with the drain electrode of the fourth MOS tube Q4, the grid electrodes of the fourth MOS tube Q4, the fifth MOS tube Q5, the sixth MOS tube Q6, the seventh MOS tube Q7 and the eighth MOS tube Q8 are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube Q5 and the seventh MOS tube Q7 is connected with the first end of the primary of the isolation transformer circuit, the second end of the primary connected with the connection point between the sixth MOS tube Q6 and the eighth MOS tube Q8 is connected with the secondary side circuit. The secondary side circuit may be a full bridge or half bridge or full wave rectifying circuit.
The working principle is referred to the working principle of embodiment 2 and will not be described here.
The isolation transformer circuit of the embodiment of the present invention may also be, but not limited to, an equivalent modified circuit as shown in fig. 13. In summary, the isolation circuit in the present invention may be any conventional isolation circuit, or may be any soft-switching circuit, and variations of any isolation circuit, including a mode in which a transformer portion in a resonant tank is arranged in parallel with an exciting inductance and a transformer as two components, and a mode in which the inductance is arranged at a load to form an equivalent inductance, etc., all belong to the protection scope of the present invention.
The foregoing is a further detailed description of the invention in connection with specific/preferred embodiments, and it is not intended that the invention be limited to such description. It will be apparent to those skilled in the art that several alternatives or modifications can be made to the described embodiments without departing from the spirit of the invention, and these alternatives or modifications should be considered to be within the scope of the invention.

Claims (7)

1. The control method of the conversion circuit is characterized in that the conversion circuit comprises a first direct current power supply, a third direct current power supply, a first capacitor, a third capacitor, a first MOS tube, a third MOS tube, a fifth MOS tube, a sixth MOS tube, a seventh MOS tube, an eighth MOS tube, a driving module, a control module, an equivalent inductor and a filter, wherein the first direct current power supply, the third direct current power supply, the first capacitor and the third capacitor are respectively connected in series between a positive bus and a negative bus, a connection point between the first direct current power supply and the third direct current power supply is connected with a connection point between the first capacitor and the third capacitor, a source electrode of the third MOS tube and a drain electrode of the fifth MOS tube are connected, a source electrode of the fifth MOS tube is connected with a drain electrode of the seventh MOS tube, a drain electrode of the first MOS tube is connected with a drain electrode of the third MOS tube, a drain electrode of the first MOS tube is connected with a drain electrode of the fifth MOS tube, a drain electrode of the sixth MOS tube is connected with a drain electrode of the fifth MOS tube, a drain electrode of the fifth MOS tube is connected with a drain of the fifth MOS tube, a drain of the fifth MOS tube is connected with a drain of the fifth MOS tube, the fifth MOS tube is connected with a drain of the fifth MOS tube is connected with the fifth MOS tube and the fifth MOS tube is connected with a drain electrode of the fifth MOS tube respectively; the method comprises the following steps: when the direct current-to-alternating current conversion or the high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the third direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the third direct current power supply at the input side, so that the effect of multi-level conversion is achieved; alternatively, the method comprises: when alternating current-to-direct current conversion or high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the third direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the third direct current power supply at the output side, so that the effect of multi-level conversion is achieved.
2. The control method of the conversion circuit is characterized in that the conversion circuit comprises a first direct current power supply, a second direct current power supply, a first capacitor, a second MOS tube, a fourth MOS tube, a fifth MOS tube, a sixth MOS tube, a seventh MOS tube, an eighth MOS tube, a driving module, a control module, an equivalent inductor and a filter, wherein the first direct current power supply, the second direct current power supply, the first capacitor and the second capacitor are respectively connected in series between a positive bus and a negative bus, a connection point between the first direct current power supply and the second direct current power supply is connected with a connection point between the first capacitor and the second capacitor, a drain electrode of the fourth MOS tube and a source electrode of the seventh MOS tube, a drain electrode of the seventh MOS tube is connected with the source electrode of the fifth MOS tube, the source electrode of the second MOS tube is connected with a negative bus, the drain electrode of the second MOS tube is connected with the source electrode of the fourth MOS tube and the source electrode of the eighth MOS tube, the drain electrode of the eighth MOS tube is connected with the source electrode of the sixth MOS tube, the drain electrode of the fifth MOS tube and the drain electrode of the sixth MOS tube are connected with a positive bus, the grid electrodes of the second MOS tube, the fourth MOS tube, the fifth MOS tube, the sixth MOS tube, the seventh MOS tube and the eighth MOS tube are respectively connected with the driving module, the driving module is connected with the control module, a connection point between the fifth MOS tube and the seventh MOS tube is connected with one input end of the filter, and a connection point between the sixth MOS tube and the eighth MOS tube is connected with the other input end of the filter through the equivalent inductor; the method comprises the following steps: when DC-AC conversion or high-frequency isolation type DC-DC conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first DC power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second DC power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first DC power supply and the second DC power supply at the input side, so that the effect of multi-level conversion is achieved; alternatively, the method comprises: when alternating current-to-direct current conversion or high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the output side, so that the effect of multi-level conversion is achieved.
3. A control method of a conversion circuit, characterized in that the conversion circuit comprises a first direct current power supply, a second direct current power supply, a third direct current power supply, a first capacitor, a second capacitor, a third capacitor, a first MOS tube, a second MOS tube, a third MOS tube, a fourth MOS tube, a fifth MOS tube, a sixth MOS tube, a seventh MOS tube, an eighth MOS tube, a driving module, a control module, an equivalent inductor and a filter, the second direct current power supply, the first direct current power supply and the third direct current power supply are sequentially connected in series between a negative bus and a positive bus respectively, a connection point between the first direct current power supply, the third direct current power supply and the positive bus is sequentially connected with the first capacitor, a connection point between the third capacitor and the third MOS tube, and a drain electrode of a third MOS tube are connected, a source electrode of the fifth MOS tube is connected with a drain electrode of a seventh MOS tube, a source electrode of the first MOS tube is connected with a drain electrode of the third MOS tube, a connection point between the second MOS tube and the fourth MOS tube is connected with the drain electrode of the fifth MOS tube, a connection point between the first MOS tube and the fourth MOS tube is connected with the fourth MOS tube, a connection point between the drain electrode of the fourth MOS tube and the fourth MOS tube is connected with the drain electrode of the fifth MOS tube, the driving module is connected with the control module, a connection point between the fifth MOS tube and the seventh MOS tube is connected with one input end of the filter, and a connection point between the sixth MOS tube and the eighth MOS tube is connected with the other input end of the filter through the equivalent inductor; the method comprises the following steps: when the direct current-to-alternating current conversion or the high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the third direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply, the second direct current power supply and the third direct current power supply at the input side, so that the effect of multi-level conversion is achieved; alternatively, the method comprises: when alternating current-to-direct current conversion or high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the third direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply, the second direct current power supply and the third direct current power supply at the output side, so that the effect of multi-level conversion is achieved.
4. The control method of the conversion circuit is characterized in that the conversion circuit comprises a first direct current power supply, a second direct current power supply, a first capacitor, a second capacitor, a first MOS tube, a third MOS tube, a fifth MOS tube, a sixth MOS tube, a seventh MOS tube, an eighth MOS tube, a driving module, a control module, an isolation transformer circuit and a secondary side circuit, wherein the first direct current power supply, the second direct current power supply, the first capacitor and the second capacitor are respectively connected in series between a positive bus and a negative bus, a connection point between the first direct current power supply and the second direct current power supply is connected with a connection point between the first capacitor and the second capacitor, a source electrode of a third MOS tube is connected with a drain electrode of a fifth MOS tube, a source electrode of the fifth MOS tube is connected with a drain electrode of a seventh MOS tube, a source electrode of the first MOS tube is connected with a drain electrode of the third MOS tube and a drain electrode of the sixth MOS tube, a drain electrode of the first MOS tube is connected with a positive bus, a source electrode of the sixth MOS tube is connected with a source electrode of the eighth MOS tube, a connection point between the first MOS tube and the transformer circuit of the eighth MOS tube is connected with a source electrode of the eighth MOS tube, a connection point between the fifth MOS tube and the secondary side of the fifth MOS tube is connected with the eighth MOS tube, a source of the fifth MOS tube is connected with a connection point of the fifth MOS tube, and the isolation module is connected with the primary side of the fifth MOS tube is connected with the eighth MOS tube; the method comprises the following steps: when DC-AC conversion or high-frequency isolation type DC-DC conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first DC power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second DC power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first DC power supply and the second DC power supply at the input side, so that the effect of multi-level conversion is achieved; alternatively, the method comprises: when alternating current-to-direct current conversion or high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the output side, so that the effect of multi-level conversion is achieved.
5. The control method of the conversion circuit is characterized in that the conversion circuit comprises a first direct current power supply, a second direct current power supply, a first capacitor, a second MOS tube, a fourth MOS tube, a fifth MOS tube, a sixth MOS tube, a seventh MOS tube, an eighth MOS tube, a driving module, a control module, an isolation transformer circuit and a secondary side circuit, wherein the first direct current power supply, the second direct current power supply, the first capacitor and the second capacitor are respectively connected in series between a positive bus and a negative bus, a connection point between the first direct current power supply and the second direct current power supply is connected with a connection point between the first capacitor and the second capacitor and a drain electrode of the fourth MOS tube, a source electrode of the seventh MOS tube is connected with a source electrode of the fifth MOS tube, a source electrode of the second MOS tube is connected with a negative bus, the drain electrode of the second MOS tube is connected with the source electrode of the fourth MOS tube and the source electrode of the eighth MOS tube, the drain electrode of the eighth MOS tube is connected with the source electrode of the sixth MOS tube, the drain electrode of the fifth MOS tube and the drain electrode of the sixth MOS tube are connected with a positive bus, the grid electrodes of the second MOS tube, the fourth MOS tube, the fifth MOS tube, the sixth MOS tube, the seventh MOS tube and the eighth MOS tube are respectively connected with the driving module, the driving module is connected with the control module, the connection point between the fifth MOS tube and the seventh MOS tube is connected with the first end of the primary of the isolation transformer circuit, the connection point between the sixth MOS tube and the eighth MOS tube is connected with the second end of the primary of the isolation transformer circuit, and the secondary side of the isolation transformer circuit is connected with the secondary side circuit; the method comprises the following steps: when DC-AC conversion or high-frequency isolation type DC-DC conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first DC power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second DC power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first DC power supply and the second DC power supply at the input side, so that the effect of multi-level conversion is achieved; alternatively, the method comprises: when alternating current-to-direct current conversion or high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the output side, so that the effect of multi-level conversion is achieved.
6. A control method of a conversion circuit is characterized in that the conversion circuit comprises a first direct current power supply, a second direct current power supply, a third direct current power supply, a first capacitor, a second capacitor, a third capacitor, a first MOS tube, a second MOS tube, a third MOS tube, a fourth MOS tube, a fifth MOS tube, a sixth MOS tube, a seventh MOS tube, an eighth MOS tube, a driving module, a control module, an isolation transformer circuit and a secondary side circuit, wherein the second direct current power supply, the first direct current power supply and the third direct current power supply are sequentially connected in series between a negative bus and a positive bus respectively, a connection point between the first direct current power supply and the third direct current power supply is connected with a connection point between the first capacitor and the third capacitor, a source electrode of the third MOS tube and a drain electrode of the fifth MOS tube, the source electrode of the fifth MOS tube is connected with the drain electrode of the seventh MOS tube, the source electrode of the first MOS tube is connected with the drain electrode of the third MOS tube and the drain electrode of the sixth MOS tube, the drain electrode of the first MOS tube is connected with the positive bus, the source electrode of the sixth MOS tube is connected with the drain electrode of the eighth MOS tube, the source electrode of the seventh MOS tube is connected with the drain electrode of the fourth MOS tube, the connection point between the first DC power supply and the second DC power supply is connected with the connection point between the first capacitor and the second capacitor, the source electrode of the eighth MOS tube is connected with the source electrode of the fourth MOS tube and the drain electrode of the second MOS tube, the source electrode of the second MOS tube is connected with the positive bus, the gates of the first MOS tube, the second MOS tube, the third MOS tube, the fourth MOS tube, the fifth MOS tube, the sixth MOS tube, the seventh MOS tube and the eighth MOS tube are respectively connected with the driving module, the driving module is connected with the control module, a connection point between the fifth MOS tube and the seventh MOS tube is connected with a first end of a primary of the isolation transformer circuit, a second end of the primary connected with a connection point between the sixth MOS tube and the eighth MOS tube, and a secondary of the isolation transformer circuit is connected with the secondary side circuit; the method comprises the following steps: when the direct current-to-alternating current conversion or the high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the third direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the input side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply, the second direct current power supply and the third direct current power supply at the input side, so that the effect of multi-level conversion is achieved; alternatively, the method comprises: when alternating current-to-direct current conversion or high-frequency isolation type direct current-to-direct current conversion is carried out, a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the third direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply and the second direct current power supply at the output side, or a corresponding switching tube combination is turned on to form a conversion loop corresponding to the first direct current power supply, the second direct current power supply and the third direct current power supply at the output side, so that the effect of multi-level conversion is achieved.
7. The control method according to any one of claims 4 to 6, characterized in that the secondary side circuit is a full-bridge or half-bridge or full-wave rectifying circuit.
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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2009039733A1 (en) * 2007-09-26 2009-04-02 Huawei Technologies Co., Ltd. Direct current converter power supply apparatus and method for improving direct current converter power supply apparatus
CN103023366A (en) * 2012-11-19 2013-04-03 南京理工大学 Half-bridge five-electrical-level inverter and high-frequency insulation-type half-bridge five-electrical-level inverter
WO2014071674A1 (en) * 2012-11-09 2014-05-15 联合汽车电子有限公司 Direct-current isolation buck convertor and bus voltage detection circuit thereof
CN104578880A (en) * 2015-01-16 2015-04-29 深圳市保益新能电气有限公司 DC-AC conversion circuit and control method thereof
WO2016150245A1 (en) * 2015-03-23 2016-09-29 深圳市皓文电子有限公司 Dc/dc converter

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2009039733A1 (en) * 2007-09-26 2009-04-02 Huawei Technologies Co., Ltd. Direct current converter power supply apparatus and method for improving direct current converter power supply apparatus
WO2014071674A1 (en) * 2012-11-09 2014-05-15 联合汽车电子有限公司 Direct-current isolation buck convertor and bus voltage detection circuit thereof
CN103023366A (en) * 2012-11-19 2013-04-03 南京理工大学 Half-bridge five-electrical-level inverter and high-frequency insulation-type half-bridge five-electrical-level inverter
CN104578880A (en) * 2015-01-16 2015-04-29 深圳市保益新能电气有限公司 DC-AC conversion circuit and control method thereof
WO2016150245A1 (en) * 2015-03-23 2016-09-29 深圳市皓文电子有限公司 Dc/dc converter

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