CN108306840B - Phase jitter-based single carrier radar communication integrated signal implementation device - Google Patents

Phase jitter-based single carrier radar communication integrated signal implementation device Download PDF

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CN108306840B
CN108306840B CN201810094110.7A CN201810094110A CN108306840B CN 108306840 B CN108306840 B CN 108306840B CN 201810094110 A CN201810094110 A CN 201810094110A CN 108306840 B CN108306840 B CN 108306840B
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communication
communication sequence
integrated signal
radar
sequence
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CN108306840A (en
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周生华
梁雪玲
刘宏伟
刘军
刘美琪
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Xidian University
Xian Cetc Xidian University Radar Technology Collaborative Innovation Research Institute Co Ltd
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Xidian University
Xian Cetc Xidian University Radar Technology Collaborative Innovation Research Institute Co Ltd
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/20—Modulator circuits; Transmitter circuits
    • H04L27/2032—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner
    • H04L27/2035—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using a single or unspecified number of carriers
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/28—Details of pulse systems
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/41—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00 using analysis of echo signal for target characterisation; Target signature; Target cross-section

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  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Signal Processing (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)

Abstract

The invention discloses a phase jitter-based single carrier radar communication integrated signal implementation device, belongs to the technical field of radar communication, is suitable for solving the problem of overhigh range sidelobe level of a radar signal in an integrated signal and simultaneously completing radar detection and communication, and comprises a radar transmitting end, a communication receiving end and a radar receiving end, wherein the radar transmitting end is used for acquiring NsOptimal integrated signal matrix of communication sequences
Figure DDA0001564553300000011
The idea is as follows: obtaining a communication data stream, and cutting the communication data stream into NsA communication sequence, calculating NsAn integration signal of the communication sequences; wherein N issIs a positive integer greater than 1; according to NsIntegral signal of communication sequence, calculating NsAn integrated signal autocorrelation sidelobe level vector of each communication sequence; according to NsAn integrated signal autocorrelation sidelobe level vector of each communication sequence constructs NsAn objective optimization function for each communication sequence; optimizing NsAn objective optimization function of the communication sequence to obtain NsOptimal integrated signal matrix of communication sequences
Figure DDA0001564553300000012

Description

Phase jitter-based single carrier radar communication integrated signal implementation device
Technical Field
The invention belongs to the technical field of radar communication, and particularly relates to a phase jitter-based single carrier radar communication integrated signal implementation device which is suitable for solving the problem that the range sidelobe level of a radar signal in an integrated signal is too high and simultaneously completing radar detection and communication.
Background
At present, the research content of radar communication integration at home and abroad can be summarized into three modes, namely a time-sharing system implementation mode, a beam-splitting system implementation mode and a simultaneous system implementation mode according to different implementation modes of an integrated system; of the three integrated system implementation modes, the simultaneous system implementation mode is the most widely researched implementation mode at present.
The system implementation mode refers to a system that the radar signal and the communication signal use the same waveform together or synthesize one waveform in an orthogonalization mode, so that the system has a communication function and does not influence the original radar performance; the existing integration method of the simultaneous system mainly aims at continuous signals, such as LFM sequences, to influence communication bandwidth, and a transmitting end is greatly changed, but the error rate is inevitably improved.
Disclosure of Invention
In view of the problems in the prior art, the present invention provides a phase jitter-based single carrier radar communication integrated signal implementation apparatus, which is an integrated signal design method for performing phase jitter on a discrete signal to obtain a simultaneous system based on the existing method, that is, performing small-amplitude jitter on a phase of a transmission communication signal to improve detection performance, and the method does not affect communication bandwidth, and has a small change at a transmitting end, but inevitably improves bit error rate. The technical idea for realizing the invention is as follows: and designing an integrated signal by taking the minimum autocorrelation sidelobe level as a criterion.
In order to achieve the technical purpose, the invention is realized by adopting the following technical scheme.
A single carrier radar communication integrated signal implementation device based on phase jitter comprises a radar transmitting end, a communication receiving end and a radar receiving end, wherein the radar transmitting end is respectively connected with the communication receiving end and the radar receiving end, and the communication receiving end is connected with the radar receiving end;
the radar transmitting terminal is used for acquiring NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000011
Said N issOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000012
In which contains NsThe system comprises a plurality of single carriers, a phase jitter-based single carrier radar communication integrated signal and a phase jitter-based single carrier radar communication integrated signal;
in the case of radar transceiver antenna integration, NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000021
Directly entering a radar receiving end, wherein the processing flow of the radar receiving end is as follows: firstly, receiving N by a radar receiving endsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000022
N to be receivedsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000023
Directly sending the signal to a radar processing channel for filtering to obtain a radar signal; then, performing distance compression on the obtained radar signal in the distance direction to obtain a radar signal after the distance compression; finally, calculating the radar range resolution and the radar fuzzy function of the radar signal after the range compression;
with separate radar transmitting and receiving antennas, NsA maximum of communication sequencesExcellent integration signal matrix
Figure BDA0001564553280000024
Respectively entering a communication receiving end and a radar receiving end; the processing flows of the communication receiving end and the radar receiving end are respectively as follows:
the processing flow of the communication receiving end is as follows: first, the communication receiving end receives NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000025
N to be received latersOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000026
Making a decision, i.e. on NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000027
Carrying out real part operation on each optimal integrated signal, and judging as a 1 code element if the optimal integrated signal is greater than 0; otherwise, judging as 0 code element; to obtain NsA communication sequence; then for the NsSequentially arranging the communication sequences to obtain communication data streams; finally, calculating the communication error rate of the communication data stream;
the processing flow of the radar receiving end is as follows: n obtained by judging communication receiving endsThe phase jitter vectors of the communication sequences and the corresponding communication sequences are respectively subjected to dot multiplication, and N is obtained through calculationsCompressing the weight value by each distance; then use NsA distance compression weight pair NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000028
Performing distance compression to obtain a radar signal after the distance compression; and finally, calculating the radar range resolution and the radar fuzzy function of the radar signal after the range compression.
Wherein said N issOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000029
The obtaining process comprises the following steps:
step 1, obtaining communication data flow, and cutting the communication data flow into NsA communication sequence, calculating NsAn integration signal of the communication sequences; wherein N issIs a positive integer greater than 1;
step 2, according to NsIntegral signal of communication sequence, calculating NsAn integrated signal autocorrelation sidelobe level vector of each communication sequence;
step 3, according to NsAn integrated signal autocorrelation sidelobe level vector of each communication sequence constructs NsAn objective optimization function PSL for each communication sequence;
step 4, optimizing NsThe target optimization function PSL of each communication sequence obtains NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000031
The invention has the beneficial effects that: the method of the invention adopts a phase jitter method to modulate a discrete communication sequence, thereby providing a certain degree of freedom for optimization; the phase jitter is to satisfy the radar function, namely the low range sidelobe level can increase the range resolution and prevent the high-power target echo from submerging the low-power target echo in the nearby range unit; in addition, the method of the invention also has higher communication code element rate and lower distance compression calculated amount, and is compatible with the existing communication receiver, thereby saving the cost.
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The present invention will be described in further detail with reference to the accompanying drawings and specific embodiments.
FIG. 1 is a scheme for obtaining NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000032
A flow chart of (1);
FIG. 2 is a block diagram of a transceiving process of a single carrier radar communication integrated signal implementation device based on phase jitter;
FIG. 3 is a PSL comparison before and after phase dithering;
FIG. 4 is a diagram of a symbol profile after a communication sequence has been phase jitter modulated;
FIG. 5 is a graph comparing the optimal, median and worst PSL after phase dithering;
fig. 6 is a PSL distribution histogram after phase jitter modulation is performed on 256 randomly selected communication sequences respectively;
FIG. 7 is a PSL comparison graph of randomly generated communication sequences at different phase jitter amplitudes;
FIG. 8 is a PSL comparison graph of an all 1 communication sequence at different phase jitter amplitudes;
fig. 9 is a graph of upper and lower bounds of BER versus PSL for different phase jitter amplitudes.
Detailed Description
The invention discloses a phase jitter-based single carrier radar communication integrated signal implementation device which comprises a radar transmitting end, a communication receiving end and a radar receiving end, wherein the radar transmitting end is respectively connected with the communication receiving end and the radar receiving end, and the communication receiving end is connected with the radar receiving end.
The radar transmitting terminal is used for acquiring NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000033
Said N issOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000034
In which contains NsThe system comprises a plurality of single carriers, a phase jitter-based single carrier radar communication integrated signal and a phase jitter-based single carrier radar communication integrated signal; in the case of co-location, i.e. integration of radar transmitting and receiving antennas, NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000035
Directly entering a radar receiving end; because the transmitting and receiving antennas are integrated, the antenna is quite equivalent to the communicationSelf-sending and self-receiving; the processing flow of the radar receiving end is as follows: firstly, receiving N by a radar receiving endsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000036
Since the phase jitter vector is exactly known to the receiving end, N will be receivedsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000041
Directly sending the signal to a radar processing channel for filtering to obtain a radar signal; then, performing distance compression on the obtained radar signal in the distance direction to obtain a radar signal after the distance compression; and finally, performing subsequent processing of radar functions on the radar signals subjected to distance compression, such as distance resolution calculation, fuzzy function calculation and the like.
Spatial separation, i.e. separation of the radar transmitting and receiving antennas, NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000042
Respectively entering a communication receiving end and a radar receiving end, wherein the radar receiving end depends on the processing data obtained by the communication receiving end under the condition; the processing flows of the communication receiving end and the radar receiving end are respectively as follows:
the processing flow of the communication receiving end is as follows: first, the communication receiving end receives NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000043
N to be received latersOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000044
Sent to the communication processing channel for decision, i.e. to NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000045
Carrying out real part operation on each optimal integrated signal, and judging as a 1 code element if the optimal integrated signal is greater than 0; otherwise, judging as 0 code element; to obtain NsA communication sequence; then for the NsSequentially arranging the communication sequences to obtain communication data streams; and finally, carrying out subsequent processing of a communication function on the communication data stream, wherein the subsequent processing mainly refers to calculating the communication error rate.
The processing flow of the radar receiving end is as follows: for a radar processing channel, N obtained according to the judgment of a communication receiving end is neededsThe phase jitter vectors of the communication sequence and the corresponding communication sequence are respectively multiplied by one another, namely N obtained by judgment of a communication receiving endsThe phase jitter vectors of the communication sequences and the corresponding communication sequences are respectively subjected to dot multiplication, and N is obtained through calculationsCompressing the weight value by each distance; then use NsA distance compression weight pair NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000046
Performing distance compression to obtain a radar signal after the distance compression; finally, the radar signal after range compression may also be subjected to subsequent processing of radar functions, such as calculating range resolution, fuzzy functions, and the like.
Referring to FIG. 1, to obtain NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000047
A flow chart of (1); wherein said N is obtainedsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000048
The method comprises the following steps:
step 1, obtaining communication data flow, and cutting the communication data flow into NsA communication sequence, calculating NsA unified signal of communication sequences.
1a) Randomly generating a communication data stream using a data generator, slicing said communication data stream into NsA communication sequence eachThe number of code elements contained in each communication sequence is Nc，Nc＝64。
1b) Selecting NsThe ith communication sequence s of the communication sequencesi，
Figure BDA0001564553280000051
i＝1,2,...,Ns，
Figure BDA0001564553280000052
Represents NcX 1-dimensional real vector, e represents belonging to, NcIndicating the number of symbols, N, contained in each communication sequencec、NsRespectively positive integers greater than 1.
1c) Calculating NsA unified signal of communication sequences, wherein the ith communication sequence siIs integrated signal of
Figure BDA0001564553280000053
The obtaining process comprises the following steps: using exp (jp)i) To NsThe ith communication sequence s of the communication sequencesiPerforming phase modulation to obtain the ith communication sequence siOf
Figure BDA0001564553280000054
The expression is as follows:
Figure BDA0001564553280000055
wherein, e represents a Hardmard product, exp (. circle.) represents an exponential function,
Figure BDA0001564553280000056
is an imaginary unit, piRepresenting the ith communication sequence siThe phase jitter vector of (a) is,
Figure BDA0001564553280000057
represents NcX 1-dimensional complex vector, e represents belonging; the ith communication sequence siN of (A)c X 1 complex phase ditheringVector piIs the ith communication sequence s under the criterion of minimizing the autocorrelation sidelobe level proposed in doctor ' MIMO radar waveform design ' of the university of Western's electronics and technologyiOf
Figure BDA0001564553280000058
The phase vector generated after optimization has an initial value of [ -B, B]A random value within a range; p (n) denotes the ith communication sequence siOf the phase jitter vector piThe nth element and the value range of [ -B, B [ -B [ ]]B represents the maximum amplitude of the phase jitter, and the value range of B is [0, pi/3 ]]，n∈{1,2,...,Nc}。
Step 2, according to NsIntegral signal of communication sequence, calculating NsAn integrated signal autocorrelation sidelobe level vector for each communication sequence.
2a) According to the ith communication sequence siOf
Figure BDA0001564553280000059
Calculating the ith communication sequence siIntegral signal self-correlation side lobe level r of middle k code elementi,kThe expression is as follows:
Figure BDA00015645532800000510
wherein, (.)HDenotes conjugate transposition, JkRepresenting the ith communication sequence siThe sliding matrix of the kth symbol is expressed as:
Figure BDA00015645532800000511
Figure BDA00015645532800000515
represents (N)c-k) x k dimensional all-zero matrix, 0k×kRepresenting a k x k dimensional all-zero matrix,
Figure BDA00015645532800000512
represents k × (N)cAll zeros in-k) dimensionThe matrix is a matrix of a plurality of matrices,
Figure BDA00015645532800000513
represents Nc-an identity matrix of order k, NcIndicating the number of symbols contained in each communication sequence,
Figure BDA00015645532800000514
representing the ith communication sequence siThe integrated signal of (1).
2b) Let the value of k take 1 to N respectivelyc-1, repeating 2a), obtaining the ith communication sequence siIntegrated signal autocorrelation sidelobe level r of middle 1 st code elementi,1To the ith communication sequence siMiddle Nc-integrated signal autocorrelation sidelobe levels of 1 symbol
Figure BDA0001564553280000061
Denoted as the ith communication sequence siIntegrated signal autocorrelation sidelobe level vector ri，
Figure BDA0001564553280000062
i＝1,2,...,Ns，NsRepresenting the number of communication sequences contained in the cut communication data stream, (-)TRepresents a conjugate transpose; the value of k is then initialized to 1.
2c) Let the value of i take 1 to N respectivelysSequentially and repeatedly executing 2a) and 2b) to respectively obtain a 1 st communication sequence s1Integrated signal autocorrelation sidelobe level vector r1To NthsA communication sequence
Figure BDA0001564553280000063
Integrated signal autocorrelation sidelobe level vector
Figure BDA0001564553280000064
Is marked as NsAn integrated signal autocorrelation sidelobe level vector for each communication sequence.
Step 3, according to NsThe integrated signal autocorrelation sidelobe level vector of the communication sequence is minimizedConstructing N by taking peak sidelobe level as a criterionsThe target optimization function PSL of each communication sequence is expressed as:
Figure BDA0001564553280000065
wherein | | | purple hairpRepresents p norm, which is infinite norm in this embodiment; r isiRepresenting the ith communication sequence siIntegrated signal autocorrelation side lobe level vector, PSLiRepresents the ith element in the target optimization function PSL, | · | represents the modulus value, p (n) represents the ith communication sequence siN of (A)c X 1 complex phase jitter vector piThe nth element in (a), B represents the maximum amplitude of the phase jitter, N ∈ {1,2cDenotes the constraint condition,
Figure BDA0001564553280000066
represents the PSLiP corresponding to minimum valueiAnd (5) carrying out value taking operation.
Step 4, optimizing NsThe target optimization function PSL of each communication sequence obtains NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000067
Specifically, the ith communication sequence s is obtained by solving according to the SQP algorithmiThe SQP algorithm can find a local minimum solution in a short time, but the generation of the result depends on an initial value, so that the initial value needs to be set for the phase jitter vector for multiple times when solving the phase jitter vector of each communication sequence, and then optimization is performed, and finally the phase jitter vector with the minimum peak side lobe level is selected as the final optimization result of the communication sequence.
4a) Initialization: setting the number of code elements contained in each communication sequence to be Nc，Nc64; setting the cycle number of each communication sequence in solving the phase jitter vector which is most matched with the communication sequence to be M, and setting the communication sequence to be communicatedContaining N after data stream slicingsA communication sequence, Ns256; one of the communication sequences is randomly selected and is marked as a communication sequence sc(ii) a Setting the highest sidelobe flag to infinity; let l denote the l-th cycle, with the initial value of l being 1,2, …, M being a positive integer greater than 1.
4b) Calculating the first cycle initialization communication sequence scOf the phase jitter vector, i.e. the communication sequence scEach element in the phase jitter vector is randomly selected from-B to-B, and the initialized result is recorded as the communication sequence s after the first circulationcOf the phase jitter vector pcAnd then calculating to obtain a communication sequence s based on the phase jitter method after the first circulationcNon-optimized radar communication integrated signal
Figure BDA0001564553280000071
The expression is as follows:
Figure BDA0001564553280000072
4c) optimizing communication sequence s after first circulation by using sequence quadratic programming algorithmcOf the phase jitter vector pcTo obtain the first sub-optimized communication sequence scOf the phase vector po(ii) a The cycle times are equal to the optimization times and correspond to one another.
4d) Comparing the first post-optimization communication sequences scOf the phase vector poThe highest sidelobe and the highest sidelobe flag of if the l-th sub-optimal communication sequence scOf the phase vector poIs greater than or equal to the highest sidelobe flag, ignore, add 1 to the value of l, return to 4 b).
If the l-th sub-optimal communication sequence scOf the phase vector poIf the highest sidelobe is smaller than the highest sidelobe mark, the first communication sequence s after the second optimization is obtained by calculationcOf
Figure BDA0001564553280000073
And then calculating the communication sequence s after the first optimizationcIntegrated letter ofNumber autocorrelation sidelobe
Figure BDA0001564553280000074
Wherein the l-th post-optimization communication sequence scIntegrated signal autocorrelation sidelobe of the kth symbol
Figure BDA0001564553280000075
Representing the l-th sub-optimal communication sequence scThe sliding matrix of the k-th symbol in (c),
Figure BDA0001564553280000076
Figure BDA00015645532800000710
represents (N)c-k) x k dimensional all-zero matrix, 0k×kRepresenting a k x k dimensional all-zero matrix,
Figure BDA0001564553280000077
represents k × (N)c-k) a dimensional all-zero matrix,
Figure BDA0001564553280000078
represents Nc-an identity matrix of order k, NcIndicating the number of symbols contained in each communication sequence.
The first post-optimization communication sequence s is then calculatedcThe integrated signal autocorrelation sidelobe levels of (1), wherein the first post-optimization communication sequence scIntegrated signal autocorrelation sidelobe level of the kth symbol
Figure BDA0001564553280000079
Figure BDA0001564553280000081
Add 1 to the value of l, return 4 b).
Ending until the M times of circulation to obtain the M second optimized communication sequence scAnd then comparing the 1 st sub-optimized communication sequence scIntegrated signal autocorrelation sidelobe level to Mth sub-optimal back-passSignal sequence scThe autocorrelation side lobe level of the integrated signal of (1) is taken as the autocorrelation side lobe level with the minimum value in the autocorrelation side lobe level of the integrated signal of (1) and a communication sequence scThe best-matched phase jitter vector, denoted as communication sequence scMatched phase jitter vector popt。
4e) Calculating a communication sequence scOf the optimal integration signal
Figure BDA0001564553280000082
As indicates a Hardmard product, exp (-) indicates an exponential function,
Figure BDA0001564553280000083
is an imaginary unit, and the value of l is initialized to 1; said communication sequence scOf the optimal integration signal
Figure BDA0001564553280000084
Is a single carrier.
4f) Because the total number of the selected communication sequences is NsThen the communication sequence scRespectively taken as the 1 st communication sequence to the Nth communication sequencesRepeating the communication sequences from 4b) to 4e), and further respectively obtaining the optimal integrated signal from the 1 st communication sequence to the Nth communication sequencesThe optimal integrated signal of a communication sequence, denoted as NsOptimal integrated signal matrix of communication sequences
Figure BDA0001564553280000085
Figure BDA0001564553280000086
Represents Nc×NsA matrix of complex numbers is maintained.
Calculating the error rate of the communication receiving end as shown in fig. 2; the inevitable phase jitter increases the communication error rate; if N is presentsThe communication sequence has a general real amplitude α at the receiving end of the communication, and the received signal expression is:
xh＝αsh+nh h＝1,2,...,Nc
wherein x ishTo representReceiving the h-th symbol, s, of the signal vectorhRepresenting the h-th symbol, n, in the echo signal vectorhDenotes the h symbol noise in the channel noise vector, assuming that the h symbol noise in the channel noise vector follows a complex gaussian distribution with zero mean, normalized to 1 in variance.
When Re (x)h)>The 0-time symbol is decided as 1; otherwise, the value is judged to be 0, wherein Re (·) represents the real part.
Given a real amplitude α, a symbol error rate in the received signal vector is
Figure BDA0001564553280000087
After phase dithering, the error rate of a single symbol will increase to erfc (α cos (p (n))). Then for one code length NcOf communication sequence of (a), average bit error rate esThe upper and lower bounds of (1) are as follows:
Figure BDA0001564553280000091
1,2, N for all hcWhen p (n) ± B and p (n) ± 0, equal signs are respectively true.
The effects of the present invention are further verified and explained by the following simulation experiments.
In simulation, N is randomly selecteds256 communication sequences, each communication sequence of length NcPhase jitter modulation is carried out on the communication sequences respectively, each group of communication sequences takes an initial value of M-10 times, and in the fig. 3, 4, 5 and 6, the maximum jitter amplitude is set to be delta-pi/6; MATLAB software was used for the whole simulation process.
As can be seen from FIG. 3, the PSL value after phase dithering is reduced from-11.0 dB to-28.5 dB, which shows the effectiveness of the method, and indeed the side lobe level value of the sequence can be reduced, thereby meeting the requirement of radar detection function; fig. 4 is a symbol distribution diagram of the set of communication sequences after phase jitter modulation.
To further illustrate the method, fig. 5 shows the optimal PSL, the middle PSL, and the worst PSL contrast curves that can be achieved after the randomly selected 256 sets of communication sequences are respectively phase-jitter modulated; it can be seen that the worst PSL is-22.2 dB, which is about 6.3dB higher than the optimal PSL.
Fig. 6 shows a PSL distribution histogram of randomly selected 256 sets of communication sequences after phase jitter modulation, and fig. 6 shows that most communication sequences can obtain a PSL value less than-25 dB. Some communication sequences may not obtain a good phase jitter vector, and the PSL value is high; once such a communication sequence is transmitted, the radar processing unit will stop operating; however, as can be seen from fig. 6, such a sequence is only a small part and does not have a large influence on the radar function.
FIG. 7 shows the effect of different phase jitter amplitudes on the PSL; similarly, in consideration of randomly selecting 256 groups of communication sequences, the maximum jitter amplitude values are respectively Δ ═ pi/10, Δ ═ pi/6 and Δ ═ pi/3, and the optimal PSL value of the 256 groups of communication sequences under each jitter amplitude is obtained; it can be seen that the larger the phase jitter amplitude, the smaller the PSL value; and the PSL value at Δ ═ pi/6 is 2dB lower than that at Δ ═ pi/10, but the PSL values at Δ ═ pi/3 and Δ ═ pi/6 are not much different, indicating that the phase jitter amplitude should be within a certain range to suppress the side lobe level.
However, the final PSL value is not only related to the optimization process but also related to the original communication sequence, and in practice, the range side lobe of some communication sequences is difficult to suppress, such as all-1 sequence; thus fig. 8 shows the PSL values of the all 1 sequence at different phase jitter amplitudes; similarly to fig. 7, the maximum jitter amplitude still takes on values of Δ ═ pi/10, Δ ═ pi/6, and Δ ═ pi/3, respectively. It can be seen that under the phase jitter method, PSL is-1.3 dB when Δ ═ pi/10, PSL is-3.2 dB when Δ ═ pi/6, and PSL is-12.4 dB when Δ ═ pi/3; this compares to the PSL of the random communication sequence in fig. 7, the all 1 sequence still has difficulty suppressing the range side lobe by the phase dithering method; so that not all communication sequences are optimized in practice.
Next, considering the influence of the method of the present invention on the communication performance, in the simulation, the maximum amplitude B of the phase jitter takes a value of 0 to pi/3, and the real part amplitude α of the communication receiving end takes a value of 2, and the result is shown in fig. 9; as can be seen from fig. 9, as the amplitude of the phase jitter increases, the bit error rate increases and the distance PSL decreases; therefore, in practice, the two are considered in a trade-off according to specific environments.
In conclusion, the simulation experiment verifies the correctness, the effectiveness and the reliability of the method.
It will be apparent to those skilled in the art that various changes and modifications may be made in the present invention without departing from the spirit and scope of the invention; thus, if such modifications and variations of the present invention fall within the scope of the claims of the present invention and their equivalents, the present invention is also intended to include such modifications and variations.

Claims (2)

1. A single carrier radar communication integrated signal implementation device based on phase jitter is characterized by comprising a radar transmitting end, a communication receiving end and a radar receiving end, wherein the radar transmitting end is respectively connected with the communication receiving end and the radar receiving end;
the radar transmitting terminal is used for acquiring NsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000011
Said N issOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000012
In which contains NsThe system comprises a plurality of single carriers, a phase jitter-based single carrier radar communication integrated signal and a phase jitter-based single carrier radar communication integrated signal;
in the case of radar transceiver antenna integration, NsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000013
Directly entering a radar receiving end; the processing flow of the radar receiving end is as follows: firstly, receiving N by a radar receiving endsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000014
N to be receivedsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000015
Filtering to obtain radar signals; then, performing distance compression on the obtained radar signal in the distance direction to obtain a radar signal after the distance compression; finally, calculating the radar range resolution and the radar fuzzy function of the radar signal after the range compression; n is a radical ofsIs a positive integer greater than 1;
with separate radar transmitting and receiving antennas, NsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000016
Respectively entering a communication receiving end and a radar receiving end; the processing flows of the communication receiving end and the radar receiving end are respectively as follows:
the processing flow of the communication receiving end is as follows: first, the communication receiving end receives NsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000017
N to be received latersOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000018
Making a decision, i.e. on NsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000019
Carrying out real part operation on each optimal integrated signal, and judging as a 1 code element if the optimal integrated signal is greater than 0; otherwise, judging as 0 code element; to obtain NsA communication sequence; then for the NsThe communication sequences are arranged in sequence to obtain communicationA data stream; finally, calculating the communication error rate of the communication data stream;
the processing flow of the radar receiving end is as follows: n obtained by judging communication receiving endsThe phase jitter vectors of the communication sequences and the corresponding communication sequences are respectively subjected to dot multiplication, and N is obtained through calculationsCompressing the weight value by each distance; then use NsA distance compression weight pair NsOptimal integrated signal matrix of communication sequences
Figure FDA00027272790400000110
Performing distance compression to obtain a radar signal after the distance compression; finally, calculating the radar range resolution and the radar fuzzy function of the radar signal after the range compression;
said N issOptimal integrated signal matrix of communication sequences
Figure FDA00027272790400000111
The obtaining process comprises the following steps:
step 1, obtaining communication data flow, and cutting the communication data flow into NsA communication sequence, calculating NsAn integration signal of the communication sequences; wherein N issIs a positive integer greater than 1; comprising the following substeps:
1a) obtaining a communication data stream, and cutting the communication data stream into NsA communication sequence, each communication sequence comprising N number of code elementsc，NcIs a positive integer greater than 1;
1b) selecting NsThe ith communication sequence s of the communication sequencesi，
Figure FDA0002727279040000021
i＝1，2，...，Ns，
Figure FDA0002727279040000022
Represents NcX 1-dimensional real vector, e represents belonging to, NcIndicating the number of symbols, N, contained in each communication sequencec、NsAre respectively positive integers greater than 1;
1c) calculating NsA unified signal of communication sequences, wherein the ith communication sequence siIs integrated signal of
Figure FDA0002727279040000023
The obtaining process comprises the following steps: using exp (jp)i) To NsThe ith communication sequence s of the communication sequencesiPerforming phase modulation to obtain the ith communication sequence siOf
Figure FDA0002727279040000024
The expression is as follows:
Figure FDA0002727279040000025
wherein, e represents a Hardmard product, exp (. circle.) represents an exponential function,
Figure FDA0002727279040000026
is an imaginary unit, piRepresenting the ith communication sequence siThe phase jitter vector of (a) is,
Figure FDA0002727279040000027
represents NcX 1-dimensional complex vector, e represents belonging; p (n) denotes the ith communication sequence siOf the phase jitter vector piThe nth element in (N) is in the range of {1,2cB represents the maximum amplitude of the phase jitter, and the value range of B is [0, pi/3 ]]；
Step 2, according to NsIntegral signal of communication sequence, calculating NsAn integrated signal autocorrelation sidelobe level vector of each communication sequence;
step 3, according to NsAn integrated signal autocorrelation sidelobe level vector of each communication sequence constructs NsAn objective optimization function PSL for each communication sequence; said N issObject of a communication sequenceAn optimization function PSL, whose expression is:
Figure FDA0002727279040000028
Figure FDA0002727279040000029
s.t.|p(n)|≤B
wherein | | | purple hairpExpressing p norm which is set norm; r isiRepresenting the ith communication sequence siIntegrated signal autocorrelation side lobe level vector, PSLiRepresents the ith element in the target optimization function PSL, | · | represents the modulus value, p (n) represents the ith communication sequence siN of (A)cX 1 complex phase jitter vector piThe nth element in (a), B represents the maximum amplitude of the phase jitter, N ∈ {1,2cDenotes the constraint condition,
Figure FDA0002727279040000031
represents the PSLiP corresponding to minimum valueiCarrying out value taking operation;
step 4, optimizing NsThe target optimization function PSL of each communication sequence obtains NsOptimal integrated signal matrix of communication sequences
Figure FDA0002727279040000032
Comprising the following substeps:
4a) initialization: setting the number of code elements contained in each communication sequence to be NcSetting the cycle number of each communication sequence in solving the phase jitter vector most matched with the communication sequence to be M, and setting the communication data stream to contain N after being cutsA communication sequence; one of the communication sequences is selected and recorded as a communication sequence sc(ii) a Setting the highest sidelobe flag to infinity; let l denote the l-th cycle, with l having an initial value of 1,2, …, M being a positive integer greater than 1;
4b) calculating the first cycle initialization communication sequence scOf the phase jitter vector, i.e. the communication sequence scEach element in the phase jitter vector is randomly selected from-B to-B, and the initialized result is recorded as the communication sequence s after the first circulationcOf the phase jitter vector pcAnd then calculating to obtain a communication sequence s based on the phase jitter method after the first circulationcNon-optimized radar communication integrated signal
Figure FDA0002727279040000033
The expression is as follows:
Figure FDA0002727279040000034
wherein, e represents a Hardmard product, exp (. circle.) represents an exponential function,
Figure FDA0002727279040000035
is an imaginary unit;
4c) optimizing communication sequence s after first circulation by using sequence quadratic programming algorithmcOf the phase jitter vector pcTo obtain the first sub-optimized communication sequence scOf the phase vector po(ii) a The cycle times are equal to the optimization times and correspond to the optimization times one by one;
4d) comparing the first post-optimization communication sequences scOf the phase vector poThe highest sidelobe and the highest sidelobe flag of if the l-th sub-optimal communication sequence scOf the phase vector poIf the highest sidelobe is greater than or equal to the highest sidelobe mark, adding 1 to the value of l, and returning to 4 b);
if the l-th sub-optimal communication sequence scOf the phase vector poIf the highest sidelobe is smaller than the highest sidelobe mark, the first communication sequence s after the second optimization is obtained by calculationcCommunication integrated signal of
Figure FDA0002727279040000036
Figure FDA0002727279040000037
And then calculating the communication sequence s after the first optimizationcIntegrated signal autocorrelation sidelobe of
Figure FDA0002727279040000038
Wherein the l-th post-optimization communication sequence scIntegrated signal autocorrelation sidelobe of the kth symbol
Figure FDA0002727279040000039
Figure FDA00027272790400000310
Figure FDA00027272790400000311
Representing the l-th sub-optimal communication sequence scThe sliding matrix of the k-th symbol in (c),
Figure FDA0002727279040000041
Figure FDA0002727279040000042
represents (N)c-k) x k dimensional all-zero matrix, 0k×kRepresenting a k x k dimensional all-zero matrix,
Figure FDA0002727279040000043
represents k × (N)c-k) a dimensional all-zero matrix,
Figure FDA0002727279040000044
represents Nc-an identity matrix of order k, NcIndicating the number of symbols contained in each communication sequence;
the first post-optimization communication sequence s is then calculatedcThe integrated signal autocorrelation sidelobe levels of (1), wherein the first post-optimization communication sequence scIntegrated signal autocorrelation sidelobe level of the kth symbol
Figure FDA0002727279040000045
Figure FDA0002727279040000046
Adding 1 to the value of l, and returning to 4 b);
ending until the M times of circulation to obtain the M second optimized communication sequence scAnd then comparing the 1 st sub-optimized communication sequence scIntegrated signal autocorrelation sidelobe level to Mth post-optimization communication sequence scThe autocorrelation side lobe level of the integrated signal of (1) is taken as the autocorrelation side lobe level with the minimum value in the autocorrelation side lobe level of the integrated signal of (1) and a communication sequence scThe best-matched phase jitter vector, denoted as communication sequence scMatched phase jitter vector popt；
4e) Then calculating a communication sequence scOf the optimal integration signal
Figure FDA0002727279040000047
Figure FDA0002727279040000048
And initializing the value of l to 1; said communication sequence scOf the optimal integration signal
Figure FDA0002727279040000049
Is a single carrier;
4f) to communicate a sequence scRespectively taken as the 1 st communication sequence to the Nth communication sequencesRepeating the communication sequences from 4b) to 4e), and further respectively obtaining the optimal integrated signal from the 1 st communication sequence to the Nth communication sequencesThe optimal integrated signal of a communication sequence, denoted as NsOptimal integrated signal matrix of communication sequences
Figure FDA00027272790400000410
Figure FDA00027272790400000411
Figure FDA00027272790400000412
Represents Nc×NsA matrix of complex numbers is maintained.
2. The single carrier radar communication integrated signal realization device based on phase jitter according to claim 1, characterized by that, the substep of step 2 is:
2a) according to the ith communication sequence siOf
Figure FDA00027272790400000413
Calculating the ith communication sequence siIntegral signal self-correlation side lobe level r of middle k code elementi，kThe expression is as follows:
Figure FDA00027272790400000414
wherein, (.)HDenotes conjugate transposition, JkRepresenting the ith communication sequence siThe sliding matrix of the kth symbol is expressed as:
Figure FDA0002727279040000051
Figure FDA0002727279040000052
represents (N)c-k) x k dimensional all-zero matrix, 0k×kRepresenting a k x k dimensional all-zero matrix,
Figure FDA0002727279040000053
represents k × (N)c-k) a dimensional all-zero matrix,
Figure FDA0002727279040000054
represents Nc-an identity matrix of order k, NcIndicating the number of symbols contained in each communication sequence,
Figure FDA0002727279040000055
representing the ith communication sequence siThe integrated signal of (a);
2b) let the value of k take 1 to N respectivelyc-1, repeating 2a), obtaining the ith communication sequence siIntegrated signal autocorrelation sidelobe level r of middle 1 st code elementi，1To the ith communication sequence siMiddle Nc-integrated signal autocorrelation sidelobe levels of 1 symbol
Figure FDA0002727279040000056
Denoted as the ith communication sequence siIntegrated signal autocorrelation sidelobe level vector ri，
Figure FDA0002727279040000057
NsRepresenting the number of communication sequences contained in the cut communication data stream, (-)TRepresents a conjugate transpose; then initializing the k value to 1;
2c) let the value of i take 1 to N respectivelysSequentially and repeatedly executing 2a) and 2b) to respectively obtain a 1 st communication sequence s1Integrated signal autocorrelation sidelobe level vector r1To NthsA communication sequence s
Figure FDA0002727279040000058
Integrated signal autocorrelation sidelobe level vector
Figure FDA0002727279040000059
Is marked as NsAn integrated signal autocorrelation sidelobe level vector for each communication sequence.
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Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106772336A (en) * 2017-02-28 2017-05-31 西安电子科技大学 The radar detection system and implementation method integrated with communication check
CN107329130A (en) * 2017-06-26 2017-11-07 电子科技大学 A kind of signal processing method based on radar-communication integration system receiving terminal

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20090015349A1 (en) * 2007-07-12 2009-01-15 Ellis Thomas J Method and appartus for altering phase shift along a transmission line section

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106772336A (en) * 2017-02-28 2017-05-31 西安电子科技大学 The radar detection system and implementation method integrated with communication check
CN107329130A (en) * 2017-06-26 2017-11-07 电子科技大学 A kind of signal processing method based on radar-communication integration system receiving terminal

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
Joint Radar-Communications Waveform Multiple Access and Synthetic Aperture Radar Receiver;Andrew Herschfelt 等;《IEEE》;20171231;全文 *
OFDM 新体制雷达研究现状与发展趋势;霍凯 等;《电子与信息学报》;20151130;全文 *

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