CN107786062B - A kind of segmented cylinder-type transverse-flux linear motor - Google Patents
A kind of segmented cylinder-type transverse-flux linear motor Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
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Abstract
The invention discloses a kind of segmented cylinder-type transverse-flux linear motor, composition includes: that each phase is segmented primary iron core (1,2,3), each mutually segmentation secondary iron core (4,5,6), each phase armature winding (7,8,9) and permanent-magnet pole (10)；Each phase armature winding (7,8,9) is wound in the core tooth of each primary iron core (1,2,3) of phase segmentation respectively and constitutes electric motor primary, permanent-magnet pole (10) is laid on each phase segmentation secondary iron core (4,5,6) and constitutes motor secondary, it is characterized by: the linear electric motor primary and motor secondary are all made of by phase segmental structure, it is pressed the number of phases with the fan-shaped column structure of each mutually segmentation secondary iron core (4,5,6) and along motor circumference by each primary iron core (1,2,3) of mutually segmentationmEqual part is carried out, i.e., the radian of central angle shared by each phase is 2π/m, and magnetic separator (11) are filled between each mutually segmentation.This kind of New-type electric machine has biggish magnetomotive force, is conducive to improve motor power output, and then obtain higher thrust density.
Description
Technical field
The invention belongs to motor fields, and in particular to a kind of segmented cylinder-type transverse-flux linear motor.
Background technique
Linear motion system has a wide range of applications in the fields such as national defence, military project.With the development of science and technology, people
Increasingly higher demands are proposed to linear motion system, including thrust density is big, control characteristic is flexible, structure is simple, manufacture
It is easy.However the power for making linear motor is restricted for the linear motor of traditional magnetic structure, electric load and the mutual of magnetic loading
Density refractory is to be fundamentally improved.In terms of high torque density electrical machine, horizontal magnetic field motor development in recent years is very fast.
The domestic research about horizontal magnetic pass permanent magnetic line electromotor at present is seldom, the Zou Jibin professor of Harbin Institute of Technology
And its student has studied using U-shaped core construction transverse flux cylinder type linear motor, electric machine structure is simple, but adjacent two-phase
There is trough rim altogether between winding, there are the coupled problem of each phase winding, additionally due to twice of Neighboring primary core tooth unit interval is forever
Pole pitch, the utilization rate of permanent-magnet pole is not high and serious (Zou Jibin, Wang Qian, Zhang Hongliang the transverse flux linear motor electromagnetism of leakage field
The analysis of power and calculating [J] electrotechnics journal, 2007,22 (8)).The Kou Baoquan of Harbin Institute of Technology is taught and its student
Have studied the plate and cylinder-type transverse-flux linear permanent magnet synchronous motor of two-way interlinkage, the tooth of the electric motor primary core unit
Away from pole span is equal to, secondary permanent magnet can make full use of, effectively reduce interelectrode magnetic leakage, but electric machine structure complexity and adjacent winding
One section of core tooth is shared, there are coupled problems between different windings, and therefore, it is difficult to realize heterogeneous structure (Kou Baoquan, Yang Guolong, week
It ties up just, the two-way plate permanent magnet linear synchronous motor of interlinkage transverse magnetic flux [J] the Proceedings of the CSEE of Zhang He, 2012,33:
75-81+178., Kou Baoquan, Yang Guolong, Li Peng, the base of the two-way interlinkage transverse flux cylinder type linear permanent magnet synchronous motor of Zhang He
Plinth studies [J] Proceedings of the CSEE, 2012,36:61-67+13.).
In short, the existing transverse flux linear motor primary space utilization rate using core constructions such as traditional U-shaped, C-shapeds
Not high, the utilization rate of permanent magnet is relatively low, and permanent magnet interelectrode magnetic leakage is larger.In addition, they mostly there is also or structure is complicated,
The problems such as processing difficulties or not high armature winding effective length ratio, is also improved in power density and processing and manufacturing
Space.
For above situation, the present invention proposes a kind of segmented cylinder-type transverse-flux linear motor technical solution.
Summary of the invention
Technical problem solved by the invention is to provide a kind of segmented cylinder-type transverse-flux linear motor, it has
Higher permanent magnet utilization rate, improves permanent magnet interelectrode magnetic leakage, and can be realized higher power density and thrust density.
The technical solution for realizing the aim of the invention is as follows:
Segmented cylinder-type transverse-flux linear motor, composition include: that each phase is segmented primary iron core 1,2,3, each phase point
Section secondary iron core 4,5,6, each phase armature winding 7,8,9 and permanent-magnet pole 10；Each phase armature winding 7,8,9 is wound on each phase point respectively
Electric motor primary is constituted in the core tooth of the primary iron core 1,2,3 of section, permanent-magnet pole 10 is laid in structure in each phase segmentation secondary iron core 4,5,6
At motor secondary；Electric motor primary and motor secondary are all made of by phase segmental structure, and each primary iron core 1,2,3 that is mutually segmented mutually divides with each
It is simultaneously carried out equal part, i.e., the center of circle shared by each phase by number of phases m along motor circumference by the section fan-shaped column structure of secondary iron core 4,5,6
The radian at angle is 2 π/m, and is filled with magnetic separator 11 between each mutually segmentation.
It is each be mutually segmented primary iron core 1,2,3 by each phase primary iron core yoke 101,201,301, be located at each phase primary iron core yoke
101,3 column on 201,301 are dislocatedly distributed the core tooth of arrangement, including in each phase outer core tooth 102,202,302 and each phase
Between the pole shoe of core tooth 103,203,303 and iron core tooth ends, the pole including each 102,202,302 end of phase outer core tooth
The pole shoe 105,205,305 of boots 104,204,304 and each 103,203,303 end of phase middle core tooth.
Each U-shaped and T shape core construction for being mutually segmented primary iron core 1,2,3 and being arranged alternately on direction of motion v, i.e., it is same
Layout pitch inside column core tooth is 2 permanent-magnet poles away from 2 τ, with the outer core tooth 102,202,302 and middle core of phase
Dislocation distance between tooth 103,203,303 is 1 permanent-magnet pole away from τ.
Between each difference of phase armature winding 7,8,9 coiling in each phase in core tooth 103,203,303.
104,204,304 edge of pole shoe of each 102,202,302 end of phase outer core tooth is perpendicularly to the direction of movement v inwardly
Extend the surface for being connected across on each 102,202,302 end of phase outer core tooth of two column and covering permanent-magnet pole 10, iron among each phase
105,205,305 edge of pole shoe of 103,203,303 end of heart tooth is perpendicularly to the direction of movement v and extends over permanent-magnet pole 10 outward
Surface.
Permanent-magnet pole 10 alternately magnetizes by N-S to be sequentially arranged in each phase segmentation secondary iron core 4,5,6, and m column permanent-magnet pole 10
Respectively correspond m phase be segmented primary iron core 1,2,3, m phase be segmented secondary iron core 4,5,6 and m phase armature winding 7,8,9.
The m column permanent-magnet pole 10 that m phase is segmented in secondary iron core 4,5,6 is separately mounted to be dislocation arrangement along direction of motion v, and
Dislocation distance between any two column permanent-magnet pole 10 is 2 τ/m.
Compared with prior art, the present invention its remarkable advantage are as follows: 1) from principle, the magnetic flux plane of this kind of New-type electric machine
Be mutually perpendicular to the direction of motion, overcome due to electric load and magnetic loading spatially mutually restricts and what is generated is unfavorable for improving
The shortcomings that motor torque density, can be realized higher power density；2) from magnetic structure, electric motor primary iron core submission
For the U-shaped and T shape core construction of arrangement, the magnetic flux of interlinkage armature winding as caused by permanent magnetic potential by outer core tooth and
Middle core tooth two parts pair opposite polarity permanent-magnet pole generate jointly, have biggish magnetomotive force, be conducive to improve electricity
Machine power output, and then obtain higher thrust density；3) from by the sectional iron core being mutually segmented, which is respectively mutually segmented
Between it is mutually indepedent, and be filled with magnetic separator between each mutually segmentation, realize the magnetic insulation between each phase segmentation；4) from iron core
Seen in teeth portion structure, used iron core tooth ends pole shoe covers magnetic pole surfaces, the part of pole shoe face magnetic pole surfaces have compared with
Big surface area, magnetic pole utilization rate with higher effectively reduce interelectrode magnetic leakage, and have lesser air-gap reluctance in magnetic loop
With permanent-magnet pole magnetic resistance, more efficient energy conversion can be realized；5) from manufacturing process, which uses segmented circle cartridge type
Iron core yoke and staggered core tooth, not only can be used the mode of traditional silicon steel plate stacking, but also the new of machining can be used
Type soft-magnetic composite material (Soft Magnetic Composites, SMC) Lai Shixian, manufacturing process is simple, and armature winding knot
Structure is simple, can hand insertion, embedding is simple；6) from application, the control and adjusting of the speed of service are simple, are suitable for low
Fast high thrust directly drives occasion.By adjusting voltage, frequency etc., available different thrust and speed have stronger
Flexibility.
Detailed description of the invention
Fig. 1 is the structural schematic diagram of the segmented cylinder-type transverse-flux linear motor；
Fig. 2 (a) is the front view and relative dimensions mark that the A phase of the segmented cylinder-type transverse-flux linear motor is segmented
Note；
Fig. 2 (b) is the A-A cross-sectional view and relative dimensions that the A phase of the segmented cylinder-type transverse-flux linear motor is segmented
Mark；
Fig. 2 (c) is the B-B cross-sectional view and relative dimensions that the A phase of the segmented cylinder-type transverse-flux linear motor is segmented
Mark；
Fig. 3 (a) is that the A phase of the segmented cylinder-type transverse-flux linear motor is segmented primary iron core；
Fig. 3 (b) is the A phase armature winding of the segmented cylinder-type transverse-flux linear motor；
Fig. 4 is that the A phase of the segmented cylinder-type transverse-flux linear motor is segmented motor secondary；
Fig. 5 is the expanded view of A, B and C three-phase segmentation motor secondary of the segmented cylinder-type transverse-flux linear motor；
Fig. 6 (a) is flux circuit figure of the segmented cylinder-type transverse-flux linear motor at position 1；
Fig. 6 (b) is flux circuit figure of the segmented cylinder-type transverse-flux linear motor at position 2；
Fig. 7 is the equivalent magnetic circuit modeling of the segmented cylinder-type transverse-flux linear motor；
Fig. 8 is the three-dimensional explosion schematic diagram of the segmented cylinder-type transverse-flux linear motor.
In figure: 1 is segmented primary iron core for A phase, and 2 are segmented primary iron core for B phase, and 3 are segmented primary iron core for C phase, and 4 be A phase
It is segmented secondary iron core, 5 are segmented secondary iron core for B phase, and 6 are segmented secondary iron core for C phase, and 7 be A phase armature winding, and 8 be B phase armature
Winding, 9 be C phase armature winding, and 10 be permanent-magnet pole, and 11 be magnetic separator, and 101 be the primary iron core yoke of A phase, and 201 be the primary iron of B phase
Heart yoke, 301 be the primary iron core yoke of C phase, and 102 be A phase outer core tooth, and 202 be B phase outer core tooth, and 302 be iron outside C phase
Heart tooth, 103 be A phase middle core tooth, and 203 be B phase middle core tooth, and 303 be C phase middle core tooth, and 104 be iron outside A phase
The pole shoe of heart tooth ends, 204 be B phase outer core tooth ends pole shoe, 304 be C phase outer core tooth ends pole shoe, 105
It is the pole shoe of B phase middle core tooth ends for the pole shoe of A phase middle core tooth ends, 205,305 be C phase middle core tooth ends
Pole shoe, v is the direction of motion.
Specific embodiment
The method for solving of general electromagnetic problems has analytic method and numerical solution.Analytic method includes magnetic equivalent circuit method and layering
Modelling；Magnetic equivalent circuit method is a kind of method of traditional solution motor-field, expresses motor by way of drawing magnetic circuit figure
Magnetic field has the characteristics that clear concept, calculating are simple；Hierarchical mode method partial differential or integral equation describe electromagnetic field, so
Afterwards with the methods of separation of variable direct solution, its application is generally limited to boundary condition simply and medium is linear field
It closes.Numerical solution applicable surface is broader, can solve a large amount of Electromagnetic Field practical problem, modern age is with computer technology
Fast development, the specific gravity that numerical solution especially FInite Element accounts in machine analysis is increasing.But FEM calculation
Required time is very long, and it is huge especially to analyze the dimensional Finite Element time-consuming that horizontal magnetic pass permanent magnetic line electromotor must use
Greatly, thus analytic method for analysis horizontal magnetic pass permanent magnetic line electromotor for be also very important.Below based on motor itself
Relation equation, relevant design of electrical motor experience and magnetic equivalent circuit method provide solution segmented circle cartridge type transverse flux linear electricity
The technical solution of machine approximate size parameter.
Segmented cylinder-type transverse-flux linear motor, composition include: that each phase is segmented primary iron core 1,2,3, each phase point
Section secondary iron core 4,5,6, each phase armature winding 7,8,9 and permanent-magnet pole 10；Each phase armature winding 7,8,9 is wound on each phase point respectively
Electric motor primary is constituted in the core tooth of the primary iron core 1,2,3 of section, permanent-magnet pole 10 is laid in structure in each phase segmentation secondary iron core 4,5,6
At motor secondary；Electric motor primary and motor secondary are all made of by phase segmental structure, and each primary iron core 1,2,3 that is mutually segmented mutually divides with each
It is simultaneously carried out equal part, i.e., the center of circle shared by each phase by number of phases m along motor circumference by the section fan-shaped column structure of secondary iron core 4,5,6
The radian at angle is 2 π/m, and is filled with magnetic separator 11 between each mutually segmentation.Technical solution specific implementation is as follows:
1. key dimension parameter calculates
Output power equation is as follows:
In formula: Pout、UoAnd IoIt is output power, output phase voltage and the phase current of motor respectively；It is bearing power
Factor；M is the number of phases.
Ampere-conductors by the definition of specific electric load A, i.e., in armature circumference unit length, it is known that
In formula: N is the number of turns that is often connected in series of armature winding；RinIt is the radius of armature circumference.
Define proportionality coefficient ku=E/Uo, E is idle end voltage.Output power in formula (1-1) can be with is defined as:
If specific magnetic loading of the motor when primary core tooth and secondary permanent-magnet pole face is Bg1, according to linear motor
The enclosed middle core number N of teeth of primary part armature windingtWith enclosed primary core shoe area St, available total magnetic linkage is flat
Mean value are as follows:
Φ=Nt·Bg1·St (1-4)
When the thickness that each phase is segmented the magnetic separator between primary iron core between each mutually segmentation secondary iron core is ignored
When,
In formula: RinFor the inside radius of primary iron core, ltFor length of the primary core tooth on direction of motion v.
The fundametal compoment for only considering winding magnetic flux, derives the induced potential of the motor:
E=4KNmfNKwΦ (1-6)
In formula: KNmFor air-gap field waveform coefficient, 1.11 are equal to when air-gap field is Sine distribution；F is power frequency；
N is the number of turns that is often connected in series of armature winding；KwFor the winding coefficient of armature, the winding coefficient of this motor is 1；Φ is every phase magnetic
It is logical.
It can be obtained by (1-4)~(1-6) and f=v/ (2 τ):
In formula: v be Rated motor linear velocity, τ be motor secondary permanent-magnet pole away from.
Magnetic circuit when by motor operation is distributed it is found that the magnetic flux that middle core tooth is guided guides magnetic by outer core tooth
Twice of flux to ensure that the flux density inside motor is uniformly distributed, therefore considers that the sectional area of middle core tooth is outside when design
Twice of core tooth sectional area.Since core tooth is along the length l of the direction of motiontIt is approximately equal to length of the permanent-magnet pole along the direction of motion
lpm, in the case where ensuring that middle core tooth and outer core tooth have same flux density, if radian corresponding to middle core tooth
For α, then radian measure beta corresponding to outer core tooth=0.5 α.If radian measure gamma=β corresponding to primary core slots, then any phase is divided
Radian corresponding to the primary iron core of section or segmentation secondary iron core, i.e. radian corresponding to primary iron core yoke or secondary iron core yoke are
By (1-3) and (1-7), it is known that:
If lt=α Rin, then
If δpm=0.2 τ, lpm≈lt=τ-δpm, have
In addition, there are also following relationships: 2 π=3m α=6m β=6m γ, radian measure alpha corresponding to permanent-magnet polepm=3 α.Furthermore root
According to design of electrical motor experience, can obtain being segmented primary iron core yoke thickness he≈0.6Rinβ is segmented primary pole shoe thickness hb≈0.3Rinβ,
Gas length lg=0.5mm, groove depth hsIt can the parameters meter such as the radian measure gamma as corresponding to required electric current I, copper factor and primary core slots
It obtains, iron core tooth height ht=hs+hb, primary iron core outer radius Rout=Rin+ht+he.Thus the several of electric motor primary are obtained
Major parameter additionally needs the major parameter for determining motor secondary, such as permanent-magnet pole thickness hpm, secondary iron core outer radius rout, it is secondary
Iron core inside radius rinWith secondary iron core yoke thickness hr, wherein secondary iron core yoke thickness hrIt can suitably choose.As long as being aware of hpm, just
Other unknown parameters can be obtained, therefore according to the constraint relationship of motor geometrically in order to seek hpm, it is also necessary to it establishes as shown in Figure 7
Equivalent magnetic circuit modeling is analyzed.
2. equivalent magnetic circuit modeling
It is respectively flux circuit of the New-type electric machine in different location as shown in Fig. 6 (a) and 6 (b).To simplify meter
It calculates, ignores permanent-magnet pole leakage permeance, it is as shown in Figure 7 to obtain equivalent magnetic circuit modeling.Wherein, the magnetomotive force of permanent magnet is
FcN=FcS=Hchpm (1-12)
In formula: HcFor the coercivity of permanent-magnet pole；hpmFor the thickness of permanent-magnet pole.
RpmiAnd RpmoFor the magnetic resistance of permanent magnet；RrFor secondary iron core yoke portion magnetic resistance；RsFor primary rear of core magnetic resistance；RgiWith
RgoFor air-gap reluctance intermediate and between outer core tooth and permanent-magnet pole；RbiAnd RboRespectively middle core tooth and outer core
Tooth ends pole shoe magnetic resistance；RtiAnd RtoRespectively intermediate and outer core teeth portion magnetic resistance.
In formula: μ0、μpm、μfeIt is the magnetic conductivity of vacuum, permanent magnet and iron core respectively；lg、lpm、ltIt is respectively that air gap is long with τ
Degree, permanent-magnet pole the length of the direction of motion, core tooth the direction of motion length and permanent-magnet pole away from；α and β is respectively middle core
Radian corresponding to tooth and outer core tooth；hr、hpm、hb、hsAnd heRespectively secondary iron core yoke thickness, permanent-magnet pole thickness, iron core
Thickness, iron core tooth height or the groove depth of tooth ends pole shoe and primary iron core yoke thickness；RinFor the inside radius for being segmented primary iron core.
It is by total magnetic resistance that flux circuit can be obtained in the magnetic conductance of (1-13)~(1-22) flux circuit each section provided
Rm=Rr+Rpmi+Rpmo+Rgi+Rgo+Rbi+Rbo+Rti+Rto+Rs (1-23)
Total magnetic resistance RmIn include two components: known components Rm1With unknown components Rm2, respectively such as formula (1-24) and formula (1-
25) shown in
Rm1=Rgi+Rgo+Rbi+Rbo+Rti+Rto+Rs (1-24)
Equivalent magnetic circuit modeling as shown in Figure 7 can establish flux circuit equation
FCN+FCS=Φ Rm=Φ (Rm1+Rm2) (1-26)
Formula (1-24) and (1-25), which are substituted into (1-26), can find out the thickness h of permanent-magnet polepm。
In the thickness h for acquiring permanent-magnet polepmLater, the outer radius r of secondary iron core can be acquiredout=Rin-lg-hpm, secondary iron
The inside radius r of the heartin=rout-hr。
3. motor fabricates scheme
It is mainly made of following components according to the physical model of Fig. 1, the novel flat-plate type transverse flux linear motor:
Three-phase is segmented primary iron core 1,2,3, three-phase segmentation secondary iron core 4,5,6, threephase armature winding 7,8,9 and three column permanent-magnet poles 10.
By taking A phase is segmented as an example, provides A phase and be segmented shown in physical model such as Fig. 3 (a) of primary iron core 1, the entity mould of A phase armature winding 7
Shown in type such as Fig. 3 (b), the physical model that a column permanent-magnet pole 10 and A phase are segmented secondary iron core 4 is as shown in Figure 4.Wherein, A phase is segmented
Core tooth of the primary iron core 1 by A phase primary iron core yoke 101 and three column Heterogeneous Permutations, including two column 102 Hes of A phase outer core tooth
The pole shoe of one column A phase middle core tooth 103 and iron core tooth ends, 104 He of pole shoe including 102 end of A phase outer core tooth
The pole shoe 105 of 103 end of A phase middle core tooth, the permanent-magnet pole 10 that a column N-S alternately magnetizes are laid in A phase and are segmented secondary iron core 4
Upper surface.The plate transverse flux linear motor structure is simple, easily manufactured, and two processing system of the motor is given below
Make scheme:
Scheme one:
Although the A phase of the segmented cylinder-type transverse-flux linear motor is segmented primary iron core 1 by the primary iron core yoke of A phase
101 and three column Heterogeneous Permutation core tooth composition, but the basic cross section of the motor only there are two types of, respectively such as Fig. 2 (b) and 2
(c).The motor can be respectively obtained by way of silicon steel plate stacking along the motor of two kinds of varying cross-section shapes of direction of motion v
Segmentation, and along direction of motion v to laminate length be approximately a permanent-magnet pole away from τ, then by both varying cross-section shapes
Primary iron core segmentation alternately connection overlap together constitute A phase be segmented primary iron core 1；A phase 7 structures of armature winding are more simple
It is single, it can be wound on by way of hand insertion in an intermediate column core tooth；A phase, which is segmented secondary iron core 4, can also pass through silicon
The mode that steel disc laminates obtains, and the column N-S permanent-magnet pole 10 alternately to magnetize is finally laid in A phase and is segmented the upper of secondary iron core 4
Surface.
Scheme two:
In addition to machining can also be carried out using soft-magnetic composite material by the way of silicon steel plate stacking.Pass through first
The mode of machining obtains the primary iron core yoke 101 of A phase and three column core tooths, then slots and obtain on the primary iron core yoke 101 of A phase
The core slots of three column Heterogeneous Permutations, and the layout pitch of same row core slots is two permanent-magnet poles away from 2 τ, outer core slot is in
Between dislocation distance between core slots be a permanent-magnet pole away from τ；Then three column core tooths are imbedded on the primary iron core yoke 101 of A phase
Three column core slots in；A phase armature winding 7 is wound in an intermediate column core tooth by way of hand insertion；A
Mutually segmentation secondary iron core 4 can also be obtained by soft-magnetic composite material machining, the permanent-magnet pole that finally a column N-S alternately magnetizes
10 are laid in the upper surface that A phase is segmented secondary iron core 4.
4. the detent force of transverse flux linear motor is analyzed
Detent force is affected to the performance of transverse flux linear motor, its presence can make the thrust of motor that wave occur
It is dynamic, to generate vibration and noise；And when the frequency of detent force is consistent with the mechanical resonance frequency of stator or mover, vibration
It will be also amplified with noise.The presence of detent force equally affects motor low-speed performance in the controls and in position control
High accuracy positioning in system.Thus it is necessary to the detent forces to transverse flux linear motor to be analyzed.
The mechanism of production of horizontal magnetic field motor detent force and the mechanism of production of conventional permanent magnet motor location torque be it is the same,
But due to the particularity of its structure, so that the detent force period of horizontal magnetic field motor is different from conventional motors, below emphatically to it
It is analyzed.
The number of the ideal Cogging Torque of traditional permanent magnet rotating machine is the least common multiple of motor pole number 2P and slot number Z
Number.For transverse flux linear motor, due to being separated by twice of pole span between each stator component of motor, if ignoring the edge effect of motor
It answers, it is believed that it is the rotating electric machine that a radius is infinity, number of poles 2N, slot number are N, and wherein N tends to be infinitely great.According to
The theory of conventional motors location torque is analyzed it is found that the detent force number of transverse flux linear motor is 2N, namely positioning
The power period is τ, and wherein τ is the pole span of motor.
Above analysis is only applicable to single-phase transverse flux linear motor.For three-phase structure, following two feelings can be divided into
Condition:
(1) transverse flux linear motor three-phase Striking symmetry, spatially 120 ° of electrical angles of mutual deviation
Fourier decomposition is carried out to detent force caused by motor three-phase, can be obtained:
Wherein, x is the position where electric mover.
General orientation power caused by transverse flux linear motor is at this time
Therefore for the transverse flux linear motor of three-phase symmetrical, the detent force period is
(2) transverse flux linear motor asymmetrical three-phase
If b phase is θ with the spatially poor electrical angle of a phaseab, c phase is θ with the spatially poor electrical angle of a phaseac,
Fourier decomposition is carried out to detent force caused by motor three-phase, can be obtained:
At this timeTherefore the detent force of motor
Period is τ.
5. the lifting scheme of electromagnetic force
Why transverse flux linear motor obtains the common concern of people, and one of reason is exactly that it can be provided than passing
The much bigger force density of system linear motor.The special construction of transverse flux linear motor allows to by increasing motor number of pole-pairs
To improve the force density of motor.Principle is promoted below to analyze the electromagnetic force of transverse flux linear motor.
Fig. 2 (a) gives the front view of the motor.In the case where outside motor size constancy, the pole span τ of motor is subtracted
Half, so that motor pole number be made to double, correspondingly, stator stack the piece number is also doubled.
It is can be found that by research: in the mechanical movement speed v for guaranteeing motormUnder the premise of constant, if by mover permanent magnetism
Number of pole-pairs doubles, and in the case where not considering leakage field, the size for the magnetic flux that every circle conductor institute chain is crossed is constant, but its change rate
But one times is increased, thus every opposite potential doubles.In this way, in the case where motor electric load is constant, the electromagnetism of motor
Power will also double.Due toSo FemIt doubles, the electromagnetism force density of motor is mentioned
It is high.
But in fact, leakage field also can correspondingly increase in motor, to make in motor while increasing mover number of pole-pairs
Main flux reduce, winding induced electromotive force can also accordingly decrease.Therefore the increase of number of pole-pairs has a limit, i.e., until it
Until increase no longer increases back-emf.In addition, the increase of number of pole-pairs will lead to the drop of transverse flux linear motor power factor
It is low.Therefore when designing transverse flux linear motor, the selection of number of pole-pairs need to combine electromagnetism force density and power factor this
Two indexs.Under certain conditions, in order to obtain a higher power factor, it is necessary to sacrifice the electromagnetism force density of motor
For cost.In conclusion when motor number of pole-pairs increases, for transverse flux linear motor, in a certain range, electromagnetic force
Density correspondingly increases.
6. the mathematical model of transverse flux linear motor
In order to carry out the performance evaluation and Control System Design of motor, need to establish the novel flat-plate type transverse flux linear
The mathematical model of motor.Since transverse flux motor is one kind of synchronous motor, thus synchronous motor can be copied to carry out laterally
The modeling of flux linear motor.However when needing to count and magnetic field is saturated with factors such as armature-reactions, transverse flux linear motor
Mathematical model just become complex, need to consider the non-of the phase relation and inductance between winding back-emf and electric current at this time
It is linear to wait brought influence.A kind of relatively good method is exactly to be carried out according to the relation curve between motor magnetic linkage and electric current
The modeling of transverse flux linear motor indicates magnetic linkage caused by magnet steel by the concept of introducing " magnet steel equivalent current ", from
And obtain the mathematical model of motor with can be convenient.
In motor unsaturation, can be approximately considered is linear relationship between magnetic linkage and electric current caused by armature supply, this
When winding inductance be a constant.Due to being regarded as decoupling mutually between each phase of transverse flux linear motor, thus can be only to it
In a phase analyzed, in the case where not considering edge effect, can be obtained transverse flux linear motor flux linkage equations and electricity
It presses shown in equation such as formula (1-30).
In formula: λmpmFor the peak value of magnetic linkage caused by permanent magnet；LaFor winding inductance (when unsaturated)；λ be motor in forever
Total magnetic linkage caused by magnet and armature supply；The electric current that i is flowed through by armature winding；θ is the equivalent electric angle where mover
Degree,Position when x=0 is defined as the magnetic flux maximum of institute's linkage in stator component where mover；r
For the resistance of armature winding；U is winding applied voltage.
Carry out steady-state analysis, should determine the waveform of armature supply first.Due to the magnetic linkage of machine winding substantially press it is remaining
The variation of string rule, in order to guarantee that the power for inputting motor in one cycle is positive, armature supply should have following functional form:
I=-Im sin(θ+θt) (1-31)
Wherein
First formula of (1-30) and (1-31) are substituted into (1-30) second formula, and are converted into phasor shape
Formula can obtain voltage equation are as follows:
In formula:To hold voltage phasor, For winding induced electromotive force phasor, For electricity
Pivot electric current phasor,θtFor phasorWithBetween angle, referred to as angle of torsion；XaFor the induction reactance of armature winding,
Xa=ω La。
It is further simplified, can obtain
This does not consider voltage equation when transverse flux linear motor steady-state operation when saturation as.It can be seen that the party
The voltage equation of journey and implicit pole synchronous motor is quite similar, this also from illustrating that transverse flux linear motor is synchronous on the other hand
One kind of motor, thus the analysis method of synchronous motor can be copied to study transverse flux linear motor, this is for cross
Performance evaluation and control strategy research to flux linear motor have great importance.It is straight for the transverse magnetic flux of other structures
Line motor, as magneticfocusing structure can be synchronous using hybrid permanent magnet type is similar to when d-axis reactance and unequal quadrature axis reactance
The voltage equation of motor carries out the steady-state analysis of transverse flux linear motor, and which is not described herein again.
When the influence for needing to count and be saturated, the amplitude of magnetic linkage caused by permanent magnet is no longer a constant, but electric
Pivot electric current i and angle of torsion θtFunction；Meanwhile armature inductance LaAlso it will change with the variation of motor degree of saturation, be armature electricity
Flow i and angle of torsion θtFunction.These all make the modeling of transverse flux linear motor become complicated, and (1-33) is represented at this time
Voltage equation no longer be applicable in, other methods must be considered as to establish the mathematical model of transverse flux linear motor.
In fact, can regard transverse flux linear motor as hidden since the relative permeability of permanent magnetic steel is close to 1
Pole motor, thus motor magnetic linkage and its shape of the relation curve of armature supply are essentially identical when mover is in different location, it
Can be obtained by being translated mutually along horizontal axis.
When θ=90 °, magnet steel magnetic linkage caused by armature winding be 0, at this time in motor total magnetic linkage and electric current relationship
Curve can be indicated with multinomial:
By translating the curve, the relationship of motor magnetic linkage and electric current when mover is in different location can be obtained are as follows:
In formula, isIt is electric current related with permanent magnetic steel, is defined as " magnet steel equivalent current ".
When armature supply is 0, the magnetic linkage in motor is generated by magnet steel, at this time isMeet
As it can be seen that isIt is the function of rotor position angle θ, that is to say the function of rotor position x, size can passes through formula (1-36)
It determines.
In this way, following equation can be obtained:
This is the mathematical model for considering motor saturation and transverse flux linear motor when armature-reaction.Using the model,
The runnability of motor is analyzed with can be convenient.
Claims (5)
1. a kind of segmented cylinder-type transverse-flux linear motor, composition includes: that each phase is segmented primary iron core (1,2,3), each
Mutually segmentation secondary iron core (4,5,6), each phase armature winding (7,8,9) and permanent-magnet pole (10)；Each phase armature winding (7,8,9) is respectively
It is wound in the core tooth of each primary iron core (1,2,3) of phase segmentation and constitutes electric motor primary, permanent-magnet pole (10) is laid in each phase segmentation
Secondary iron core constitutes motor secondary on (4,5,6)；It is each be mutually segmented primary iron core (1,2,3) by each phase primary iron core yoke (101,
201,301) 3, positioned at each phase primary iron core yoke (101,201,301) on arrange the core tooths composition for the arrangement that is dislocatedly distributed；Iron core
Tooth includes each phase outer core tooth (102,202,302) He Gexiang middle core tooth (103,203,303) and iron core tooth ends
Pole shoe；Pole shoe includes iron among the pole shoe (104,204,304) and each phase of each phase outer core tooth (102,202,302) end
The pole shoe (105,205,305) of heart tooth (103,203,303) end；It is each to be mutually segmented primary iron core (1,2,3) on direction of motion v
The U-shaped and T shape core construction being arranged alternately, i.e. layout pitch inside same row core tooth are 2 permanent-magnet poles away from 2 τ, together
Dislocation distance between the outer core tooth (102,202,302) and middle core tooth (103,203,303) of phase is 1 permanent-magnet pole
Away from τ, it is characterised in that: the linear electric motor primary and motor secondary are all made of by phase segmental structure, each to be mutually segmented primary iron core
(1,2,3) are carried out it by number of phases m with each mutually segmentation secondary iron core (4,5,6) fan-shaped column structure and along motor circumference etc.
Point, i.e., the radian of central angle shared by each phase is 2 π/m, and is filled with magnetic separator (11) between each mutually segmentation.
2. segmented cylinder-type transverse-flux linear motor according to claim 1, it is characterised in that: the linear motor
Each phase armature winding (7,8,9) respectively between coiling in each phase in core tooth (103,203,303).
3. segmented cylinder-type transverse-flux linear motor according to claim 1, it is characterised in that: each phase outer core
The pole shoe (104,204,304) of tooth (102,202,302) end extends that be connected across two column each along being perpendicularly to the direction of movement v inwardly
On phase outer core tooth (102,202,302) end and cover the surfaces of permanent-magnet pole (10), each phase middle core tooth (103,203,
303) pole shoe (105, the 205,305) edge of end is perpendicularly to the direction of movement the surface that v extends over permanent-magnet pole (10) outward.
4. segmented cylinder-type transverse-flux linear motor according to claim 1, it is characterised in that: permanent-magnet pole (10) is pressed
N-S, which alternately magnetizes, to be sequentially arranged on each phase segmentation secondary iron core (4,5,6), and m column permanent-magnet pole (10) respectively corresponds m phase and is segmented
Primary iron core (1,2,3), m phase are segmented secondary iron core (4,5,6) and m phase armature winding (7,8,9).
5. segmented cylinder-type transverse-flux linear motor according to claim 1 or 4, it is characterised in that: install respectively
It is dislocation arrangement in the m column permanent-magnet pole (10) that m phase is segmented on secondary iron core (4,5,6) along direction of motion v, and any two column permanent magnetism
Dislocation distance between pole (10) is 2 τ/m.
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| CN108377083A (en) * | 2018-03-15 | 2018-08-07 | 鲁东大学 | A kind of cylindrical linear motor |
| CN108512392B (en) * | 2018-04-20 | 2021-02-09 | 中国矿业大学 | Cylindrical transverse flux switch reluctance linear motor with modular stator |
| CN109713872B (en) * | 2019-01-08 | 2021-02-02 | 河北科技大学 | High-thrust linear motor |
| CN113300564B (en) * | 2021-06-11 | 2022-10-21 | 哈尔滨工业大学 | High-power-factor transverse flux permanent magnet synchronous linear motor |
| CN113300566B (en) * | 2021-06-11 | 2023-07-07 | 哈尔滨工业大学 | Modularized transverse flux permanent magnet synchronous linear motor |
| CN117318432B (en) * | 2023-11-29 | 2024-02-20 | 湖南天友精密技术有限公司 | Dynamic magnetic type permanent magnet motor and control method |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE10062823A1 (en) * | 2000-12-15 | 2002-07-04 | Bob Bobolowski Gmbh | Multi-phase and multi-pole synchronous moving coil motor |
| CN101552534A (en) * | 2009-05-19 | 2009-10-07 | 哈尔滨工业大学 | Transverse flux cylinder type permanent magnet linear synchronous motor |
| CN101741216A (en) * | 2009-12-24 | 2010-06-16 | 哈尔滨工业大学 | Interphase electromagnetic decoupling cylindrical permanent magnet linear synchronous motor |
| CN101958633A (en) * | 2010-09-26 | 2011-01-26 | 华中科技大学 | Composite core-based primary permanent magnet synchronous linear motor |
| JP2012060756A (en) * | 2010-09-08 | 2012-03-22 | Mitsubishi Electric Corp | Linear motor |
| CN102664504A (en) * | 2012-05-09 | 2012-09-12 | 哈尔滨工业大学 | Polyphase permanent magnet motor with leakage reactance adjustable structure |
| CN105356720A (en) * | 2015-12-10 | 2016-02-24 | 山东大学 | Double-permanent-magnet lateral magnetic flux linear permanent magnet motor |
-
2016
- 2016-08-24 CN CN201610721371.8A patent/CN107786062B/en active Active
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE10062823A1 (en) * | 2000-12-15 | 2002-07-04 | Bob Bobolowski Gmbh | Multi-phase and multi-pole synchronous moving coil motor |
| CN101552534A (en) * | 2009-05-19 | 2009-10-07 | 哈尔滨工业大学 | Transverse flux cylinder type permanent magnet linear synchronous motor |
| CN101741216A (en) * | 2009-12-24 | 2010-06-16 | 哈尔滨工业大学 | Interphase electromagnetic decoupling cylindrical permanent magnet linear synchronous motor |
| JP2012060756A (en) * | 2010-09-08 | 2012-03-22 | Mitsubishi Electric Corp | Linear motor |
| CN101958633A (en) * | 2010-09-26 | 2011-01-26 | 华中科技大学 | Composite core-based primary permanent magnet synchronous linear motor |
| CN102664504A (en) * | 2012-05-09 | 2012-09-12 | 哈尔滨工业大学 | Polyphase permanent magnet motor with leakage reactance adjustable structure |
| CN105356720A (en) * | 2015-12-10 | 2016-02-24 | 山东大学 | Double-permanent-magnet lateral magnetic flux linear permanent magnet motor |
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