CN107167775A - One kind is based on the anti-multi-hop noise jamming waveform design method of cognitive radar - Google Patents
One kind is based on the anti-multi-hop noise jamming waveform design method of cognitive radar Download PDFInfo
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- CN107167775A CN107167775A CN201710368938.2A CN201710368938A CN107167775A CN 107167775 A CN107167775 A CN 107167775A CN 201710368938 A CN201710368938 A CN 201710368938A CN 107167775 A CN107167775 A CN 107167775A
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/023—Interference mitigation, e.g. reducing or avoiding non-intentional interference with other HF-transmitters, base station transmitters for mobile communication or other radar systems, e.g. using electro-magnetic interference [EMI] reduction techniques
Abstract
One kind is based on the anti-multi-hop noise jamming waveform design method of cognitive radar, and the present invention relates to anti-multi-hop noise jamming waveform design method.The invention aims to solve existing method to realize multi-hop clutter and the separation of target in certain limit, but part Doppler's detection interval is sacrificed simultaneously, interval size depends on multi-hop clutter extension width, influences the shortcoming of the normal detection of target.Process is：One：Radar outwards launches linear frequency modulation continuous wave signal, and radar carries out range Doppler two-dimensional process to echo-signal, obtains width and present position of the multi-hop clutter on doppler spectral in echo-signal；Two：Phase-modulation is carried out on the basis of Linear Frequency Modulation continuous wave, U is obtainedT(t)；Three phase code coefficients are tried to achieve according to the width of obtained multi-hop clutter, the compression of multi-hop clutter is realized；Three：To UT(t) quadratic phase coding is carried out, makes multi-hop clutter that there is controllable move on doppler spectral.The present invention is used for radar anti-clutter technical field.
Description
Technical field
The present invention relates to anti-multi-hop noise jamming waveform design method.
Background technology
Doppler processing is the committed step that high-frequency sky-wave over-the-horizon radar realizes target detection.However, due to sky wave thunder
There is the multi-hop clutter beyond range-folded phenomenon, radar power coverage up in transmitting procedure and pass through ionosphere and earth table
The multiple reflections in face enter formation doppler spread clutter in receiver.Usual echo signal backward energy is miscellaneous much smaller than multi-hop
Wave energy, therefore, when target Doppler frequency and the adjoining Doppler frequency residing for multi-hop clutter, strong multi-hop clutter can be
Echo signal is flooded on doppler spectral.Therefore, for ensure folded Clutter in Skywave Radars under multi-hop noise jamming it is normal to target detection with
Track, solving the influence of multi-hop clutter has important theory value and practical significance.
Waveform Design is to resist an effective measures of multi-hop noise jamming.20 end of the centurys, John T.Clancy are proposed
A kind of waveform design method of resistant to collapsing multi-hop clutter, it devises in a kind of arteries and veins phase-coded signal between linear frequency modulation arteries and veins, can
So that the Doppler frequency of different folding times echoes produces different frequency displacements after signal processing, made by parameter designing many
General Le multi-hop clutter is moved between aimless Doppler region, so as to realize normal detection of the rest interval to target.See
[Mitigation of range folded clutter by a nonrecurrent waveform.Clancy J T,
Bascom HF,Hartnett MP.Proc 1999IEEE Radar Conference.1999].It the method achieve multi-hop miscellaneous
Ripple and the separation of target in certain limit, but part Doppler's detection interval is sacrificed simultaneously, it is miscellaneous that interval size depends on multi-hop
Ripple extension width, this will influence the normal detection of target.
The content of the invention
It is same the invention aims to solve that existing method realizes that multi-hop clutter separates with target in certain limit
When sacrifice part Doppler's detection interval, due to interval size depend on multi-hop clutter extension width, so as to influence target
The shortcoming normally detected, and propose a kind of based on the anti-multi-hop noise jamming waveform design method of cognitive radar.
One kind is based on the cognitive anti-multi-hop noise jamming waveform design method detailed process of radar：
Step one：Radar outwards launches linear frequency modulation continuous wave signal, and receiver receives echo-signal, and radar is to echo
Signal carries out range Doppler two-dimensional process, obtains width l and multi-hop of the multi-hop clutter on doppler spectral in echo-signal
Clutter present position f on doppler spectralloction；
Step 2：Phase-modulation is carried out on the basis of the linear frequency modulation continuous wave of step one, three phases are adjusted between obtaining arteries and veins
Linear frequency modulation continuous wave signal waveform U after systemT(t)；Three phases are tried to achieve according to the width of the multi-hop clutter obtained in step one
Position code coefficient, realizes the compression of multi-hop clutter；
Step 3：Linear frequency modulation continuous wave signal waveform U the arteries and veins obtained step 2 after three phase-modulationsT(t)
Quadratic phase coding is carried out, makes multi-hop clutter that there is controllable move on doppler spectral.
Beneficial effects of the present invention are：
Phase-modulated signal is compressed to multi-hop clutter in doppler spectral between a kind of intra-pulse chirp arteries and veins of present invention design.This method
The priori of multi-hop clutter relevant parameter is obtained by cognitive radar first.According to phase modulation between obtained parameter designing arteries and veins because
Son, multi-hop clutter is compressed on doppler spectral, so that being greatly reduced on doppler spectral by multi-hop clutter Polluted area.
At the same time, the present invention also retains the function of being moved in background technology to multi-hop clutter, therefore multi-hop can be controlled miscellaneous
Ripple greatly improves detection performance of the radar to target in region residing for doppler spectral.By the waveform design method of the present invention,
Can meet simultaneously multi-hop clutter compression and carried out on doppler spectral it is controllable move, realize correct detection of the radar to target.
Solution existing method, which is realized, sacrifices part Doppler's detection interval while multi-hop clutter is separated with target in certain limit,
Because interval size depends on multi-hop clutter extension width, so as to influence the shortcoming of the normal detection of target.
Can be drawn according to Fig. 3 b can not all detect target between 175Hz to 339Hz, multi-hop clutter by target coverage,
Multi-hop clutter is removed using Fig. 3 a of the present invention and -390Hz to -406Hz is compressed to, Polluted area is reduced, and realizes radar
Correct detection to target.
It can be drawn according to Fig. 4 b and remove multi-hop clutter, but band width can not all be detected between -423Hz to -259Hz
Go out target, Polluted area is big, multi-hop clutter width pressure while multi-hop clutter multi-hop clutter is removed using Fig. 4 a of the present invention
- 390Hz to -406Hz is reduced to, Polluted area is reduced, and realizes correct detection of the radar to target.
Brief description of the drawings
Fig. 1 is the designed signal schematic representation of the present invention, ψ1For three phase code coefficient c1In first frequency modulation cycle T class
The first phase of interior imparting, ψ2For three phase code coefficient c1The first phase assigned in second frequency modulation cycle T class, ψnFor three phases
Position code coefficient c1The first phase assigned in n-th of frequency modulation cycle T class, ψn+1For three phase code coefficient c1In (n+1)th tune
The first phase assigned in frequency cycle T class, φ1For quadratic phase code coefficient c2The first phase assigned in first frequency modulation cycle T class,
φ2For quadratic phase code coefficient c2The first phase assigned in second frequency modulation cycle T class, φnFor quadratic phase code coefficient c2
The first phase assigned in n-th of frequency modulation cycle T class, φn+1For quadratic phase code coefficient c2In (n+1)th frequency modulation cycle T class
The first phase of imparting, f is frequency；
Fig. 2 is the designed signal transmitted wave of the present invention and echo schematic diagram, ψn+m-1For three phase code coefficient c1N-th
The first phase assigned in+m-1 frequency modulation cycle T classes, φn+m-1For quadratic phase code coefficient c2In the n-th+m-1 frequency modulation cycle T classes
The first phase of interior imparting, ψn+mFor three phase code coefficient c1The first phase assigned in the n-th+m frequency modulation cycle T classes, φn+mFor two
Secondary phase code coefficient c2The first phase assigned in the n-th+m frequency modulation cycle T classes, ψn+m+1For three phase code coefficient c1
The first phase assigned in n+m+1 frequency modulation cycle T class, φn+m+1For quadratic phase code coefficient c2In the n-th+m+1 frequency modulation cycle Ts
The first phase assigned in class, ψn-1For three phase code coefficient c1The first phase assigned in (n-1)th frequency modulation cycle T class, φn-1For
Quadratic phase code coefficient c2The first phase assigned in (n-1)th frequency modulation cycle T class；N, m value are positive integer；
Fig. 3 a are the designed signal echo Doppler frequency spectrum analogous diagram of the present invention, and Frequency is frequency, Amplitude
For amplitude；
Fig. 3 b are linear frequency modulation continuous wave echo Doppler frequency spectrum analogous diagram；
Fig. 4 a are the designed signal echo Doppler frequency spectrum analogous diagram of the present invention；
Fig. 4 b are quadratic phase encoded signal echo Doppler frequency spectrum analogous diagram between linear frequency modulation arteries and veins in arteries and veins.
Embodiment
Embodiment one：Illustrate present embodiment with reference to Fig. 1, Fig. 2, one kind of present embodiment is based on cognitive radar
Anti- multi-hop noise jamming waveform design method detailed process is：
Step one：Radar outwards launches linear frequency modulation continuous wave signal, and receiver receives echo-signal, and radar is to echo
Signal carries out range Doppler two-dimensional process, obtains width l and multi-hop of the multi-hop clutter on doppler spectral in echo-signal
Clutter present position f on doppler spectralloction；
Step 2：Phase-modulation is carried out on the basis of the linear frequency modulation continuous wave of step one, three phases are adjusted between obtaining arteries and veins
Linear frequency modulation continuous wave signal waveform U after systemT(t)；Three phases are tried to achieve according to the width of the multi-hop clutter obtained in step one
Position code coefficient, realizes the compression of multi-hop clutter；
Step 3：Linear frequency modulation continuous wave signal waveform U the arteries and veins obtained step 2 after three phase-modulationsT(t)
Quadratic phase coding is carried out, makes multi-hop clutter that there is controllable move on doppler spectral.
Embodiment two：Present embodiment from unlike embodiment one：In the step one radar to
Outer emission lines CW with frequency modulation signal, receiver receives echo-signal, and radar carries out range Doppler two to echo-signal
Dimension processing, obtains the width l and multi-hop clutter present position f of multi-hop clutter in echo-signalloction；Detailed process is：
Radar outwards launches linear frequency modulation continuous wave signal, and receiver carries out range Doppler two-dimensional process to echo, obtained
Obtain target range velocity information；Multi-hop clutter enters receiver by ionosphere multiple reflections, because multi-hop clutter is between arteries and veins
Nonlinear change, so multi-hop clutter can be produced on doppler spectral and moved and broadening when carrying out doppler processing between arteries and veins.
Note ionosphere slow phase footpath phase modulation function is M (t), and ionosphere slow phase footpath phase modulation function is using sinusoidal mould
Type, i.e.,The sum that Taylor expansion obtains unlimited item power series, wherein constant term pair are carried out to it
As a result without influence, first order can cause multi-hop clutter to be moved on doppler spectral, and quadratic term and high-order term can cause multi-hop clutter
Extend, but degree of expansion is mainly determined by quadratic term, so cubic term and more high-order term are negligible, without considering.
Radar outwards launches linear frequency modulation continuous wave signal, and signal waveform is：
In formula：uT(t) it is linear frequency modulation continuous wave signal waveform, n is uT(t) frequency modulation on pulse sequence number in the coherent accumulation cycle,
1≤n≤N；N is uT(t) coherent accumulation periodicity, value is positive integer；K is uT(t) chirp rate；T is uT(t) the frequency modulation cycle；
f0For uT(t) carrier frequency；T is time, ejπValue is -1；
If UR(t) outwards launch linear frequency modulation continuous wave signal for the radar that receiver is received and be irradiated to the echo after target
Signal, then
In formula：τ is delayed for echo, and M (t) is ionosphere slow phase footpath phase modulation function, and M (t) adjusts for the slow change in cycle
System, M (t) uses sinusoidal model, is expressed asWherein α is M (t) coefficient of frequency, and β is M (t)
Range coefficient,For M (t) first phase, M (t) is obtained by Taylor expansion：
diFor the coefficient of ith, i values are positive integer, and ith is (2 π α n Τ
)i；
It is more than cubic term and cubic term relatively small due to 2 π α Ν Τ ＜ 1, herein without a moment's thought.Therefore it is main to consider i
Span is 0~2 situation, and 2 π α n Τ are constant term during i=0, are not considered；
During i=1 (2 π α n Τ)1For first order, multi-hop clutter is caused to be moved on doppler spectral, i.e.,fshift1The amount of moving produced for first order；α is M (t) coefficient of frequency；d1For the 1st time
The coefficient of item；
During i=2 (2 π α n Τ)2For quadratic term, cause multi-hop clutter broadening；Draw multi-hop clutter broadening width by ionosphere
Slow phase footpath phase modulation function M (t) quadratic term decision, i.e.,Multi-hop is miscellaneous
Ripple broadening width l=d24πα2NT, multi-hop clutter broadening width l by radar emission linear frequency modulation continuous wave signal uT(t) and its
Echo UR(t) measure, multi-hop clutter broadening width obtains coefficient after measuringd2For the coefficient of the 2nd item；
Multi-hop clutter present position floctionBy the linear frequency modulation continuous wave signal u of radar emissionTAnd its echo U (t)R(t)
Measure.
Other steps and parameter are identical with embodiment one.
Embodiment three：Present embodiment from unlike embodiment one or two：In the step 2
Phase-modulation is carried out on the basis of the linear frequency modulation continuous wave of step one, the linear frequency modulation obtained between arteries and veins after three phase-modulations is continuous
Ripple signal waveform UT(t)；Three phase code coefficients are tried to achieve according to the width of the multi-hop clutter obtained in step one, multi-hop is realized
The compression of clutter；Detailed process is：
Know multi-hop clutter broadening mainly by secondary after the phase modulation function Taylor expansion of ionosphere slow phase footpath
Item is produced；In order to which quadratic term compensation is fallen, three phase codes between arteries and veins, warp are carried out on the basis of original linear frequency modulation continuous wave
After pulse pressure processing, linear change amount and quadratic nonlinearity variable quantity can be produced between arteries and veins, linear term can cause multi-hop clutter how general
Strangle and moved in spectrum, do not consider that it influences temporarily herein, quadratic term then can be to ionosphere slow phase footpath phase modulation function Taylor
Quadratic term after expansion is compensated；Three phase code systems then can obtain by the multi-hop clutter width measured in step one
Number, so that the waveform of design realizes the function of multi-hop clutter compression；
By quadratic term (2 π α n Τ)2Compensation is fallen：
In original linear frequency modulation continuous wave uT(t) phase-modulation is carried out on the basis of, its waveform is as follows：
In formula, UT(t) it is the linear frequency modulation continuous wave signal waveform after three phase-modulations between arteries and veins；c1Compiled for three phases
Code coefficient；
If known echo is m apart from folding times, after distance processing, by three phase code coefficient c1The phase of generation
Position deviation is shown below：
In formula, ψn+mFor three phase code coefficient c1The first phase assigned in the n-th+m frequency modulation cycle T classes, ψnFor three times
Phase code coefficient c1The first phase assigned in n-th of frequency modulation cycle T class；
When m is known constant, formula (5) Section 3 c1m3For constant term, doppler processing result of adjusting the distance is without influence；The
Binomial 3c1m2N is first order, and what three phase code coefficients were produced moves, and the amount of moving is fshift2=3c1m2/2T；
Section 1 3c1mn2It is secondary after the phase modulation function Taylor expansion of slow phase footpath in order to be compensated with it for quadratic term
, according to the coefficient d obtained in step one2, try to achieve c1=lT/3mN, then it is linear after three phase-modulations between radar emission arteries and veins
CW with frequency modulation signal waveform UT(t) compression of multi-hop clutter is realized.
Other steps and parameter are identical with embodiment one or two.
Embodiment four：Unlike one of present embodiment and embodiment one to three：The step 3
In linear frequency modulation continuous wave signal waveform U the arteries and veins that is obtained step 2 after three phase-modulationsT(t) quadratic phase volume is carried out
Code, makes multi-hop clutter have controllable move on doppler spectral；Detailed process is：
Because the first order produced after the phase modulation function Taylor expansion of ionosphere slow phase footpath causes multi-hop clutter how general
Strangling in spectrum has the amount of a moving fshift1, meanwhile, in step 2, in order to compensate after the phase modulation function Taylor expansion of slow phase footpath
Three phase codes are carried out between quadratic term, arteries and veins, after processing, the amount of a moving f can be produced on doppler spectralshift2.In order to be able to
Enough control multi-hop clutter present position on doppler spectral, between arteries and veins on the basis of three phase codes, is carried out secondary again between arteries and veins
Phase code, can make multi-hop clutter have one on doppler spectral and controllable move after processing.So it can then realize simultaneously many
The compression for jumping clutter is moved with controllable.
C in step 21Value is it has been determined that when m is known constant, then step 2 obtains what three phase code coefficients were produced
The amount of moving fshift2=3c1m2/ 2T is also constant；M is echo apart from folding times；
Position f of the multi-hop clutter on doppler spectral is obtained according to step oneloctionThree phase volumes are obtained with step 2
The amount of the moving f that code coefficient is producedshift2=3c1m2/ 2T, multi-hop clutter final position on doppler spectral is expressed as floction'=
lm/2N+floction；In order to three times controlling multi-hop clutter present position on doppler spectral, the arteries and veins obtained step 2
Linear frequency modulation continuous wave signal waveform U after phase-modulationT(t) quadratic phase coding is carried out, its waveform is as follows：
In formula, UT(t) ' for the signal U after three phase codes being obtained to step 2T(t) quadratic phase volume is carried out between arteries and veins
Waveform after code；c2For quadratic phase code coefficient；
If known echo is apart from folding times m, after distance processing, by quadratic phase code coefficient c2The phase of generation
Deviation is shown below：
In formula, φn+mFor quadratic phase code coefficient c2The first phase assigned in the n-th+m frequency modulation cycle T classes, φnFor two
Secondary phase code coefficient c2The first phase assigned in n-th of frequency modulation cycle T class；
When m is known constant, formula (7) Section 2 c2m2For constant term, doppler processing result of adjusting the distance is without influence；The
One 2c2Mn is first order, and the amount of moving f is produced on doppler spectralshift-change=c2M/T, the amount of moving fshift-changeSize
Pass through quadratic phase code coefficient c2It is adjusted, multi-hop clutter is moved no target location f on doppler spectralend；
fend=flocation′+fshift-change (8)
F is obtained according to formula (8)shift-change, and then try to achieve c2, make multi-hop clutter that there is controllable remove on doppler spectral
Move.
It can be seen that in multi-hop noise jamming scene, set by the waveform of the present invention by the specific implementation of the present invention
Meter method, can meet simultaneously multi-hop clutter compression with carried out on doppler spectral it is controllable move, realize radar to target just
Really detection.
Other steps and parameter are identical with one of embodiment one to three.
Beneficial effects of the present invention are verified using following examples：
Embodiment one：
The present embodiment one kind is specifically according to following steps based on the anti-multi-hop noise jamming waveform design method of cognitive radar
Prepare：
By setting suitable waveform parameter and ionosphere slow phase footpath phase modulation function M (t), in emulation tool MATLAB
Upper carry out simulating, verifying.
Waveform parameter is designed：
As shown in Fig. 3 a, 3b, linear frequency modulation continuous wave echo multi-hop clutter on Doppler frequency spectrum floods echo signal, makes
It can not be arrived into target by effective detection, the designed signal multi-hop clutter on Doppler frequency spectrum of the present invention is compressed and is shifted to
Between unconcerned Doppler region.
As shown in Fig. 4 a, 4b, quadratic phase encoded signal multi-hop clutter on Doppler frequency spectrum between linear frequency modulation arteries and veins in arteries and veins
Moved out, slower-velocity target can be arrived by effective detection, but high-speed target detection is affected, and the designed signal of the present invention is how general
Strangle multi-hop clutter on frequency spectrum to be compressed and moved out, the detection beneficial to radar to target.
The present invention can also have other various embodiments, in the case of without departing substantially from spirit of the invention and its essence, this area
Technical staff works as can make various corresponding changes and deformation according to the present invention, but these corresponding changes and deformation should all belong to
The protection domain of appended claims of the invention.
Claims (4)
1. one kind is based on the anti-multi-hop noise jamming waveform design method of cognitive radar, it is characterised in that：Methods described detailed process
For：
Step one：Radar outwards launches linear frequency modulation continuous wave signal, and receiver receives echo-signal, and radar is to echo-signal
Range Doppler two-dimensional process is carried out, width l and multi-hop clutter of the multi-hop clutter on doppler spectral in echo-signal is obtained
The present position f on doppler spectralloction；
Step 2：Phase-modulation is carried out on the basis of the linear frequency modulation continuous wave of step one, is obtained between arteries and veins after three phase-modulations
Linear frequency modulation continuous wave signal waveform UT(t)；Three phase volumes are tried to achieve according to the width of the multi-hop clutter obtained in step one
Code coefficient, realizes the compression of multi-hop clutter；
Step 3：Linear frequency modulation continuous wave signal waveform U the arteries and veins obtained step 2 after three phase-modulationsT(t) two are carried out
Secondary phase code, makes multi-hop clutter have controllable move on doppler spectral.
2. it is a kind of based on the anti-multi-hop noise jamming waveform design method of cognitive radar according to claim 1, it is characterised in that：
Radar outwards launches linear frequency modulation continuous wave signal in the step one, and receiver receives echo-signal, and radar is believed echo
Number carry out range Doppler two-dimensional process, obtain width l and the multi-hop clutter present position of multi-hop clutter in echo-signal
floction；Detailed process is：
Radar outwards launches linear frequency modulation continuous wave signal, and signal waveform is：
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In formula：uT(t) it is linear frequency modulation continuous wave signal waveform, n is uT(t) frequency modulation on pulse sequence number, 1≤n in the coherent accumulation cycle
≤N；N is uT(t) coherent accumulation periodicity, value is positive integer；K is uT(t) chirp rate；T is uT(t) the frequency modulation cycle；f0For
uT(t) carrier frequency；T is the time；
If UR(t) outwards launch linear frequency modulation continuous wave signal for the radar that receiver is received and be irradiated to the echo-signal after target,
Then
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In formula：τ is delayed for echo, and M (t) is ionosphere slow phase footpath phase modulation function；
diFor the coefficient of ith, i values are positive integer, and ith is (2 π α n Τ)i；
Due to 2 π α Ν Τ ＜ 1, then i >=3 do not consider, it is considered to which i spans are 0~2 situation, and 2 π α n Τ are constant during i=0
, do not consider；
During i=1 (2 π α n Τ)1For first order, multi-hop clutter is caused to be moved on doppler spectral, i.e.,
fshift1The amount of moving produced for first order；α is M (t) coefficient of frequency；d1For the coefficient of the 1st item；
During i=2 (2 π α n Τ)2For quadratic term, cause multi-hop clutter broadening；Draw multi-hop clutter broadening width by ionosphere slow phase
Footpath phase modulation function M (t) quadratic term decision, i.e.,Multi-hop clutter exhibition
Wide degree l=d24πα2NT, multi-hop clutter broadening width l by radar emission linear frequency modulation continuous wave signal uTAnd its echo (t)
UR(t) measure, multi-hop clutter broadening width obtains coefficient after measuringd2For the coefficient of the 2nd item；
Multi-hop clutter present position floctionBy the linear frequency modulation continuous wave signal u of radar emissionTAnd its echo U (t)R(t) survey
.
3. it is a kind of based on the anti-multi-hop noise jamming waveform design method of cognitive radar according to claim 2, it is characterised in that：
Phase-modulation is carried out in the step 2 on the basis of the linear frequency modulation continuous wave of step one, is obtained between arteries and veins after three phase-modulations
Linear frequency modulation continuous wave signal waveform UT(t)；Three phase volumes are tried to achieve according to the width of the multi-hop clutter obtained in step one
Code coefficient, realizes the compression of multi-hop clutter；Detailed process is：
By quadratic term (2 π α n Τ)2Compensation is fallen：
In original linear frequency modulation continuous wave uT(t) phase-modulation is carried out on the basis of, its waveform is as follows：
<mrow>
<msub>
<mi>U</mi>
<mi>T</mi>
</msub>
<mrow>
<mo>(</mo>
<mi>t</mi>
<mo>)</mo>
</mrow>
<mo>=</mo>
<munderover>
<mi>&Sigma;</mi>
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</mrow>
<mi>N</mi>
</munderover>
<msup>
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<mrow>
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<mi>k</mi>
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<mi>n</mi>
<mi>T</mi>
</mrow>
<mo>)</mo>
</mrow>
<mn>2</mn>
</msup>
</mrow>
</msup>
<msup>
<mi>e</mi>
<mrow>
<mi>j</mi>
<mn>2</mn>
<msub>
<mi>&pi;f</mi>
<mn>0</mn>
</msub>
<mi>t</mi>
</mrow>
</msup>
<msup>
<mi>e</mi>
<mrow>
<mo>-</mo>
<msub>
<mi>j&pi;c</mi>
<mn>1</mn>
</msub>
<msup>
<mi>n</mi>
<mn>3</mn>
</msup>
</mrow>
</msup>
<mi>r</mi>
<mi>e</mi>
<mi>c</mi>
<mi>t</mi>
<mrow>
<mo>(</mo>
<mfrac>
<mrow>
<mi>t</mi>
<mo>-</mo>
<mfrac>
<mi>T</mi>
<mn>2</mn>
</mfrac>
<mo>-</mo>
<mi>n</mi>
<mi>T</mi>
</mrow>
<mi>T</mi>
</mfrac>
<mo>)</mo>
</mrow>
<mo>-</mo>
<mo>-</mo>
<mo>-</mo>
<mrow>
<mo>(</mo>
<mn>4</mn>
<mo>)</mo>
</mrow>
</mrow>
In formula, UT(t) it is the linear frequency modulation continuous wave signal waveform after three phase-modulations between arteries and veins；c1For three phase code systems
Number；
If known echo is m apart from folding times, after distance processing, by three phase code coefficient c1The phase of generation is inclined
Difference is shown below：
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<mn>3</mn>
<msub>
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<mn>1</mn>
</msub>
<msup>
<mi>m</mi>
<mn>2</mn>
</msup>
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<mo>+</mo>
<msub>
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<mn>1</mn>
</msub>
<msup>
<mi>m</mi>
<mn>3</mn>
</msup>
</mrow>
</mtd>
</mtr>
</mtable>
<mo>-</mo>
<mo>-</mo>
<mo>-</mo>
<mrow>
<mo>(</mo>
<mn>5</mn>
<mo>)</mo>
</mrow>
</mrow>
In formula, ψn+mFor three phase code coefficient c1The first phase assigned in the n-th+m frequency modulation cycle T classes, ψnFor for three phases
Position code coefficient c1The first phase assigned in n-th of frequency modulation cycle T class；
When m is known constant, formula (5) Section 3 c1m3For constant term, doppler processing result of adjusting the distance is without influence；Section 2
3c1m2N is first order, and what three phase code coefficients were produced moves, and the amount of moving is fshift2=3c1m2/2T；
Section 1 3c1mn2For quadratic term, according to the coefficient d obtained in step one2, try to achieve c1=lT/3mN, then between radar emission arteries and veins
Linear frequency modulation continuous wave signal waveform U after three phase-modulationsT(t) compression of multi-hop clutter is realized.
4. it is a kind of based on the anti-multi-hop noise jamming waveform design method of cognitive radar according to claim 3, it is characterised in that：
Linear frequency modulation continuous wave signal waveform U the arteries and veins obtained in the step 3 step 2 after three phase-modulationsT(t) carry out
Quadratic phase is encoded, and multi-hop clutter is had controllable move on doppler spectral；Detailed process is：
C in step 21Value is it has been determined that when m is known constant, then step 2 obtains moving for three phase code coefficients generations
Measure fshift2=3c1m2/ 2T is also constant；M is echo apart from folding times；
Position f of the multi-hop clutter on doppler spectral is obtained according to step oneloctionThree phase code coefficients are obtained with step 2
The amount of the moving f producedshift2=3c1m2/ 2T, multi-hop clutter final position on doppler spectral is expressed as floction'=lm/2N+
floction；Linear frequency modulation continuous wave signal waveform U the arteries and veins obtained step 2 after three phase-modulationsT(t) secondary phase is carried out
Position coding, its waveform is as follows：
<mrow>
<msub>
<mi>U</mi>
<mi>T</mi>
</msub>
<msup>
<mrow>
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<mi>N</mi>
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<mi>k</mi>
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<mn>2</mn>
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<msup>
<mi>e</mi>
<mrow>
<mi>j</mi>
<mn>2</mn>
<msub>
<mi>&pi;f</mi>
<mn>0</mn>
</msub>
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</mrow>
</msup>
<msup>
<mi>e</mi>
<mrow>
<mo>-</mo>
<mi>j</mi>
<mi>&pi;</mi>
<mrow>
<mo>(</mo>
<msub>
<mi>c</mi>
<mn>1</mn>
</msub>
<msup>
<mi>n</mi>
<mn>3</mn>
</msup>
<mo>+</mo>
<msub>
<mi>c</mi>
<mn>2</mn>
</msub>
<msup>
<mi>n</mi>
<mn>2</mn>
</msup>
<mo>)</mo>
</mrow>
</mrow>
</msup>
<mi>r</mi>
<mi>e</mi>
<mi>c</mi>
<mi>t</mi>
<mrow>
<mo>(</mo>
<mfrac>
<mrow>
<mi>t</mi>
<mo>-</mo>
<mfrac>
<mi>T</mi>
<mn>2</mn>
</mfrac>
<mo>-</mo>
<mi>n</mi>
<mi>T</mi>
</mrow>
<mi>T</mi>
</mfrac>
<mo>)</mo>
</mrow>
<mo>-</mo>
<mo>-</mo>
<mo>-</mo>
<mrow>
<mo>(</mo>
<mn>6</mn>
<mo>)</mo>
</mrow>
</mrow>
In formula, UT(t) ' for the signal U after three phase codes being obtained to step 2T(t) carried out between arteries and veins after quadratic phase coding
Waveform；c2For quadratic phase code coefficient；
If known echo is apart from folding times m, after distance processing, by quadratic phase code coefficient c2The phase deviation of generation
It is shown below：
<mrow>
<mtable>
<mtr>
<mtd>
<mrow>
<msub>
<mi>&phi;</mi>
<mrow>
<mi>n</mi>
<mo>+</mo>
<mi>m</mi>
</mrow>
</msub>
<mo>-</mo>
<msub>
<mi>&phi;</mi>
<mi>n</mi>
</msub>
<mo>=</mo>
<msub>
<mi>c</mi>
<mn>2</mn>
</msub>
<msup>
<mrow>
<mo>(</mo>
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<mi>m</mi>
<mo>)</mo>
</mrow>
<mn>2</mn>
</msup>
<mo>-</mo>
<msub>
<mi>c</mi>
<mn>2</mn>
</msub>
<msup>
<mi>n</mi>
<mn>2</mn>
</msup>
</mrow>
</mtd>
</mtr>
<mtr>
<mtd>
<mrow>
<mo>=</mo>
<mn>2</mn>
<msub>
<mi>c</mi>
<mn>2</mn>
</msub>
<mi>m</mi>
<mi>n</mi>
<mo>+</mo>
<msub>
<mi>c</mi>
<mn>2</mn>
</msub>
<msup>
<mi>m</mi>
<mn>2</mn>
</msup>
</mrow>
</mtd>
</mtr>
</mtable>
<mo>-</mo>
<mo>-</mo>
<mo>-</mo>
<mrow>
<mo>(</mo>
<mn>7</mn>
<mo>)</mo>
</mrow>
</mrow>
In formula, φn+mFor quadratic phase code coefficient c2The first phase assigned in the n-th+m frequency modulation cycle T classes, φnFor secondary phase
Position code coefficient c2The first phase assigned in n-th of frequency modulation cycle T class；
When m is known constant, formula (7) Section 2 c2m2For constant term, doppler processing result of adjusting the distance is without influence；Section 1
2c2Mn is first order, and the amount of moving f is produced on doppler spectralshift-change=c2M/T, the amount of moving fshift-changeSize pass through
Quadratic phase code coefficient c2It is adjusted, multi-hop clutter is moved no target location f on doppler spectralend；
fend=flocation′+fshift-change (8)
F is obtained according to formula (8)shift-change, and then try to achieve c2, make multi-hop clutter that there is controllable move on doppler spectral.
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