CN107148729B - The control device and direct power converter of charge-discharge circuit, the control method of charge-discharge circuit, charge-discharge circuit - Google Patents
The control device and direct power converter of charge-discharge circuit, the control method of charge-discharge circuit, charge-discharge circuit Download PDFInfo
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- CN107148729B CN107148729B CN201580065019.7A CN201580065019A CN107148729B CN 107148729 B CN107148729 B CN 107148729B CN 201580065019 A CN201580065019 A CN 201580065019A CN 107148729 B CN107148729 B CN 107148729B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
- H02M1/126—Arrangements for reducing harmonics from ac input or output using passive filters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
- H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4266—Arrangements for improving power factor of AC input using passive elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
When even with inhibiting electric current to inhibit the resonance of LC filters, the update of the sampling, command value that will not make the control system of control inverter deteriorates.In module (10a), current division ratio generating unit (11) is input with the amplitude (Vm) of single-phase AC voltage (Vin), the amplitude (Im) of input current, the command value (Idc*) in relation to DC current (Idc), the command value (Vc*) in relation to both end voltage (Vc) and power supply angular speed (ω).Current division ratio generating unit (11) output current command value (Ib*).Resonance inhibits control unit (15) with reactor voltage (VL) for input, output calibration value (kVL).Subtracter (17) subtracts corrected value (kVL) from current instruction value (Ib*), and is supplied to chop control portion (16).Chop control portion (16) is according to the current instruction value (Ib* kVL) after being corrected, output boosting duty ratio (dl).Boosting duty ratio (dl) is compared with carrier wave (C2) in comparator (14), its result is exported as control signal (SSI).
Description
Technical field
The present invention relates to the charge-discharge circuit for including in direct power converter, the charge-discharge circuit control method,
The control device of the charge-discharge circuit and the direct power converter.
Background technology
Patent document 1,3,4 discloses direct power converter.Direct-type electric power disclosed in these patent documents
The capacitor of the voltage to be boosted by the boost voltage equipped with booster circuit and support in converter.In the straight of supply inverter
In galvanic electricity power, to from the capacitor electric power and the electric power that is obtained from diode rectifier carry out proper treatment, thus improve
Input the DC voltage of inverter.
Patent document 2 also discloses that direct power converter, but is not provided with above-mentioned booster circuit and capacitor.Separately
On the one hand, for inhibiting the LC filters of the carrier current of inverter to be set to the input side of inverter.
Direct power converter disclosed in patent document 1 not only has above-mentioned booster circuit and capacitor, but also
Also there is above-mentioned LC filters.Also, electric current flows to the LC filters from the capacitor in order to prevent, is equipped with therebetween
Diode.
All it is (or to be filtered in LC according to the voltage generated in the reactor of LC filters in patent document 1,2,5
The voltage generated in the capacitor of device) electric current (hereinafter, referred to as " inhibit electric current ") for inhibiting LC filters to resonate is found out, and
The electric current is superimposed upon in the electric current (hereinafter, referred to as " inverter current ") for flowing through inverter.
Existing technical literature
Patent document
Patent document 1：Japanese Unexamined Patent Publication 2014-96976 bulletins
Patent document 2：No. 4067021 bulletins of Japanese Patent No.
Patent document 3：Japanese Unexamined Patent Publication 2011-193678 bulletins
Patent document 4：Japanese Unexamined Patent Publication 2014-82926 bulletins
Patent document 5：No. 5257533 bulletins of Japanese Patent No.
Invention content
Problems to be solved by the invention
LC filters are designed to, are made in the electric current for flowing through inverter, the decaying of the ingredient of the carrier frequency of inverter.Cause
The resonant frequency of LC filters, is preferably set as the part of carrier frequency by this.
In this case, when that electric current will be inhibited to be superimposed upon in inverter current, the control of control inverter cannot be ignored
The sampling of system processed, the newer delay of command value.
In addition, in patent document 1, make from the DC voltage that DC link inputs inverter, from diode rectifier
The value of the ratio of the voltage of application changes, thus the DC voltage changes, and thus leads to the reduction of its average value.
Therefore, the object of the present invention is to provide following technologies, inhibit LC filters even with electric current is inhibited
When resonance, the update of the sampling, command value that will not make the control system of control inverter deteriorates.
The means used to solve the problem
The control method of the charge-discharge circuit of the present invention is the method for the charge-discharge circuit for controlling direct power converter.
The direct power converter has：1st power cord (LH)；2nd power cord (LL) is applied in lower than the 1st power cord
Current potential；Rectification circuit (203), have be applied in single-phase AC voltage (Vin) input side and with the 1st power cord
And the outlet side of the 2nd power cord connection；Charge-discharge circuit (4) is set to institute in the outlet side of the rectification circuit
It states between the 1st power cord and the 2nd power cord；And inverter (5), it is entered the 1st power cord and the 2nd electricity
Voltage, that is, DC voltage (Vdc) between the line of source, the rectification circuit have：Diode rectifier (2) carries out single-phase full wave
Rectification；1st capacitor (C3), directly or via the diode rectifier be coupled indirectly to the 1st power cord and
Between 2nd power cord；And the 1st reactor (L3), directly or via the diode rectifier in series with institute
The 1st power cord or the 2nd power cord connection are stated, and than the 1st capacitor further from the inverter.
The charge-discharge circuit has：Buffer circuit (4a) comprising be set to the 1st power cord and the 2nd power supply
The 2nd capacitor (C4) between line makes the 2nd capacitor discharge according to controllable time ratio (dc)；And booster circuit
(4b), the rectified voltage to coming from the diode rectifier (2) are boosted and are charged to the 2nd capacitor.
The control method more reduces when the voltage (VL) of the 1st reactor is higher is input to the booster circuit
DC current (IL2).
It is set to the feelings between the diode rectifier (2) and the 1st capacitor (C3) in the 1st reactor (L3)
Under condition, the polarity of the voltage (VL) of the 1st reactor is with the opposite direction for flowing through the direction of the electric current of the 1st reactor
Just.The 1st reactor (L3) than the diode rectifier (2) further from the inverter (5) in the case of, described
The polarity of the voltage (VL) of 1 reactor with from the high potential of the single-phase AC voltage (Vin) towards the direction of low potential be just.
For example, the control method will be subtracted from the 1st command value (Ib*) with the voltage (VL) of the 1st reactor at than
2nd command value (Ib*-kVL) obtained from the corrected value (kVL) of example is used as desired value, controls the DC current
(IL2), the 1st command value (Ib*) by be input to the alternating current (Iin) of the diode rectifier (2) amplitude (Im) and
The voltage (Vr) of the diode rectifier output determines.
In this case, the booster circuit (4b) has the 2nd reactor for flowing through the DC current (IL2)
(L4), it and is made whether to export the copped wave processing of the DC current to the 2nd capacitor.The control method is according to by the time
Ratio (dl) is carried out with defined carrier wave (C2) result of the comparison, which is to use the 2nd command value (Ib*-
KVL), the inductance of the voltage (Vc), the single-phase AC voltage (Vin), the 2nd reactor of the 2nd capacitor (C4)
It is worth (Lm) decision.
For example, two times of cosine value of the buffer circuit (4a) in the phase (ω t) of the single-phase AC voltage (Vin)
(cos (2 ω t)) be it is negative during in charge to the 1st capacitor (C3), during the cosine value is just in make it is described
1st capacitor discharge.
Alternatively, at least the time ratio (dc) be more than 0 during a part during in, carry out the buffer circuit
The charging of (4a) to the 1st capacitor (C3).
The control device of the charge-discharge circuit of the present invention is to control the charge-discharge circuit when carrying out the copped wave processing
(4) device (10), the control device have：Subtracter (17) subtracts the correction from the 1st command value (Ib*)
Value (kVL) and obtain the 2nd command value (Ib*-kVL)；Chop control portion (16), using the 2nd command value and
The voltage (Vc) of 2nd capacitor (C4), the single-phase AC voltage (Vin), the 2nd reactor inductance value (Lm) certainly
The fixed time ratio (dl)；And comparator (14), the time ratio and the carrier wave (C2) are compared, exported
Control the control signal (SSI) of the copped wave.
The charge-discharge circuit of the present invention is the charge and discharge electricity controlled using the control method of above-mentioned charge-discharge circuit
Road.The charge-discharge circuit (4) also have electric current blocking portion (4c), the electric current blocking portion (4c) be set to the 1st power cord or
2nd power cord prevents electric current from flowing to the 1st capacitor (C3) from the buffer circuit (4a).
The direct power converter of the present invention has the charge-discharge circuit (4), the 1st power cord (LH), described
It is 2nd power cord (LL), the diode rectifier (2), the 1st capacitor (C3), the 1st reactor (L3), described inverse
Become device (5).
Invention effect
Charge-discharge circuit according to the present invention, the control method of charge-discharge circuit, the control device of charge-discharge circuit and straight
Direct type power converter will not make the control of control inverter when even with inhibiting electric current to inhibit the resonance of LC filters
The sampling of system processed, the update of command value deteriorate.
The purpose of the present invention, feature, aspect and advantage will be apparent from according to following detailed description and attached drawing.
Description of the drawings
Fig. 1 is the structure chart of an example for the conceptual configuration for showing direct power converter.
Fig. 2 is to show to control the wire figure of an example of the conceptual configuration of the control device of the direct power converter.
Fig. 3 is the circuit diagram for the equivalent circuit for showing direct power converter shown in FIG. 1.
Fig. 4 is the wire figure that the equivalent circuit of Fig. 3 is interpreted as equivalent circuit composition control system and is shown.
Fig. 5 is the wire figure of the deformation for the wire figure for showing Fig. 4.
Fig. 6 is the wire figure of the deformation for the wire figure for showing Fig. 5.
Fig. 7 is the wire figure of the deformation for the wire figure for showing Fig. 6.
Fig. 8 be show input current, reactor voltage, electric current waveform curve graph.
Fig. 9 be show input current, reactor voltage, electric current waveform curve graph.
Figure 10 be show input current, reactor voltage, electric current waveform curve graph.
Figure 11 be show input current, reactor voltage, electric current waveform curve graph.
Figure 12 is the circuit diagram for the deformation for showing the position relationship between reactor and diode rectifier.
Figure 13 is the circuit diagram for the deformation for showing the position relationship between capacitor and reactor and diode rectifier.
Figure 14 is the circuit diagram for the deformation for showing diode rectifier.
Figure 15 is the block diagram that example resonance inhibits the structure of control unit and the periphery of reactor.
Specific implementation mode
A. the structure of Direct-type power-converting device：
Before illustrating the characteristic technology of embodiment, to the Direct-type power-converting device using the technology
Structure illustrates.In addition, the structure elemental motion of itself is known in patent document 1, thus it is omitted herein in detail
Feelings.
As shown in Figure 1, the Direct-type power-converting device has diode rectifier 2, LC filters 3, charge-discharge circuit 4
And inverter 5.Direct current supply line LH, LL play a role between inverter 5 and charge-discharge circuit 4 as DC link.It is right
Direct current supply line LH applies the current potential higher than direct current supply line LL.
Diode rectifier 2 has the input side and outlet side for applying single-phase AC voltage Vin from single phase alternating current power supply 1.
Diode rectifier 2 to single-phase AC voltage Vin carry out single-phase full-wave rectifier circuit and be transformed to voltage Vr (=| Vin
|), export the voltage from outlet side.
In addition, alternating current Iin (hereinafter, referred to as " input current Iin ") flows into diode rectification from single phase alternating current power supply 1
The input side of device 2.
Diode rectifier 2 has diode D21~D24.Diode D21~D24 constitutes bridge circuit.
LC filters 3 have reactor L3 and capacitor C3.Capacitor C3 is set between direct current supply line LH, LL.Reactance
Device L3 specific capacitance device C3 (in the example of fig. 1, are further from inverter 5, and with direct current supply line LH or direct current supply line LL
In the outlet side and direct current supply line LH of diode rectifier 2) it is connected in series with.
Capacitor C3 is, for example, thin film diode, has the electrostatic capacitance value smaller than the electrostatic capacitance value of electrolytic capacitor.
Such capacitor C3 hardly carries out the voltage Vr that diode rectifier 2 exports smooth.Therefore, although the two of capacitor C3
Terminal voltage V3 is DC voltage, is but pulsed with the period identical with the period of the pulsation of voltage Vr.
The assembly of diode rectifier 2 and LC filters 3 can be understood as following rectification circuit 203, the rectification circuit
203 have the outlet side for being applied in the input side of single-phase AC voltage Vin and being connected between direct current supply line LH, LL.Scheming
In 1, reactor L3 and being connected in series with for capacitor C3 are applied in voltage Vr, however according to the structure of rectification circuit 203, diode
The output of rectifier 2 is not required to be applied to capacitor C3 via reactor L3.Deformation about such rectification circuit will be
It is described later.
Charge-discharge circuit 4 is set to 5 side of inverter relative to capacitor C3, has buffer circuit 4a and booster circuit 4b and electricity
Flow resistance stop 4c.Buffer circuit 4a includes sending and receiving electric power between capacitor C4, with direct current supply line LH, LL.
Buffer circuit 4a further includes that the transistor being connect with diode D42 inverse parallels (refers to that insulated gate polar form is bipolar herein
Transistor, hereinafter simply referred to as " IGBT ") Sc.Transistor Sc is between direct current supply line LH, LL, in the sides direct current supply line LH and electricity
Container C4 is connected in series with.Here, inverse parallel connection refers to forward reciprocal is connected in parallel.Specifically, transistor Sc's is suitable
To referring to direction from direct current supply line LL towards direct current supply line LH, diode D42's refers to forward from direct current supply line LH
Towards the direction of direct current supply line LL.Can transistor Sc and diode D42 being integrally interpreted as a switch element, (the 1st opens
It closes).It may be said that capacitor C4 is set to via the 1st switch between direct current supply line LH, LL.
Booster circuit 4b makes the both end voltage V3 of capacitor C3 (refer to the whole of the output of rectification circuit 203 in the structure of fig. 1
Galvanic electricity pressure) it boosts and charges to capacitor C4.For example, booster circuit 4b includes diode D40, reactor L4, transistor
(referred to IGBT) SI.There is diode D40 cathode and anode, the cathode to be connected between the 1st switch and capacitor C4.Reactance
Device L4 is connected between direct current supply line LH and the anode of diode D40.Transistor SI is connected to direct current supply line LL and two poles
Between the anode of pipe D40.Diode D41 is connect with transistor SI inverse parallels, and the two can be interpreted as to the switch of an entirety
Element (the 2nd switch).This structure is known as so-called boost chopper.
Capacitor C4 is electrically charged by booster circuit 4b, supports the both end voltage Vc higher than both end voltage V3.Specifically, from
Direct current supply line LH, which is switched via the 2nd to direct current supply line LL, flows through electric current IL2, thus in reactor L4 energy accumulations, then
By disconnecting the 2nd switch, which is accumulated via diode D40 in capacitor C4.Electric current IL2 is from direct current supply line LH
Direct current supply line LL is flowed to, thus its polarity is nonreversible, so being direct current.
Since both end voltage Vc is higher than both end voltage V3, thus electric current does not flow to diode D42 substantially.Therefore, it the 1st opens
The conducting of pass/being not turned on the conducting for only relying upon transistor Sc/is not turned on.Therefore, not only transistor Sc is known as switching below
The 1st switch for being combined with transistor Sc and diode D42 is also known as switch Sc by Sc sometimes.
By the conducting of switch Sc, capacitor C4 discharges to DC link.The time ratio of switch Sc conductings is known as
Duty ratio of discharging dc.Electric discharge duty ratio dc can be controlled.
In addition, the current potential of direct current supply line LH is higher than direct current supply line LL, thus electric current does not flow to diode substantially
D41.Therefore, the conducting/being not turned on the conducting for only relying upon transistor SI/of the 2nd switch is not turned on.It therefore, below not only will be brilliant
Body pipe SI is known as switch SI, and the 2nd switch for being combined with transistor SI and diode D41 is also known as switch SI sometimes.
Whether electric current IL2 flows through capacitor C4 is determined by booster circuit 4b.Specifically, using switch SI according to the time
The i.e. boosting duty ratio dl of ratio carries out copped wave processing.Copped wave processing is the ratio according to boosting duty ratio dl and aftermentioned carrier wave C2
Compared with progress.
Electric current blocking portion 4c between capacitor C3, C4 be set to direct current supply line LH or direct current supply line LL, prevent from
Capacitor C4 flows to the electric current of capacitor C3.The both end voltage Vc of capacitor C4 is due to booster circuit 4b and more than capacitor C3's
Both end voltage V3.However, electric current blocking portion 4c prevents to flow to the electric current of capacitor C3 from capacitor C4.Therefore, it is possible to avoid two
Terminal voltage V3 is influenced by both end voltage Vc.
Electric current blocking portion 4c is for example realized by diode D43.In the example of fig. 1, diode D43 is set to direct current supply line
LH refers to forward the direction from diode rectifier 2 towards inverter 5.
Inverter 5 will generate straight between direct current supply line LH, the LL for more leaning on 5 side of inverter than charge-discharge circuit 4
Galvanic electricity pressure Vdc is transformed to alternating voltage, and the alternating voltage is exported to output end Pu, Pv, Pw.
Inverter 5 includes 6 switch elements Sup, Svp, Swp, Sun, Svn, Swn.Switch element Sup, Svp, Swp difference
Be connected between output end Pu, Pv, Pw and direct current supply line LH, switch element Sun, Svn, Swn be connected to output end Pu,
Between Pv, Pw and direct current supply line LL.Inverter 5 constitutes so-called voltage source inverter, including 6 diodes.
6 diodes are all to configure its cathode towards the sides direct current supply line LH, by its anode towards direct current supply line LH
Side configures.1 diode and switch element Sup are connected in parallel between output end Pu and direct current supply line LH.Equally, in addition 5
A diode is connected in parallel with switch element Svp, Swp, Sun, Svn, Swn respectively.
For example, switch element Sup, Svp, Swp, Sun, Svn, Swn use IGBT.In this case, 6 diodes point
It is not connect with IGBT inverse parallels used by switch element Sup, Svp, Swp, Sun, Svn, Swn.
Irritability load 6 is, for example, whirler, is rotated according to the alternating voltage from inverter 5.
B. the control of the both end voltage VL based on reactor L3
Fig. 2 is an example for showing to control the conceptual configuration of the control device 10 of the above-mentioned direct power converter
Block diagram.Control device 10 has as module (block) 10a that plays a role of control device of charge-discharge circuit 4 and as inverse
Become the module 10b that the control device of device 5 plays a role.
There is module 10a current division ratio generating unit 11, resonance to inhibit control unit 15, adder 13, subtracter 17, copped wave
Control unit 16, comparator 12,14 and carrier wave generating unit 23,24.
Module 10b have output voltage command generation unit 31, operational part 32,33, comparator 34,35 and logic and/patrol
Collect product operational part 36.
Current division ratio generating unit 11 is with the amplitude Im, related of the amplitude Vm of single-phase AC voltage Vin, input current Iin
Input command value Idc*, the command value Vc* and power supply angular velocity omega in relation to both end voltage Vc of the DC current Idc of inverter 5
For input.For example, by test section well known to setting, detected amplitude Vm, Im and power supply angular velocity omega, and input current apportionment ratio
Generating unit 11.Command value Idc*, Vc* is inputted from external structure (not shown).
Current division ratio generating unit 11 exports rectification duty ratio drec, electric discharge duty ratio dc, zero dutycycle closest dz and electric current and refers to
Enable value Ib*.
Rectification duty ratio drec is that (LC filters 3 are typically with non-compared to power supply angular velocity omega from rectification circuit 203
The low-pass filter of normal high cutoff frequency, thus can also be known as " from diode rectifier 2 ") supplied electric power to DC link
Time ratio.Both end voltage Vc is higher than both end voltage V3, thus when switch Sc is connected, electric current is not flowed from rectification circuit 203
To DC link, therefore the sum of rectification duty ratio drec and electric discharge duty ratio dc are less than 1.Zero dutycycle closest dz is neither from rectified current
The time ratio that road 203 is not also supplied electric power from charge-discharge circuit 4 to DC link, zero dutycycle closest dz and rectification duty ratio drec
It is 1 with the sum of the duty ratio dc that discharges.
In the case where not considering the inhibition of resonance of LC filters 3, current instruction value Ib* is input booster circuit 4b
, the command value of the electric current IL2 for more specifically flowing to reactor L4.
About the method for determining rectification duty ratio drec, electric discharge duty ratio dc, zero dutycycle closest dz, current instruction value Ib*,
Through being described in detail in patent document 1,3,4, thus its details is omitted herein.
Resonance inhibition control unit 15 is defeated with the both end voltage VL (hereinafter, referred to as " reactor voltage VL ") of reactor L3
Enter.As shown in Figure 1, when reactor L3 is going here and there than diode rectifier 2 closer to the side of capacitor C3 and direct current supply line LH
In the case of connection setting, reactor voltage VL is using the end of the reactor L3 of the sides capacitor C3 as benchmark.Reactor voltage VL
It is detected using well known technology.Resonance inhibits control unit 15 to export bigger corrected value when reactor voltage VL is higher.
For example, by reactor voltage VL and specified value k (>0) product is exported as corrected value kVL.Corrected value kVL can
It is interpreted as proportional to reactor voltage VL.
Subtracter 17 subtracts corrected value kVL from current instruction value Ib*, and exports the current instruction value after being corrected
(Ib*-k·VL).This is equivalent to command value of the adopted value (- kVL) as the inhibition electric current for flowing through reactor L4.
In this way, when reactor voltage VL is higher, the current instruction value (Ib*-kVL) of the desired value as electric current IL2
It is lower, thus carry out the control for reducing electric current IL2.When reactor L3 than diode rectifier 2 closer to capacitor C3 one
In the case that side is arranged in series with direct current supply line LL, reactor voltage VL is with the end of the reactor L3 of 2 side of diode rectifier
Portion is as benchmark.That is, in the case where reactor L3 is set between diode rectifier 2 and capacitor C3, about reactor electricity
Press VL polarity, use with electric current flow through reactor L3 in the opposite direction for positive polarity.
Rectification duty ratio drec is added with zero dutycycle closest dz in adder 13, by its result in comparator 12
(drec+dz) it is compared with carrier wave C1.Carrier wave C1 is generated in carrier wave generating unit 23.
Using the comparison result of comparator 12 as being supplied to the switching signal SSc of switch Sc to export.For example, comparator
12 export the signal activated during carrier wave C1 reaches value (drec+dz) or more as switching signal SSc.Switch Sc
It is connected according to the activation of switching signal SSc.
Chop control portion 16 (more precisely shows each voltage with both end voltage Vc and single-phase AC voltage Vin
Value) it is input, according to current instruction value (Ib*-kVL) the output boosting duty ratio dl after being corrected.According to the electricity provided
Command value is flowed, boosting duty ratio dl is determined using the inductance value Lm of both end voltage Vc and single-phase AC voltage Vin and reactor L4
Technology, and the well known technology in patent document 1,3,4 etc., thus omit details herein.
Boosting duty ratio dl is compared with carrier wave C2 in comparator 14.Carrier wave C2 is generated in carrier wave generating unit 24
's.It is exported the comparison result of comparator 14 as the control signal SSI of the opening and closing of control switch SI.For example, comparator
14 export the signal for reaching boosting duty ratio dl period activation below in carrier wave C2 as switching signal SSI.Switch
SI is connected according to the activation of switching signal SSI.
Output voltage command generation unit 31 generates phase voltage directive Vu*, Vv*, Vw*.In the figure 2 example, output voltage
Command generation unit 31 is input with rotary speed ω m and its command value the ω m* of irritability load 6.Rotary speed ω m are by known
Test section be detected, the not shown external structures of command value ω m* are inputted.31 profit of output voltage command generation unit
Phase voltage directive Vu*, Vv*, Vw* are generated with well known method so that the deviation of rotary speed ω m and its command value ω m* subtract
It is small.
Operational part 32 with rectification duty ratio drec, electric discharge duty ratio dc, zero dutycycle closest dz and phase voltage directive Vu*, Vv*,
Vw* is input.(wherein, x represents u, v, w) to 32 calculated value of operational part (drec+dz+dcVx*), and exports these values.Operation
Portion 33 is to input with rectification duty ratio drec and phase voltage directive Vu*, Vv*, Vw*, calculated value (drec (1-Vx*)), and defeated
Go out these values.
Value (drec+dz+dcVx*) is compared with carrier wave C1 in comparator 34, it will value in comparator 35
(drec (1-Vx*)) is compared with carrier wave C1.Comparator 34 is for example exported reaches value (drec+dz+dc in carrier wave C1
Vx* the signal activated during more than), comparator 35 for example export that reach value (drec (1-Vx*)) in carrier wave C1 below
The signal of period activation.
In this way, carrier wave C1 can use module 10a, 10b, thus be shown in FIG. 2 carrier wave generating unit 23 across
More the boundary of module 10a, 10b and be arranged.
By the comparison result input logic of comparator 34,35 and/logic product operational part 36.By the comparison of comparator 34,35
As a result it logic and is carried out as switching signal SSup, SSvp, the SSwp for being respectively supplied to switch element Sup, Svp, Swp defeated
Go out, using their negative logic as switching signal SSun, SSvn, the SSwn for being respectively supplied to switch element Sun, Svn, Swn
It is exported.
In the following, explanation inhibits LC filters 3 by utilizing corrected value kVL correcting current command values as described above
Resonance the case where.
Fig. 3 is the circuit diagram for the equivalent circuit for showing direct power converter shown in FIG. 1.Wherein, it has imported in electricity
Electric current IL, the electric current I3 flowed through in capacitor C3 that anti-device L3 flows through.Electric current IL is exported from diode rectifier 2.Therefore,
In reactor L3 and direct current supply line LH, LL, either one is connected in series in diode rectifier 2 and capacitor C3 to the equivalent circuit
Between in the case of be also appropriate, this is according to the benchmark of reactor voltage VL above-mentioned (or the polarity of reactor voltage VL
Positive direction) it is clear.
As understood according to Fig. 1, the electric current flowed out from LC filters 3 branches to booster circuit 4b and electric current prevents
Portion 4c.Therefore, import flow to the inverter current I4 of inverter 5 when, flow to the direct current of booster circuit 4b electric current IL2 and to
The inverter current I4 that inverter 5 exports, can equally be shown as the current source being connected in parallel with capacitor C3.In addition,
Electric current IL2 can be understood as being worth obtained by corrected value kVL from having subtracted in electric current Ib.The case where by assuming k=0, electric current
Ib can be understood as flowing to the electric current of reactor L4 using current instruction value Ib* as command value.
Fig. 4 is the wire figure that the equivalent circuit of Fig. 3 is interpreted as equivalent circuit composition control system and is shown.By imitative
It imitates patent document 2 to deform the wire figure, the wire figure of Fig. 5, Fig. 6, Fig. 7 can be deformed into successively.In addition, inhibiting to realize
The value of the control system of resonance, command value VL* is 0.
In addition, wire figure, Direct-type power-converting device shown in FIG. 1 can be understood as with voltage according to figure 7
Vr is external disturbance, reponse system in relation to reactor voltage VL.Understand that command value VL* becomes the target of reactor voltage VL
Value, no matter voltage Vr how, reactor voltage VL follows command value VL*=0, thus controls both end voltage V3 and makes and voltage
Vr is consistent.Inhibit the variation of the voltage because of caused by the resonance of LC filters 3 as a result,.
In this way, in the control of present embodiment, not inhibiting electric current, (electric current is equivalent to the corrected value k of electric current Ib
VL it) is superimposed upon in inverter current I4, it is thus possible to utilize reactor voltage VL control electric currents IL2.Electric current IL2 is according to boosting electricity
The action of road 4b is that the copped wave of switch SI is handled and controlled, thus its controlling cycle is shorter than the controlling cycle of inverter 5.For
For Fig. 2, the period of carrier wave C2 is shorter than carrier wave C1, and based on reactor voltage VL is with than inverter 5 to the control of electric current IL2
Control higher frequency carry out.
According to the above it is found that according to the present embodiment, inhibiting the resonance of LC filters 3 even with inhibition electric current
When, the update of the sampling, command value that will not make the control system of control inverter 5 deteriorates.
Fig. 8~Figure 11 be show DC voltage Vdc control input current Iin when being fixed value, reactor voltage VL,
The curve graph of the waveform of electric current IL2.
Fig. 8 and Fig. 9 is shown (is temporarily known as " half period control below using the method control as follows as disclosed in patent document 3
System ") the case where：Switch to electricity according to the once for every half (i.e. the per quart period of single-phase AC voltage Vin) of voltage Vr
(" during the receiving " that patent document 3 is said, electric discharge duty ratio dc is zero, and boosting duty ratio dl is during container C4 chargings
Just) and make (" during authorizing " that patent document 3 is said, electric discharge duty ratio dc are just) during capacitor C4 electric discharges.
In addition, during authorizing it can be appreciated that import phase ω t of single-phase AC voltage Vin, two times of phase ω t
Cosine value cos (2 ω t) be just during, during receiving it can be appreciated that during cosine value cos (2 ω t) is negative.
Figure 10 and Figure 11 is shown as (temporarily referred to as " charge and discharge is automatically controlled below for method control as follows disclosed Patent Document 4
System ") the case where：During at least part during the duty ratio dc that discharges is more than 0, electric current IL2 charges to capacitor C4.
Fig. 8 and Figure 10 show all without used corrected value kVL correction the case where.It is shown in FIG. 8 anti-
The situation of half period control is reflected, electric current IL2 T2 only during receiving are flowed, do not flowed authorizing period T1.It is shown in FIG. 10
The situation of reflection charge and discharge control, total phases charging during and charge and discharge during of the electric current IL2 only described in patent document 4
Between (boosting duty ratio dl be just during) T3 flowings, (boosting duty ratio dl is zero during the electric discharge described in patent document 4
Period) T4 do not flow.
Fig. 9 and Figure 11 shows the case where carrying out having used the correction of corrected value kVL.Electric current is shown in FIG. 9
IL2 it is shown in Fig. 8 authorize the case where period T1 also flows.In addition, Figure 11 shows electric current IL2 in the electric discharge phase shown in Fig. 10
Between T4 the case where also flowing.
Therefore, by the processing of chop control portion 16 (with reference to Fig. 2), boosting duty ratio dl by corrected value kVL shadow
Ring, not necessarily according to described in patent document 3 authorize period/receiving during and patent document 4 described in charging during/discharge
Definition during period/charge and discharge is set like that.However, for the sake of following for simplification, either with or without using corrected value k
The correction of VL all uses the interim appellation of " half period control " " charge and discharge control ".
It is appreciated that according to the comparison of Fig. 8 and Fig. 9 and has used corrected value kVL's by being imported in being controlled in the half period
It corrects, the transition (リ Application ギ Application グ) in input current Iin reduces.Equally, it is appreciated that according to the comparison of Figure 10 and Figure 11 logical
The correction for being imported in charge and discharge control and having used corrected value kVL is crossed, the transition in input current Iin reduces.
In this way, the half period is whether used to control or use charge and discharge control, corrected value kVL has been used by importing
Correction, all confirm can reduce because LC filters 3 resonance generate influence.
In addition, in the case where using half period control, current instruction value Ib* is set as zero authorizing period T1.
Therefore, period T1 is being authorized, is only flowing through inhibition electric current in the case where reactor voltage VL is negative.
On the other hand, using charge and discharge control in the case of, current instruction value Ib* during more in be more than value
k·VL.Therefore, the current instruction value after correction (Ib*-kVL) also during more in be just.Therefore, no matter reactor
The both end voltage of L3, that is, reactor voltage VL it is positive and negative how, all flow through inhibition electric current in reactor L4, inhibit LC filters
The effect of resonance be improved.
C. it deforms
In rectification circuit 203, diode rectifier 2, capacitor C3, reactor L3 position relationship be not limited to it is above-mentioned
Example.The reactive component of diode rectifier 2 itself, capacitive component cannot be ignored, it is thus possible to carry out various modifications below.
Figure 12 is the circuit diagram of the deformation for the position relationship for showing reactor L3 and diode rectifier 2.Show in above-mentioned
In example, reactor L3 specific capacitance device C3 are directly connected in series with (certainly, reactance further from inverter 5 with direct current supply line LH
Device L3 can also be directly connected in series with direct current supply line LL).However, in structure as shown in figure 12, reactor L3 is than electricity
Container C3 is connected in series with direct current supply line LH indirectly further from inverter 5, via diode rectifier 2.Specifically, reactance
Device L3 is connected in series in the input side of diode rectifier 2 with single phase alternating current power supply 1.
In this configuration, for reactor L3 than diode rectifier 2 further from inverter 5, voltage Vr is rectification circuit 203
The rectified voltage of output.In this case, reactor L3 is connected in series in diode rectifier 2 with single phase alternating current power supply 1
Input side.Therefore, by being embodied as the positive direction of the direction (polarity of reactor voltage VL) of reactor voltage VL from list
The high potential of phase alternating voltage Vin towards the direction of low potential, even in this configuration, with above-mentioned embodiment one
Sample, it is clear that equivalent circuit shown in Fig. 3 is also appropriate, can obtain above-mentioned functions and effects.
Replace resonance to inhibit control unit 15 using following structure in the deformation (with reference to Fig. 2)：With reference to solid at some
Fixed direction measures the value of the potential difference at the both ends reactor L3 and from the high potential of single-phase AC voltage Vin towards low potential
Direction determines reactor voltage VL, and exports the corrected value based on reactor voltage VL.
Figure 15 be example reactor L3 than diode rectifier 2 further from inverter 5 in the case of, replace shown in Fig. 2
The resonance resonance that inhibits control unit 15 and use inhibit the structure of control unit 151 and the periphery of reactor L3 (referring to Fig.1)
Block diagram.
Here, using close to the current potential of the end of the reactor L3 of the side of diode rectifier 2 as benchmark, using reactance
The potential difference VL1 at the both ends of device L3.Specifically, the connection of the cathode of the anode and diode D22 of reactor L3 and diode D21
The current potential of point becomes the benchmark of above-mentioned potential difference.
It (is more precisely respective to inhibit control unit 151 to input potential difference VL1 and single-phase AC voltage Vin to resonance
Value).Resonance inhibits control unit 151 that there is polarity judging portion 15b, polarity judging portion 15b to judge one of single-phase AC voltage Vin
The polarity in direction (such as in fig.15 with the direction of the single-phase AC voltage Vin shown in arrow), polar positive and negative point according to this
Other output valve 1, -1.The judgement can also use its phase using the positive and negative of single-phase AC voltage Vin.Here, blow-up
Galvanic electricity presses the benchmark of Vin using the current potential of the anode of diode D23 and the tie point of the cathode of diode D24.
Resonance inhibits control unit 151 also to have multiplier 15a, 15c.Multiplier 15a is by potential difference VL1 and polarity judging portion
The output of 15b is multiplied.As a result, the reactor voltage VL that above-mentioned embodiment is said is obtained from multiplier 15a.Multiplier 15c
The product of calculating reactance device voltage VL and specified value k, obtain corrected value kVL.
Certainly, polarity judging portion 15b also can determine the polarity of single-phase AC voltage Vin, polar positive and negative point according to this
Other output valve k ,-k, do not need multiplier 15c in this case.In addition, the resonance of above-mentioned embodiment inhibits control unit
15 can also be considered as the structure for deleting multiplier 15a and polarity judging portion 15b.In this configuration, it is clear that can also obtain
The functions and effects of above-mentioned each embodiment.
Figure 13 is that the circuit diagram of Figure 12 circuits further deformed is shown that reactor L3 and capacitor C3 and diode are whole
Flow the deformation of the position relationship between device 2.In the above example, capacitor C3 be directly connected in direct current supply line LH, LL it
Between.However, in the structure shown in Figure 13, capacitor C3 via diode rectifier 2 be indirectly attached to direct current supply line LH,
Between LL.Also, reactor L3 specific capacitance device C3 are further from inverter 5, via diode rectifier 2 indirectly with DC power supply
Line LH connections.Specifically, reactor L3 is and single-phase alternating current relative to the input side and capacitor C3 of diode rectifier 2
Source 1 is connected in series with.
In this configuration, the electric current I3 for flowing through capacitor C3 also becomes exchange, therefore the polarity of both end voltage V3 is also
Alternately change, the functions and effects of above-mentioned embodiment can be obtained as the structure of Figure 12.Because according to Fig. 7, nothing
By make to flow through the polarity of the electric current I3 of capacitor C3, both end voltage V3 due to the polarity of single-phase AC voltage Vin it is different or
It is different not due to the polarity of single-phase AC voltage Vin, even or even in the presence of the voltage Vr as external disturbance, all control becomes
It is zero to make reactor voltage VL, and this point is constant.
Moreover, in the structure shown in Figure 13, diode rectifier 2 also undertakes electric current blocking portion 4c such as diode D43
Function, thus have the advantages that not needing electric current blocking portion 4c.
Figure 14 is the circuit diagram for the deformation that the circuit diagram of Figure 13 circuits further deformed is shown to diode rectifier 2.
Here, by a pair of diodes of hot side in diode rectifier 2 be divided into input charge-discharge circuit 4 diode and with
This two groups of the diode that inverter 5 connects.
Specifically, diode rectifier 2 has diode D21a, D21b, D22, D23a, D23b, D24.Diode D21a,
The anode of D21b is connect with one end of capacitor C3 jointly, and the anode of diode D23a, D23b are jointly another with capacitor C3
End connection.The cathode of diode D21a, D23a are connect with direct current supply line LH jointly, and the cathode of diode D21b, D23b all pass through
It is connect with switch SI by reactor L4.That is, in the structure shown in Figure 14, relative to circuit shown in Figure 13, diode D21 is simultaneous
Make diode D21a, D21b, diode D23 doubles as diode D23a, D23b.In addition, in charge-discharge circuit 4, reactor L4
It is not direct to be connect with direct current supply line LH.
In this configuration, it is to be understood that applied to be made of diode D21a, D23a, D22, D24 to direct current supply line LH
The bridge circuit of making alive Vr is made of the electricity for applying voltage Vr to direct current supply line LH diode D21b, D23b, D22, D24
Bridge circuit, diode rectifier 2 include the two bridge circuits.In this structure, it is clear that can also obtain above-mentioned each
The functions and effects of embodiment.
It describes the invention in detail, however above description is to illustrate in terms of whole, the present invention is not limited thereto.
It is understood that without departing from the present invention it is contemplated that the countless variations not illustrated.
Claims (14)
1. a kind of control method of charge-discharge circuit, which is the charge and discharge controlled in direct power converter
The method of circuit,
The direct power converter has：
1st power cord (LH)；
2nd power cord (LL) is applied in the current potential lower than the 1st power cord (LH)；
Rectification circuit (203), have be applied in single-phase AC voltage (Vin) input side and with the 1st power cord (LH)
And the outlet side of the 2nd power cord (LL) connection；
Charge-discharge circuit (4) is set to the 1st power cord (LH) and institute in the outlet side of the rectification circuit (203)
It states between the 2nd power cord (LL)；And
Inverter (5), the voltage i.e. direct current being entered between the 1st power cord (LH) and the 2nd power cord (LL)
It presses (Vdc),
The rectification circuit (203) has：
Diode rectifier (2) carries out single-phase full-wave rectifier circuit；
1st capacitor (C3) directly or is coupled indirectly to the 1st power cord via the diode rectifier (2)
(LH) between the 2nd power cord (LL)；And
1st reactor (L3), directly or via the diode rectifier (2) in series with the 1st power cord (LH)
Or the 2nd power cord (LL) connection, and than the 1st capacitor (C3) further from the inverter (5),
The charge-discharge circuit (4) has：
Buffer circuit (4a) comprising the 2nd capacitance being set between the 1st power cord (LH) and the 2nd power cord (LL)
Device (C4) makes the 2nd capacitor (C4) discharge according to controllable time ratio (dc)；And
Booster circuit (4b), to the rectified voltage (V3, Vr) of the rectification circuit (203) output boosted and to described the
2 capacitors (C4) charge, wherein
The the voltage (VL) of the 1st reactor (L3) the high, more reduces the DC current for being input to the booster circuit (4b)
(IL2)。
2. the control method of charge-discharge circuit according to claim 1, wherein
1st reactor (L3) is set between the diode rectifier (2) and the 1st capacitor (C3), the 1st electricity
The polarity of the voltage (VL) of anti-device (L3) is just with the opposite direction for flowing through the direction of the electric current of the 1st reactor (L3).
3. the control method of charge-discharge circuit according to claim 1, wherein
1st reactor (L3) is than the diode rectifier (2) further from the inverter (5), the 1st reactor
(L3) polarity of voltage (VL) with from the high potential of the single-phase AC voltage (Vin) towards the direction of low potential be just.
4. the control method of charge-discharge circuit according to any one of claims 1 to 3, wherein
Corrected value (the k proportional to voltage (VL) of the 1st reactor (L3) will be subtracted from the 1st command value (Ib*)
VL the 2nd command value (Ib*-kVL) obtained from) is used as desired value, controls the DC current (IL2), the 1st command value
(Ib*) by the amplitude (Im) for being input to the alternating current (Iin) of the diode rectifier (2) and the diode rectifier
(2) voltage (Vr) exported determines.
5. the control method of charge-discharge circuit according to claim 4, wherein
The booster circuit (4b) has the 2nd reactor (L4) for flowing through the DC current (IL2), and is made whether to described
2nd capacitor (C4) exports the copped wave processing of the DC current (IL2),
The copped wave processing, the time ratio are carried out according to by time ratio (dl) and defined carrier wave (C2) result of the comparison
(dl) it is voltage (Vc), the single-phase alternating current for using the 2nd command value (Ib*-kVL), the 2nd capacitor (C4)
The inductance value (Lm) of (Vin) and the 2nd reactor (L4) is pressed to determine.
6. the control method of charge-discharge circuit according to any one of claims 1 to 3, wherein
Two times of cosine value (cos (2 ωs of the buffer circuit (4a) in the phase (ω t) of the single-phase AC voltage (Vin)
T)) be it is negative during in charge to the 1st capacitor (C3), during the cosine value is just in make the 1st capacitance
Device (C3) discharges.
7. the control method of charge-discharge circuit according to claim 4, wherein
Two times of cosine value (cos (2 ωs of the buffer circuit (4a) in the phase (ω t) of the single-phase AC voltage (Vin)
T)) be it is negative during in charge to the 1st capacitor (C3), during the cosine value is just in make the 1st capacitance
Device (C3) discharges.
8. the control method of charge-discharge circuit according to claim 5, wherein
Two times of cosine value (cos (2 ωs of the buffer circuit (4a) in the phase (ω t) of the single-phase AC voltage (Vin)
T)) be it is negative during in charge to the 1st capacitor (C3), during the cosine value is just in make the 1st capacitance
Device (C3) discharges.
9. the control method of charge-discharge circuit according to any one of claims 1 to 3, wherein
In a part at least during the time ratio (dc) is more than 0, the buffer circuit (4a) is carried out to the described 1st
The charging of capacitor (C3).
10. the control method of charge-discharge circuit according to claim 4, wherein
In a part at least during the time ratio (dc) is more than 0, the buffer circuit (4a) is carried out to the described 1st
The charging of capacitor (C3).
11. the control method of charge-discharge circuit according to claim 5, wherein
In a part at least during the time ratio (dc) is more than 0, the buffer circuit (4a) is carried out to the described 1st
The charging of capacitor (C3).
12. a kind of control device of charge-discharge circuit, which is the control by the charge-discharge circuit described in claim 5
The device (10) that method processed controls the charge-discharge circuit (4) to be controlled, the control device have：
Subtracter (17) subtracts the corrected value (kVL) from the 1st command value (Ib*) and obtains the 2nd instruction
It is worth (Ib*-kVL)；
Chop control portion (16) uses the voltage of the 2nd command value (Ib*-kVL) and the 2nd capacitor (C4)
(Vc), inductance value (Lm) the decision time ratio (dl) of the single-phase AC voltage (Vin), the 2nd reactor (L4)；
And
Comparator (14), the time ratio (dl) and the carrier wave (C2) are compared, the control of output control copped wave
Signal (SSI).
13. a kind of charge-discharge circuit (4), by the controlling party of the charge-discharge circuit by any one of claim 1~11
Method is controlled,
Also there is the charge-discharge circuit (4) electric current blocking portion (4c), the electric current blocking portion (4c) to be set to the 1st power cord
(LH) or the 2nd power cord (LL), prevention electric current flow to the 1st capacitor (C3) from the buffer circuit (4a).
14. a kind of direct power converter,
The direct power converter is with the charge-discharge circuit (4) described in claim 13, the 1st power cord (LH), institute
State the 2nd power cord (LL), the diode rectifier (2), the 1st capacitor (C3), the 1st reactor (L3) and institute
State inverter (5).
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2014-254777 | 2014-12-17 | ||
| JP2014254777 | 2014-12-17 | ||
| PCT/JP2015/084887 WO2016098714A1 (en) | 2014-12-17 | 2015-12-14 | Charge/discharge circuit, control method for charge/discharge circuit, control device for charge/discharge circuit, and direct power converter |
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| Publication Number | Publication Date |
|---|---|
| CN107148729A CN107148729A (en) | 2017-09-08 |
| CN107148729B true CN107148729B (en) | 2018-08-10 |
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| CN201580065019.7A Active CN107148729B (en) | 2014-12-17 | 2015-12-14 | The control device and direct power converter of charge-discharge circuit, the control method of charge-discharge circuit, charge-discharge circuit |
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| Country | Link |
|---|---|
| US (1) | US9948200B2 (en) |
| EP (1) | EP3236575B9 (en) |
| JP (1) | JP5920520B1 (en) |
| CN (1) | CN107148729B (en) |
| AU (1) | AU2015364879C1 (en) |
| BR (1) | BR112017011261B1 (en) |
| ES (1) | ES2959498T3 (en) |
| MY (1) | MY182570A (en) |
| WO (1) | WO2016098714A1 (en) |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| JP6772577B2 (en) * | 2016-06-22 | 2020-10-21 | ダイキン工業株式会社 | Charge / discharge circuit, charge / discharge circuit control method, and direct power converter |
| JP6265297B1 (en) * | 2016-09-30 | 2018-01-24 | ダイキン工業株式会社 | Control device for direct power converter. |
| KR101875914B1 (en) * | 2016-10-31 | 2018-07-06 | 한국철도기술연구원 | System for charging and discharging of energy for railway vehicle |
| JP6418287B1 (en) * | 2017-06-30 | 2018-11-07 | ダイキン工業株式会社 | Control unit for direct power converter |
| JP6962203B2 (en) * | 2018-01-11 | 2021-11-05 | 株式会社デンソー | Boost system |
| SG11202011091QA (en) * | 2018-05-10 | 2020-12-30 | Toshiba Kk | Dc transformation system |
| JP6721097B2 (en) * | 2018-09-27 | 2020-07-08 | ダイキン工業株式会社 | Direct power converter, controller |
| EP3896835B1 (en) * | 2018-12-13 | 2024-02-28 | Mitsubishi Electric Corporation | Power conversion device |
| CN110133516B (en) * | 2019-02-27 | 2021-02-26 | 延边中谷领创电力科技有限公司 | Battery charging and discharging device |
| JP7206491B2 (en) * | 2019-03-28 | 2023-01-18 | ダイキン工業株式会社 | Controller for direct power converter |
| EP3979459A4 (en) * | 2019-05-29 | 2023-01-11 | Toshiba Mitsubishi-Electric Industrial Systems Corporation | Power conversion system |
| JP7436783B2 (en) * | 2019-09-30 | 2024-02-22 | ダイキン工業株式会社 | power converter |
| CN112117924B (en) * | 2020-09-23 | 2021-08-13 | 南通大学 | Control method of DCM single-bridge-arm integrated split-source boost inverter |
| EP4207573A4 (en) * | 2020-09-30 | 2024-03-06 | Daikin Ind Ltd | Power conversion device |
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| WO2014057883A1 (en) * | 2012-10-10 | 2014-04-17 | ダイキン工業株式会社 | Direct power conversion device and method for controlling direct power conversion device |
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| Publication number | Publication date |
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| BR112017011261B1 (en) | 2022-09-06 |
| CN107148729A (en) | 2017-09-08 |
| EP3236575B9 (en) | 2024-01-10 |
| AU2015364879C1 (en) | 2018-10-18 |
| WO2016098714A1 (en) | 2016-06-23 |
| MY182570A (en) | 2021-01-25 |
| BR112017011261A2 (en) | 2017-12-26 |
| ES2959498T3 (en) | 2024-02-26 |
| EP3236575A1 (en) | 2017-10-25 |
| US20170324348A1 (en) | 2017-11-09 |
| AU2015364879A1 (en) | 2017-06-22 |
| JP5920520B1 (en) | 2016-05-18 |
| JP2016119835A (en) | 2016-06-30 |
| EP3236575B1 (en) | 2023-08-23 |
| AU2015364879B2 (en) | 2018-06-21 |
| US9948200B2 (en) | 2018-04-17 |
| EP3236575A4 (en) | 2018-06-13 |
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