CN107113265B

CN107113265B - Efficient FBMC transmission and reception for multiple access communication systems

Info

Publication number: CN107113265B
Application number: CN201480083555.5A
Authority: CN
Inventors: 赵兆; 龚希陶
Original assignee: Huawei Technologies Duesseldorf GmbH
Current assignee: Huawei Technologies Duesseldorf GmbH
Priority date: 2014-12-19
Filing date: 2014-12-19
Publication date: 2020-06-26
Anticipated expiration: 2034-12-19
Also published as: WO2016096032A1; CN107113265A

Abstract

A transmitting device for generating a filter bank multi-carrier FBMC signal from a payload signal is provided. The transmitting device comprises at least one filtering unit and is adapted to generate at least one resource block from a time-frequency resource grid corresponding to the payload signal. Each resource block is a specific spectral region for a specific slot and includes one spectral middle region and at least one spectral edge region located at a spectral edge of the resource block. The at least one filtering unit is adapted to generate a spectral middle region of each resource block by filtering a first part of a signal derived from the payload signal, thereby generating a dual sideband modulated first part of the FBMC signal. Furthermore, the filtering unit is adapted to generate at least one spectral border-region of each resource block by filtering at least a second part of the signal derived from the payload signal, thereby generating a single sideband modulated second part of the FBMC signal.

Description

Efficient FBMC transmission and reception for multiple access communication systems

Technical Field

The present invention relates to a Filter Bank Multi-Carrier Modulation (FBMC) -based wireless communication system for design based on general frequency domain multiple access resources and structures, and relates to but is not limited to Multi-user uplink transmission or precoded downlink transmission, such as codebook-based or beamforming-based MIMO transmission.

Background

Filterbank Multicarrier (FBMC) transmission with Offset Quadrature-Amplitude Modulation (OQAM) is one of the candidate transmission schemes for future wireless systems such as 5G. Compared with the most advanced Cyclic-Prefix orthogonal frequency Division Multiplexing (CP-OFDM) transmission, the FBMC/OQAM system has the advantages of better controlling out-of-band radio power leakage and achieving higher spectral efficiency.

In the baseband discrete time model with M subcarriers, the FBMC/OQAM signal at the transmitter side can be written as:

wherein, P_T,K[t]Is a prototype filter P_T[t]Frequency-shifted version of (a):

c_k,nis a complex symbol (OQAM symbol) modulated on the mth subcarrier of the nth symbol, and can be expressed as:

wherein d is_k,nRepresenting the real-valued symbols (Pulse Amplitude Modulation, PAM symbols)), an additional phase term

In order to alternately add real and imaginary parts in time and frequency domains to construct an OQAM symbol. The following is an example:

therefore, for simplicity, we can overwrite the FBMC/OQAM signal at the transmitter side:

wherein

Therefore, the FBMC/OQAM signal can be a PAM modulated signal. Note that the PAM notation model is employed below.

Assuming that the prototype filter is symmetric and real-valued, r is in the real domain under ideal channel conditions_k,nAnd r_k',n'The condition of orthogonality is satisfied between the two symbols,

where Re { } is the real part of the complex number, δ represents the dirac δ function.

Since the prototype filter used by FBMC has high side lobe suppression properties, the mutual interference between non-adjacent subcarriers k and k' is negligible. For adjacent subcarriers, i.e., k' ± 1, their respective orthogonality depends only on the channel flatness on the two subcarriers. However, if non-flat channels exist between boundary subcarriers, it is difficult to mitigate mutual interference by prototype filters.

Such a situation may occur, for example, in channel precoded downlink transmission such as multi-antenna transmission based on codebook or beamforming, or in multi-user uplink transmission. Since the channel between the boundary subcarriers of two pre-encoded blocks or users is not flat, strong mutual interference between the two subcarriers occurs.

For this case, possible schemes are:

subcarrier backoff: the code block/user has at least one boundary subcarrier free. The method can be applied to systems with difficult interference cancellation, such as multi-user uplink transmission. Although the design complexity of the transceiver is relatively low, this solution leads to a high loss of system spectral efficiency if there are a large number of blocks/users. This scenario is further described in the description of fig. 3.

Precoder based interference pre-cancellation: in this scheme, a transmitter signature pre-encoder pre-cancels mutual interference based on prior knowledge of the channel. This may apply to systems where Channel State Information (CSI) is present at the transmitter, e.g., channel precoded downlink transmissions. Two main drawbacks of this scheme are high implementation complexity and sensitivity to CSI, i.e., the performance of the precoder is highly dependent on the accuracy of channel information (channel knowledge). Therefore, the performance is poor in practice. This scenario is further described in the description of fig. 4.

Quadrature amplitude modulation modulated boundary band (QMB): in this scheme, to avoid inter-block interference (IBI), boundary subcarriers are QAM modulated and a Cyclic Prefix (CP) is added instead of the conventional PAM (or OQAM) modulation. The resulting fast internal and inter-symbol interference is mitigated by the new transceiver scheme. The advantages of this approach are a slight loss of spectral efficiency and robustness of the CSI at the transmitter. The limitation is that the complexity of the transceiver design increases due to interference cancellation. This scenario is further described in the description of fig. 5.

As mentioned above, in the proposed scheme, there is strong mutual interference between boundary subcarriers belonging to two different user blocks. This has long been a published problem for FBMC. To date, a great deal of effort has been made to cancel or mitigate this mutual interference, e.g., using precoding IBI cancellation, or CP-QAM modulated boundary bands (QMBs), with a simple scheme with at least one subcarrier backoff. However, there is no satisfactory solution to effectively cancel this interference without loss of spectral efficiency and low complexity in transceiver design.

Disclosure of Invention

An object of the present invention is to provide a transmitting apparatus, a receiving apparatus, a transmitting method, and a receiving method, which can reduce the design complexity of a transceiver while achieving high spectral efficiency.

This object is achieved by a transmitting device (3) for generating a filter bank multi-carrier FBMC signal (2) from a payload signal (1), a receiving device (4) for receiving a payload signal (1) from a filter bank multi-carrier FBMC signal (2) comprising at least one resource block (100, 101, 210, 211, 220, 221), a method of generating a filter bank multi-carrier FBMC signal (2) from a payload signal (1), and a method of receiving a payload signal (1) from a filter bank multi-carrier FBMC signal (2) comprising at least one resource block (100, 101, 210, 211, 220, 221) as provided herein, which further is achieved by a computer program product controlling a computer or a digital signal processor.

In order to completely avoid interference between boundary subcarriers belonging to different user blocks, the present invention proposes a new modulation design and a new block/frame structure design for FBMC/OQAM. It has no loss of spectral efficiency and the corresponding transceiver can be implemented with lower complexity. It is assumed below that the FBMC system is using the PHYDYAS prototype filter. Nevertheless, all design schemes and algorithms can be easily adapted to other prototype filters. In addition, a multi-antenna channel precoding downlink transmission system is shown below. However, all of the designs and algorithms can be easily adapted to other systems with inter-block interference and multi-user interference.

In a first aspect of the invention, a transmitting device for generating a filter bank multi-carrier, FBMC, signal from a payload signal is provided. The transmitting device comprises at least one filtering unit and is adapted to generate at least one resource block from a time-frequency resource grid corresponding to the payload signal. Each resource block is a specific spectral region for a specific time slot and comprises one spectral middle region and at least one spectral edge region located at a spectral edge of the resource block. The at least one filtering unit is adapted to generate the spectral mid-region of each resource block by filtering a first part of a signal derived from the payload signal, thereby generating a dual sideband modulated first part of the FBMC signal. Furthermore, the filtering unit is adapted to generate the at least one spectral border-region of each resource block by filtering at least a second part of the signal derived from the payload signal, thereby generating a single sideband modulated second part of the FBMC signal. Thereby making it possible to avoid inter-block interference and achieve high spectral efficiency.

In a first implementation form according to the first aspect, the single sideband modulated second part of the FBMC signal comprises a spectral cut-off edge and a non-cut-off edge corresponding to a starting edge of an underlying baseband signal. The at least one filtering unit is adapted to generate the at least one payload region of the spectral border region such that the non-cut-off edge of the second part of the FBMC signal is on a spectral middle region of the spectral border region and the cut-off edge of the second part of the FBMC signal is on a non-spectral middle region of a side of the spectral border region, thereby reducing inter-block interference with great advantage.

In a second implementation form according to the first aspect or the first implementation form the double sideband modulated first part of the FBMC signal of the middle spectral region is spectrally partially overlapping the single sideband modulated second part of the FBMC signal of the edge spectral region. The single sideband modulated second part of the FBMC signal has no or hardly any signal components beyond the spectral edges of the spectral edge regions opposite the spectral middle region, thereby further reducing inter-block interference.

In a third implementation form according to the first aspect as such or the first or the second implementation form each spectral border-region comprises at least one payload segment of the second part of the FBMC signal and/or comprises at least one zero-padding segment of at least one zero-padding or no signal. The at least one payload segment and the at least one zero padding segment have the same duration and are arranged consecutively in time if both segments are included within the edge region of the spectrum. By alternating between payload segments and zero-filled segments within the edge regions of the spectrum, efficient utilization of the spectrum is achieved, as the zero-filled segment regions can be used by adjacent resource blocks.

In a fourth implementation according to the third implementation, each spectral border region comprises at least two payload segments and/or at least two zero padding segments. If at least two payload segments and at least two zero-padding segments are both included in a spectrum border region, the at least two payload segments and the at least two zero-padding segments are temporally alternately arranged in the spectrum border region, so that efficient use of the spectrum can be achieved.

In a fifth implementation form according to the first aspect as such or any of the preceding implementation forms, the transmitting device comprises an encoding unit adapted to symbol map the payload signal resulting in a symbol mapped payload signal, and/or a resource mapping unit adapted to perform a resource mapping on said symbol mapped payload signal or a signal derived from said payload signal to obtain a resource mapped payload signal, and/or a modulation unit adapted to modulate said resource mapped payload signal or a signal derived from said payload signal resulting in a modulated payload signal, and/or a layer mapping unit adapted for MIMO layer mapping of the modulated payload signal or a signal derived from the payload signal resulting in a layer mapped payload signal, thereby making efficient processing of the payload signal into the FBMC signal possible.

In a second aspect of the invention, a receiving device for receiving a payload signal in accordance with a filter bank multi-carrier, FBMC, signal comprising at least one resource block and comprising at least one filtering unit is provided. The resource block is a particular spectral region for a particular time slot. Each resource block includes a spectral mid-region comprising a dual sideband modulated first portion of the FBMC signal, and at least one spectral edge region located at a spectral edge of each resource block comprising a single sideband modulated second portion of the FBMC signal. The at least one filtering unit is adapted to filter the double sideband modulated first part of the FBMC signal, thereby generating a first part of a signal derived from the FBMC signal. The at least one filtering unit is further adapted to filter the single sideband modulated second part of the FBMC signal, thereby generating a second part of the signal derived from the FBMC signal, thereby possibly receiving a validly transmitted FBMC signal.

In a first implementation form according to the second aspect, the double sideband modulated first part of the FBMC signal of the spectral middle region and the single sideband modulated second part of the FBMC signal of the spectral edge region partially overlap spectrally. The single sideband modulated second part of the FBMC signal has no or hardly any signal components beyond the spectral edges of the spectral edge regions opposite the spectral middle region, so that an efficient use of the spectrum is possible.

In a second implementation form according to the second aspect or the first implementation form, each spectral border-region comprises at least one payload segment of the second part of the FBMC signal and/or at least one zero-padding segment comprising at least one zero-padding or no signal. If at least one payload segment and at least one zero padding segment are both included within a spectrum edge region, the at least one payload segment and the at least one zero padding segment have the same duration and are arranged consecutively in time, thereby making it possible to achieve efficient spectrum utilization of the spectrum edge region, since the zero padding segment region can be used by adjacent resource blocks.

In a third implementation form according to the second implementation form, the spectral border region comprises at least two payload segments and/or at least two zero padding segments. If at least two payload segments and at least two zero-padding segments are both included within a spectrum border region, the at least two payload segments and the at least two zero-padding segments are temporally alternately arranged within the spectrum border region, thereby achieving efficient use of the spectrum.

In a fourth implementation form according to the second aspect as such or the first, second or third implementation form of the second aspect, the receiving device comprises a layer demapping unit adapted for MIMO layer demapping the first part of the signal derived from the FBMC signal and the second part of the signal derived from the FBMC signal resulting in a first part of a layer demapping signal and a second part of the layer demapping signal, and/or a demodulation unit adapted for demodulating the first part of the layer demapping signal, the second part of the layer demapping signal and/or a signal derived from the FBMC signal resulting in a first part of a demodulated signal and a second part of the demodulated signal, and/or an equalizer adapted for double sideband equalization of the first part of the demodulated signal or of a signal derived from the FBMC signal, -deriving a first part of an equalized signal, and/or-single sideband equalizing said second part of said demodulated signal or a signal derived from said FBMC signal, deriving a second part of said equalized signal, and/or-a resource demapping unit adapted for resource demapping said equalized signal or a signal derived from said FBMC signal, deriving a resource demapping signal, and/or-a decoding unit adapted for symbol demapping said resource demapping signal or a signal derived from said FBMC signal, deriving said payload signal, thereby making it possible to efficiently process said FBMC signal into said payload signal.

In a third aspect of the present invention there is provided a communication system comprising a first transmitting device according to the first aspect or any implementation of the present invention, a second transmitting device according to the first aspect or any implementation, and a receiving device according to the second aspect or any implementation. The first transmitting device is adapted to transmit a first payload signal comprising a first resource block, the first resource block comprising a first spectral border region. The second transmitting device is adapted to transmit a second payload signal comprising a second resource block comprising a second spectral border region. The first and second transmitting devices are adapted to simultaneously transmit the first and second spectrally adjacent resource blocks and to transmit the spectral border regions of the first and second resource blocks on the same frequency, wherein at least one payload segment of the first spectral border region overlaps with at least one zero padding segment of the second spectral border region and at least one payload segment of the second spectral border region overlaps with at least one zero padding segment of the first spectral border region. The receiving device is adapted to receive the first resource block and the second resource block and thereby regenerate the first payload signal and the second payload signal, making it possible to efficiently transmit and receive resource blocks.

In a fourth aspect of the invention, a method for generating a filter bank multi-carrier, FBMC, signal from a payload signal is provided. The method comprises generating at least one resource block from a time-frequency resource grid corresponding to the payload signal, wherein each resource block is a specific spectral region for a specific time slot and comprises a spectral middle region and at least one spectral edge region located at a spectral edge of the resource block, filtering a first part of a signal derived from the payload signal to generate a double sideband modulated first part of the FBMC signal to generate the spectral middle region of each resource block, and filtering a second part of the signal derived from the payload signal to generate a single sideband modulated second part of the FBMC signal to generate the at least one spectral edge region of each resource block to achieve efficient utilization of spectrum.

In a first implementation form according to the fourth aspect, the single sideband modulated second part of the FBMC signal comprises a spectral cut-off edge and a non-cut-off edge corresponding to a starting edge of an underlying baseband signal. The at least one payload region of the spectral border region is generated by filtering such that the non-cut-off edge of the second portion of the FBMC signal is on a spectral middle region of the spectral border region and the cut-off edge of the second portion of the FBMC signal is on a non-spectral middle region on one side of the spectral border region, thereby advantageously reducing inter-block interference.

In a second implementation form according to the fourth aspect as such or according to the first implementation form of the fourth aspect, the double sideband modulated first part of the FBMC signal of the spectral middle region is spectrally partially overlapping with the single sideband modulated second part of the FBMC signal of the spectral edge region. The single sideband modulated second part of the FBMC signal has no or hardly any signal components beyond the spectral edges of the spectral edge regions opposite the spectral middle region, thereby further reducing inter-block interference.

In a third implementation form according to the fourth aspect as such or according to the first or second implementation form of the fourth aspect, each spectral border-region comprises at least one payload segment of the second part of the FBMC signal and/or comprises at least one zero-padding segment of at least one zero-padded or no-signal. The at least one payload segment and the at least one zero padding segment have the same duration and are arranged consecutively in time if both the at least two payload segments and the at least two zero padding segments are included within the spectral border region. By alternating between payload segments and zero-filled segments within the edge regions of the spectrum, efficient utilization of the spectrum is achieved, as the zero-filled segment regions can be used by adjacent resource blocks.

In a fourth implementation form according to the third implementation form of the fourth aspect, each spectral border-section comprises at least two payload segments and/or at least two zero-padding segments. If at least two payload segments and at least two zero-padding segments are both included in a spectrum border region, the at least two payload segments and the at least two zero-padding segments are temporally alternately arranged in the spectrum border region, so that efficient use of the spectrum can be achieved.

In a fifth implementation form according to the fourth aspect as such or according to any of the preceding implementation forms of the fourth aspect, the method comprises symbol mapping the payload signal to obtain a symbol mapped payload signal, and/or resource mapping the symbol mapped payload signal or a signal derived from the payload signal to obtain a resource mapped payload signal, and/or modulating the resource mapped payload signal or a signal derived from the payload signal to obtain a modulated payload signal, and/or MIMO layer mapping the modulated payload signal or a signal derived from the payload signal to obtain a layer mapped payload signal, such that the payload signal may be efficiently processed to the FBMC signal.

In a fifth aspect of the invention, a method for receiving a payload signal from a filter bank multi-carrier, FBMC, signal comprising at least one resource block is provided. The resource block is a particular spectral region for a particular time slot. Each resource block includes a spectral mid-region comprising a dual sideband modulated first portion of the FBMC signal, and at least one spectral edge region located at a spectral edge of each resource block comprising a single sideband modulated second portion of the FBMC signal. The method includes filtering the dual sideband modulated portion of the FBMC signal to generate a first portion of a signal derived from the FBMC signal, filtering the single sideband modulated portion of the FBMC signal to generate a second portion of the signal derived from the FBMC signal, and regenerating the payload signal of the signal derived from the FBMC signal to enable reception of a spectrally encoded signal.

According to a fifth aspect in a first implementation form the double sideband modulated first part of the FBMC signal of the spectral middle section spectrally partially overlaps with the single sideband modulated second part of the FBMC signal of the spectral edge section. The single sideband modulated second part of the FBMC signal has no or hardly any signal components beyond the spectral edges of the spectral edge regions opposite the spectral middle region, so that an efficient use of the spectrum is possible.

In a second implementation form according to the fifth aspect as such or according to the first implementation form of the fifth aspect, each spectral border region comprises at least one payload segment of the second part of the FBMC signal and/or at least one zero-padding segment comprising at least one zero-padding or no signal. If at least two payload segments and at least two zero padding segments are both comprised within a spectrum edge region, the at least one payload segment and the at least one zero padding segment have the same duration and are arranged consecutively in time, thereby making it possible to achieve efficient spectrum utilization of the spectrum edge region, since the zero padding segment region can be used by adjacent resource blocks.

In a third implementation form according to the second implementation form of the fifth aspect, the spectral border section comprises at least two payload sections and/or at least two zero padding sections. If at least two payload segments and at least two zero-padding segments are both included within a spectrum border region, the at least two payload segments and the at least two zero-padding segments are temporally alternately arranged within the spectrum border region, thereby achieving efficient use of the spectrum.

In a fourth implementation form according to the fifth aspect as such or according to the first, second or third implementation form of the fifth aspect, the receiving method comprises MIMO layer demapping the first part of the signal derived from the FBMC signal and the second part of the signal derived from the FBMC signal resulting in a first part of a layer demapping signal and a second part of the layer demapping signal, and/or demodulating the first part of the layer demapping signal, the second part of the layer demapping signal and/or a signal derived from the FBMC signal resulting in a first part of a demodulated signal and a second part of the demodulated signal, and/or double sideband equalizing the first part of the demodulated signal or a signal derived from the FBMC signal resulting in a first part of an equalized signal, and/or demodulating the second part of the demodulated signal or a signal derived from the FBMC equalized signal resulting in a second part of the demodulated signal Obtaining a second portion of the equalized signal, and/or resource demapping the equalized signal or a signal derived from the FBMC signal to obtain a resource demapping signal, and/or symbol demapping the resource demapping signal or a signal derived from the FBMC signal to obtain the payload signal, thereby possibly efficiently processing the FBMC signal into the payload signal.

In a sixth aspect of the invention, a computer program is provided having a program code for performing all the steps according to the fourth or fifth aspect of the invention, when the program is executed on a computer or digital signal processor.

It should be noted that generally all structures, devices, elements, units, means, etc. described in this application can be implemented by software or hardware elements or any combination of both. Furthermore, the apparatus may be or may comprise a processor, wherein the functions of these elements, units and means described in the present application may be implemented in one or more processors. All steps performed by the various entities described in the present application, as well as the functions described as being performed by the various entities, are intended to illustrate that the various entities are adapted or configured to perform the respective steps and functions. In the following description or specific embodiments, although specific functions or steps performed by the general-purpose entity are not reflected in the description of specific detailed elements of the entity performing the specific steps or functions, it will be apparent to those skilled in the art that these methods and functions may be implemented by software or hardware elements or any combination of both.

Drawings

The invention will be described in detail below with reference to the drawings and embodiments thereof, wherein

Fig. 1 shows a first embodiment of a transmitting device according to a first aspect;

fig. 2 shows a first embodiment of a receiving device according to a second aspect;

FIG. 3 illustrates a first exemplary transmitting device;

FIG. 4 illustrates a second exemplary transmitting device;

FIG. 5 illustrates a third exemplary transmitting device;

fig. 6 shows a second embodiment of the transmitting device according to the first aspect;

fig. 7 shows a second embodiment of a receiving device according to the second aspect;

fig. 8 shows a third embodiment of a transmitting device according to the first aspect;

fig. 9 shows a third embodiment of a receiving device according to the third aspect;

figure 10 shows two resource blocks for embodiments of the first, second, third, fourth, fifth and sixth aspects;

fig. 11 shows a diagram of a frequency spectrum for an exemplary transmission system;

fig. 12 shows a diagram of frequency spectra for embodiments of the first, second, third, fourth, fifth and sixth aspects;

fig. 13 shows a detail of a fourth embodiment of the first aspect;

FIG. 14 shows a graph depicting impulse response;

figure 15 shows a detail of a fourth embodiment of the second aspect;

FIG. 16 shows a detail of a fifth embodiment of the second aspect;

figure 17 shows a detail of a fifth embodiment of the second aspect;

FIG. 18 shows the spectral efficiency of embodiments of the first, second, third, fourth, fifth and sixth aspects relative to an alternative;

figure 19 shows the spectral efficiency of embodiments of the first, second, third, fourth, fifth and sixth aspects relative to an alternative;

figure 20 shows the spectral efficiency of embodiments of the first, second, third, fourth, fifth and sixth aspects relative to an alternative;

fig. 21 shows a sixth embodiment of the first aspect;

fig. 22 shows a seventh embodiment of the first aspect;

FIG. 23 shows a flow chart of an embodiment of the fourth aspect; and

fig. 24 shows a flow chart of an embodiment of the fifth aspect.

Detailed Description

First, a method for processing inter-block interference in the prior art is described with reference to fig. 3 to 5. Several embodiments of the transmitting device and the receiving device of the present invention are shown using fig. 1 to 2 and fig. 6 to 9. According to fig. 10 to 20, details of some embodiments are described. The achievable performance is shown with fig. 19 to 20. With fig. 21 to 22, an alternative embodiment is described. Finally, embodiments of the inventive transmission method and reception method are shown in accordance with fig. 23 and 24. The same entities and reference numerals in different figures have been partly omitted.

As shown in fig. 3, for channel precoded downlink transmission with two

different user equipments

34, 35, it is difficult to acquire accurate channel information in real time to adapt to the precoder. The only possible solution is to avoid mutual interference between user blocks 30 and 31 by making at least one boundary subcarrier sc0 empty, also referred to as "subcarrier backoff". The established user blocks are passed to two different beam forming units 32, 33, respectively, and transmitted over channels h1, h 2. The scheme is also suitable for uplink multi-user transmission because it is impossible to obtain the channel information of other users in advance or in real time or know the channel information of other users by using the precoder.

As shown in fig. 4, for the case of downlink channel precoding, one approach is to use a precoder 44 for canceling interference between two consecutive user blocks 40, 41. The precoder structure relies on real-time channel information between the two downlink user channels h1 and h 2. Before precoding, each signal passes through a

beamformer

42, 43, respectively. In this scheme, interference cannot be effectively removed since the a priori information of channels h1 and h2 is inaccurate at the transmitter. Therefore, the performance of this solution is poor.

As shown in fig. 5, for downlink channel precoded transmission, one scheme uses QAM modulation with a cyclic prefix dedicated only to the boundary subcarriers of the user blocks 50, 51 that are susceptible to inter-block interference. One of the results of using CQMBs is to cause interference to other subcarriers within the same block, also known as intra-block interference. Thus, the

precoders

52, 53 are used at the transmitter to pre-fetch the interference between the CQMB and its neighboring OQAM modulated subcarriers. After passing through the

precoders

52, 53, the signals pass through the

beamformers

54, 55 before being transmitted to two

different user equipments

56, 57 through the channels h1, h2, respectively.

Note that compared to the previously proposed scheme, the

precoder

52, 53 is only associated with the prototype filter and is not limited by channel information. Therefore, the CQMB scheme is robust against inaccurate channel information. Furthermore, QAM modulated symbols in CQMBs may interfere with each other because FBMC has orthogonality only in the real domain. However, such interference is easily cancelled by performing CP cancellation and Frequency Domain Equalization (FDE) at the receiver. The CQMB has a slight loss of spectral efficiency according to the selection of the CP length, compared to the subcarrier backoff scheme. The CQMB scheme is robust against inaccurate channel information at the transmitter side compared to pre-coding interference based pre-cancellation schemes. The CQMB scheme is limited in that complexity of transceiver design increases due to interference cancellation.

Fig. 1 shows a first embodiment of a transmitting device 3 according to the first embodiment. The transmitting device 3 comprises a filtering unit 5. The payload signal 1 is provided to the transmitting device 3. The transmitting device is adapted to generate at least one resource block from a time-frequency resource grid corresponding to the payload signal 1. Each resource block is a specific spectral region for a specific time slot and comprises one spectral middle region and at least one spectral edge region located at a spectral edge of the resource block. The structure of the resource block will be described in more detail when describing fig. 10. The at least one filtering unit 5 is adapted to generate a middle section of each resource block by filtering a first part of a signal derived from the payload signal 1, thereby generating a double sideband modulated first part of the FBMC signal 2. The at least one filtering unit 5 is adapted to generate at least one spectral border-region of each resource block by filtering at least a second part of the signal derived from the payload signal 1, thereby generating a single sideband modulated second part of the FBMC signal 2.

In fig. 2, an embodiment of a receiving device according to the second aspect is provided. The receiving device 4 comprises a filter unit 6. The receiving device 4 is adapted to receive the FBMC signal 2 comprising at least one resource block and to regenerate the payload signal 1 therefrom. The resource block is a specific spectral region for a specific time slot and comprises one spectral middle region comprising the double sideband modulated first part of the FBMC signal and at least one spectral edge region located at a spectral edge of the resource block comprising the single sideband modulated part of the FBMC signal 2. The filtering unit 6 is adapted to filter the double sideband modulated first part of said FBMC signal 2, thereby generating a first part of a signal derived from the FBMC signal 2. The filtering unit 6 is further adapted to filter the single sideband modulated second part of the FBMC signal 2, thereby generating a second part of the signal derived from the FBMC signal 2.

The transmitting device 3 according to fig. 1 and the receiving device 4 according to fig. 2 together form a communication system. In this case, the signal transmitted by the transmitting device 3 is the signal received by the receiving device 4. The payload signal 1 regenerated by the receiving device 4 corresponds to the payload signal 1 which was the input signal of the transmitting device 3.

The theoretical idea behind the proposed invention can be explained as:

instead of applying a double Sideband prototype filter to all subcarriers in the FBMC in order to avoid inter-block interference, we have designed a new Single Sideband (SSB) modulated transmission method only for the boundary subcarriers that are susceptible to the above-mentioned inter-block interference. Such SSB modulated boundary subcarriers are also referred to as SSB-MBs.

To be compatible with the legacy prototype filter, a new resource mapping method is proposed specifically for the boundary subcarriers. In conjunction with the SSB modulated filter, there is neither inter-block interference nor intra-block interference between boundary subcarriers and adjacent subcarriers in the same block. Thus, there is no need to use a precoder at the transmitter to reduce inter-block interference and intra-block interference as compared to earlier proposed schemes.

In fact, the SSB modulated filter is implemented to a finite length. Due to this truncation effect, the Nyquist criterion is not fully met, i.e., applying the SSB-MB scheme may result in residual inter-symbol interference between symbols in the boundary subcarriers. However, frequency domain equalization at the receiver can easily eliminate this interference.

In general, the proposed SSB-MB can be applied either on the transmitter side alone, on the receiver side alone, or on both sides of the communication system.

Fig. 6 shows a further embodiment of the transmitting device 3 according to the first aspect of the present invention. The transmitting device 3 comprises an encoding unit 60, which encoding unit 60 is connected to a resource mapping unit 61, which resource mapping unit 61 is in turn connected to a modulation unit 62 and a layer mapping unit 63. The layer mapping unit 63 is in turn connected to a filtering unit 5 comprising a first filtering unit 65 and a second filtering unit 64.

The payload signal 1 is provided to an encoding unit 60, the encoding unit 60 being adapted to symbol map the payload signal resulting in a symbol mapped payload signal 1 a. Forward Error Correction (FEC) may also be performed here. In this example, PAM modulated symbols are used for FBMC transmission.

The symbol mapped payload signal 1a is then provided to a resource mapping unit 61, the resource mapping unit 61 being adapted to perform a resource mapping on the symbol mapped payload signal resulting in a resource mapped payload signal 1 b. In particular, the payload symbols are mapped together with reference symbols onto a time-frequency resource grid of each transport block. The resource mapping will be described in detail in the description of fig. 10.

The resource mapped payload signal 1b is then provided to a modulation unit 62, the modulation unit 62 being adapted to modulate the resource mapped payload signal 1b resulting in a modulated payload signal 1 c. In particular, the PAM modulated symbols are modulated such that only pure real symbols or pure imaginary symbols are directly adjacent, so that the real domain quadrature condition can be maintained. The PAM modulated symbols in the regular subcarriers are denoted as sc1.. scN, where N is the number of subcarriers in each block, are processed by the modulation unit 62 in the same way as in the conventional FBMC OQAM pre-modulation algorithm, and the SSB-MB symbols in the boundary subcarriers denoted as sc0 may or may not be processed by the unit.

The resulting modulated payload signal 1c is passed to the layer mapping unit 63. If the SSB-MB symbols in the boundary subcarriers are not processed by the modulation unit 62, parts of the resource mapping payload signal 1b are also passed to the layer mapping unit 63. The layer mapping unit 63 is adapted to perform MIMO layer mapping on these signals 1b, 1c resulting in a layer mapped payload signal 1 d. It is to be noted in particular that this layer mapping unit 63 is optional.

Finally, the resulting signal 1d is passed to the filtering unit 5. A first portion of the signal corresponding to the regular sub-carrier sc1.. scN is passed to a first filtering unit 65 and a second portion of the signal corresponding to the SSB-MB symbols in the boundary sub-carrier sc0 is passed to a second filtering unit 64. Specifically, second filtering unit 64 performs special processing to cancel inter-block interference by applying a quadrature filter at the boundary subcarrier, denoted sc 0. The design also ensures that there is no intra-block interference between boundary subcarriers and adjacent subcarriers in the same block. Detailed information on the SSB modulation unit will be explained at the description of fig. 11 to 14. On the other hand, the conventional subcarriers sc1.. scN are further modulated and filtered by the first filtering unit 65, and the resulting signal is the FBMC signal 2.

Fig. 7 depicts an embodiment of the receiving device 3 according to the second aspect. The receiving device 3 comprises a filter unit 6 comprising a first filter unit 71 and a second filter unit 70. The filtering unit 6 is connected to an optional layer demapping unit which is in turn connected to a demodulation unit 72. In this example, the layer demapping unit is not provided. Here, the first filtering unit 71 is directly connected to the demodulating unit 72, the demodulating unit 72 is in turn connected to the equalizer 73, and the second filtering unit 70 bypasses the demodulating unit 72 and is directly connected to the equalizer 73. In this example, the equalizer 73 includes a first equalizer 75 and a second equalizer 74. Furthermore, the equalizer 73 is directly connected to the resource demapping unit 76, and the resource demapping unit 76 is connected to the demodulation unit 77.

The received FBMC signal 2 is provided to a filtering unit 6. A first part of the received FBMC signal corresponding to the conventional subcarrier sc1.. scN is filtered by a first filtering unit 71 resulting in a first part of the signal resulting from the FBMC signal 2 a. Specifically, the FBMC signal is demodulated and matched filtered here and passed into the frequency domain of each subcarrier.

A second part of the FBMC signal 2 is filtered by a second filtering unit 70 resulting in a second part of the signal derived from the FBMC signal 2 a. Here, the signal at boundary subcarrier sc0 is match filtered. The second filtering unit 70 is designed to reduce intra-block interference between boundary subcarriers and adjacent subcarriers in the same block. Details regarding this filtering will be described in the description of fig. 15-17.

The resulting signal from FBMC signal 2a is passed to an optional layer demapping unit, which is not provided here. If a layer demapping unit is provided, it performs MIMO layer demapping on a first part of a signal derived from the FBMC signal and a second part of a signal derived from the FBMC signal, resulting in a first part of a layer demapping signal and a second part of the layer demapping signal.

For the signal obtained by the layer demapping unit or the signal 2a obtained by the filtering unit 6, if there is no layer demapping unit, specifically, the portion of the signal corresponding to the conventional subcarrier sc1.. scN is passed to the demodulation unit 72, and the demodulation unit 72 demodulates to obtain the first portion of the demodulated signal 2 b. Optionally, the second portion of the signal corresponding to conventional subcarrier sc0 may also be demodulated here. In this case, a second part of the demodulated signal 2b is also generated. In this demodulation unit 72, specifically, the post-OQAM modulation part corresponds to the pre-OQAM modulation part, and is configured to convert the symbols in the normal subcarriers sc1.. scN from pure real or pure imaginary back to pure real PAM symbols, and set as an imaginary interference part.

The resulting demodulated signal 2b, or demodulated signal 2b and the signal 2a resulting from the second filtering unit 70, are passed to an equalizer 73. The first equalizer 75 performs a double sideband equalization on the first part of the demodulated signal 2b or the signal derived from the FBMC signal 2a resulting in a first part of the equalized signal 2 c. Specifically, the PAM modulated conventional subcarriers, sc1.. scN, are equalized here. The second equalizer 74 performs a single sideband equalization on the second part of the demodulated signal 2b or the signal derived from the FBMC signal 2a resulting in a second part of the equalized signal 2 c. Specifically, only the SSB-MB symbols are equalized here. Detailed information on this equalization is explained in the description of fig. 15 to 17.

The resulting equalized signal 2c is passed to a resource demapping unit 76, which resource demapping unit 76 is adapted to perform a resource demapping of the equalized signal 2c, resulting in a resource demapped signal 2 d. In particular, symbols in the time-frequency resource grid returning to the transport block are demapped here. This is the reverse operation of the resource mapping unit 61 in fig. 6.

Finally, the resource demapped signal 2d is passed to a decoding unit 77, which decoding unit 77 is adapted to symbol demap the resource demapped signal, resulting in a payload signal 1. In particular, FEC decoding and symbol-to-bit mapping are performed here. This process corresponds to the FEC encoding and bit to symbol mapping performed by the encoding unit 60 in fig. 6.

Fig. 8 and 9 show alternative transceiver designs. The prototype filter for SSB-MB is closely related to the conventional prototype filter for conventional FBMC systems, and with this feature, SSB-MB can be implemented by reusing most of the functional blocks.

Fig. 8 shows an alternative embodiment of the transmitting device according to the first aspect. The main components are the same as described in fig. 6, except that here the filter unit 5 comprises a first filter unit 84 and a second filter unit 85. The entire layer mapped signal 1d is passed to the first filtering unit 84, filtered by the filtering unit 84. Second filter unit 85 then converts the normal Double Sideband (DSB) modulated signal 1c from first filter unit 84 into an SSB modulated signal 1c at boundary subcarrier sc 0. In this embodiment, the entire resource mapping signal 1b is also passed to the modulation unit 82, and the entire resource 1b is modulated by the modulation unit 82 in the same way.

Fig. 9 shows an alternative embodiment of a receiving device according to the second aspect. The main components are the same as described in fig. 8, except that here the filter unit 6 comprises a first filter unit 91 and a second filter unit 90. The second filtering unit 90 processes a first part of the FBMC signal 2 and converts the SSB modulated signal into a DSB modulated signal. The first filter unit 91 then processes the signal generated by the second filter unit 90 and the remaining FBMC signal 2 by demodulation and matched filtering using a conventional prototype filter to obtain a signal derived from the FBMC signal 2 a.

Here, the demodulation unit 92 demodulates the entire filtered FBMC signal 2 a. The resulting signal 2b is passed to an equalizer 93.

The equalizer 93 includes a first equalizer 94 that processes the entire demodulated signal 2b and a second equalizer that processes only the subcarriers corresponding to the boundary block. The second equalizer mitigates residual inter-symbol interference (ISI) due to the application of the SSB-MB with the truncation filter. The design is similar to that of the equalizer 74 of fig. 7. The only difference is that here the second equalizer 95 is aimed at reducing the degradation caused by the effects of channel fading and truncation, whereas the first equalizer 94 focuses on the degradation caused by channel fading, the unit second equalizer 95 handles the degradation caused by the application of SSB-MB.

Fig. 10 shows the structure of resource blocks 100, 101. The resource blocks 100, 101 are part of a time-frequency resource grid. Each

resource block

100, 101 is a particular spectral region for a particular time slot. The resource blocks 100, 101 comprise one spectral

middle region

102, 103 and at least one

spectral edge region

104a, 104b located at a spectral edge of the resource blocks 100, 101, respectively.

The

spectral border regions

104a, 104b of two adjacent resource blocks 100, 101 overlap in spectrum but do not overlap in time axis. This illustrates that the

spectral edge regions

104a, 104b share the combined bandwidth. This is represented in fig. 10 by the continuous black and white regions in the spectral regions labeled 104a, 104 b. On the time axis, although the

spectrum edge regions

104a, 104b of the two adjacent resource blocks 100, 101 do not overlap, the alternation may be performed by using the spectrum. When the edge region 104 is occupied by a white-labeled user, a black-labeled user sends zero padding or no signal at all. Similarly, when the border region 104 is occupied by a black-labeled user, a white-labeled user sends zero padding or no signal at all. Specifically, as shown in the figure, NTTI symbol resources in the SSB subcarriers are alternately allocated to block No. 1 and block No. 2 by symbol. Further, the replacement may be more than one symbol interval. The

middle regions

102, 103 of the spectrum adjacent to the resource blocks 100, 101 are double sideband modulated and the edge regions of the spectrum are single sideband modulated.

It is important to note that the

spectral border regions

104a, 104b do not necessarily include the interlocking structure (interlocking structure) of the payload region and the zero padding region shown above.

Fig. 11 is a filter bank showing the use of a conventional prototype filter on all FBMC subcarriers. Black arrows indicate the boundaries of user blocks. Due to the complex waveform at the boundary, if the channel between two adjacent blocks is not flat, there is inter-block interference.

Fig. 12 shows that the proposed filter bank utilizes SSB-MB on boundary subcarriers, while using the conventional prototype filter on conventional subcarriers. In the boundary subcarrier, symbols belonging to block No. 1 use a Lower Sideband (LSB), and symbols belonging to block No. 2 use an Upper Sideband (USB). LSB and USB are orthogonal to each other. Therefore, to reduce inter-block interference, SSB-MB constructs a filter bank that is orthogonal in the real domain at the boundary of two neighboring blocks. In addition, to avoid intra-block interference, filters constructed at boundary subcarriers also implement real domain orthogonality with adjacent subcarriers within the same block.

FIG. 13 shows a diagram for constructing SSB-MB. In particular, the odd symbols on boundary subcarrier sc0 belong to block number 1, using a Lower Sideband (LSB) filter p_LSB(t) the mixture is modulated. The even symbols on the boundary subcarrier sc0 belong to block number 1, using an Upper Sideband (USB) filter P_USB(t) the mixture is modulated. scN all other subcarriers use the conventional prototype filter p used in FBMC systems_i(t) modulation is performed, where i is the index of the subcarrier.

The generic expression for the prototype filter on the transmitter side for SSB-MB is:

wherein

Represents p_i(t) Hilbert conversion. p is a radical of_LSB(t) or (p)_USB(t)) and p_iThe relationship between (t) is exemplified in fig. 14. It shows a prototype filter p_USBImpulse response of (t): p is a radical of_USBThe real part of (t) is the conventional prototype filter p_i(t)，p_USBThe imaginary part of (t) is p_i(t) the imaginary part of the hubert transform.

By ensuring that the filters are designed orthogonally, i.e., complex domain orthogonality is supported between different blocks, and real domain orthogonality within each block is preserved, the structure of the SSB-MB produces neither inter-block nor intra-block interference.

However, since a finite length filter is used, the self-quadrature distortion caused by the actual implementation of the LSB or USB is small, and therefore, causes marginal intersymbol interference on the boundary subcarrier sc 0. Such interference can be easily eliminated at the receiver side by using an equalizer.

Detailed analysis of orthogonality is as follows:

1) the LSBs in boundary subcarrier sc0 are orthogonal to the complex field of the USB filter:

adjusting the real value g (t) and its Hilbert transform H_gThe orthogonal property of (t), i.e.<g(t),H_g(t)>0, LSB and USB filters remain in quadrature, i.e.

<p_LSB(t),p_USB(t)>

＝{<H_PT(t)(t),p_T(t)>+<p_T(t),H_PT(t)(t)>+j(<p_T(t),p_T(t)>-<H_PT(t),H_PT(t)(t)>)}＝0

Therefore, at the boundary subcarrier, the LSB and the USB are orthogonal to each other to ensure no inter-block interference.

2) Real number domain orthogonality between boundary subcarriers and their neighboring subcarriers in the same block:

first, the orthogonality of the LSBs at the boundary subcarrier (sc0) with the prototype filter at the adjacent subcarrier (sc1) in the first block is as follows:

<p_<SB(t),p_T(t)e^j2πΔft>R

＝R{<H_PJ(r)(t),p_T(t)>e^-j2πΔft+j<p_T(t),p_T(t)>e^-j2πΔft}

＝0

where Δ f is the sampling interval in frequency. The above equation applies to the hubert transfer function and the real-domain quadrature property of the prototype filter in the FBMC system.

Second, the orthogonality of the USB at the boundary subcarrier (sc0) in the second block to the prototype filter at the adjacent subcarrier can be similarly derived.

Therefore, the filters in the boundary subcarriers are orthogonal to their neighboring subcarriers, respectively, to ensure that there is no intra-block interference.

3) The real-number domain orthogonality of the LSB or USB filter in the LSB or boundary subcarrier sc0 and its implementation issues:

maintaining the orthogonality of the LSB (or USB) filter, i.e., using the Hilbert transform and the real-field orthogonality properties of prototype filters in conventional FBMC systems

<p_LSB(t),p_LSB(t)>_R

＝R{<H_PT(t)(t),H_PT(t)(t)+p_T(t),p_T(t)>}＝2δ(t)

Similarly, the case of a USB filter can be derived.

Therefore, with an infinite length filter at the boundary subcarrier, the LSB or USB is orthogonal to ensure there is no intersymbol orthogonality.

However, only a finite length filter can be implemented in reality. Such practical limitations cause slight non-orthogonality of the LSB or USB filters. Therefore, there is little intersymbol interference. This interference can be easily reduced at the receiver side by an equalizer, as will be explained in more detail in the description of fig. 16.

Fig. 15 shows an overview of SSB demodulation at the boundary subcarrier sc 0. In particular, the symbols received at boundary subcarrier sc0 are passed through a matched filter

And

the recovered symbols are generated at odd and even positions, respectively. Reference numerals

And

respectively represent p given in FIG. 13_LSB(t) and p_USB(t) a matched filter. All other subcarriers sc1.. scN utilize the conventional prototype filter p used in FBMC systems_i(t) demodulating, where i is the index of the subcarrier.

Fig. 16 shows details of the equalization of SSB symbols by the equalizers in fig. 7 and 9. In particular, details of the equalizer 74 of fig. 7 are shown. A serial-to-parallel converter (serial-to-parallel-converter)160 is connected to a digital fourier transform unit 161, and the digital fourier transform unit 161 is connected to a frequency domain equalizer 162 including a first partial frequency domain equalizer 163 and a second partial frequency domain equalizer 164. The digital fourier transform unit 161 is connected to a first partial frequency domain equalizer 163 which is connected to a second partial frequency domain equalizer 164. The second partial frequency-domain equalizer 164 is further connected to an inverse digital fourier transform unit 165, and the inverse digital fourier transform unit 165 is further connected to a parallel-to-serial converter 166.

Serial to parallel converter 160 is adapted to arrange the complex symbols after SSB demodulation from serial order to parallel order. The symbols may be both in the odd-numbered positions of the SSB band or both in the even-numbered positions of the SSB band. The digital fourier transform unit 161 then converts the signal into the frequency domain. The DFT size is the same as the body payload symbol length. The frequency domain equalizer 162 then performs frequency domain equalization to reduce residual intersymbol interference from the filter bank. By multiplication of data by H^* _eqThe vectors are equalized, where H_eqIs the equivalent channel response in the frequency domain, (.)^*Is a complex conjugate. Specifically, first, the first partial frequency domain equalizer 163 multiplies the signal by 1/H^* _fb-eqThe resulting signal is then multiplied by W by a second partial frequency domain equalizer 164^* _ch-eq。

The equivalent channel response is shown in fig. 17, where

And

receiver filters and transmitter filters that are SSB subcarriers (sc0) that may be greater than one symbol in length (e.g., 8M in length)_FFT). FFT size is represented by M_FFTGiven a channel impulse response of L_ch. In this case, the channel impulse response is much smaller than the transmitter (receiver) filter length, and the equivalent channel in the time domain can be abbreviated as:

wherein h is₀Is the channel gain of SSB subcarrier sc0 and the DFT (.) is a DFT operation.

Is an intrinsic filter bank response that relies only on the prototype filter for SSB modulation and demodulation. For example, the coefficients thereof may be predetermined and stored in a look-up table.

For the case of PHYDYAS with a DFT size of 14 for the SSB bands,

the coefficients of (a) are shown in the following table:

coefficient of (2)

Continuing with fig. 16, after frequency domain equalization, the signal is converted to the time domain by inverse digital fourier transform 165 and reordered into a serial signal by parallel-to-serial converter 166.

To evaluate the above-described scheme, computer simulations were performed based on the simulation parameters given in the following table.

Simulation parameters

FFT size M_FFT	512
		Prototype filter	PHYDYAS 4M in length_FFT
Symbol per subcarrier	14
		Per TBS subcarrier	36
TBS per TTI	2
		Modulation	MCS9,MCS16,MCS25

Fig. 18 shows the spectral efficiency of the above-described transmitting apparatus and receiving apparatus. It is readily seen that the spectral efficiency of this scheme is significantly higher than the subcarrier backoff scheme described earlier, but depends on the number of subcarriers allocated to each user. If the number of subcarriers per (user) block is small, the gain can be as high as 50%.

Fig. 19 and 20 show the block error rate BLER and snr (db) for the 3GPP SCME urban micro scenario and the urban macro scenario. For comparison, the results of three reference schemes are also shown: OFDM (LTE/LTE-evolution), NoIBI (one subcarrier backoff), and IBI (no subcarrier backoff, and therefore inter-block interference). Especially in high SNR regions, the proposed scheme can effectively reduce inter-block interference with high modulation and coding schemes.

Fig. 21 shows a further embodiment of the transmitting device. This applies here to the case of downlink MIMO precoding. The first resource block 210 and the second resource block 211 each have an edge region, and together constitute a shared boundary subcarrier sc 0. The respective beamformers 212 and 213 perform beamforming on the obtained signals. The

user equipment

214, 215, e.g. a mobile handset, then sends and receives these signals over the channels h1, h 2. Thus, inter-block interference between users number 1 and number 2 can be avoided successively by using this scheme.

As another example, fig. 22 illustrates an embodiment of a transmitting device adapted for an uplink multiple access scenario. Here, the first resource block 220 and the second resource block 221 also have edge regions, respectively, and together constitute a shared boundary subcarrier sc 0. Different users # 1 and # 2 transmit the resulting signals to the base station 222 over channels h1, h 2. Thus, inter-block interference between users number 1 and number 2 can be avoided successively by using this scheme.

Furthermore, the communication system utilizes frequency domain multiple access, as long as the signal is OQAM modulated and for different users (blocks), which is applicable to alternative transmissions from FBMC and different prototype filters (except for PHYDYAS filters).

Fig. 23 shows an embodiment of a transmission method according to the fourth aspect. The purpose of the transmission method is to generate an FBMC signal 2 from a payload signal 1. In a first step 230, at least one resource block comprising at least one spectral edge region and at least one spectral middle region is generated from the payload signal. In a second step 231, the content of the spectral middle region of the resource block is generated by filtering a first part of the signal derived from the payload signal 1, thereby generating a double sideband modulated first part of the FBMC signal 2. In a third step 232, the content of the spectral border-regions of the resource block is generated by filtering a second part of the signal derived from the payload signal, thereby generating a single sideband modulated second part of the FBMC signal 2.

Fig. 24 shows an embodiment of the receiving method according to the fifth aspect. The purpose of the receiving method is to regenerate the payload signal 1 from the transmitted FBMC signal 2. In a first step 240, the double sideband modulated first portion of the FBMC signal is filtered, thereby generating a first portion of the signal derived from FBMC signal 2. In a second step 241, the single sideband modulated second part of the FBMC signal is filtered, thereby generating a second part of the signal derived from the FBMC signal 2. In a final third step 242, the payload signal 1 is regenerated from the signal derived from the FBMC signal 2.

Since the method is closely associated with the device, reference may be made to further details regarding embodiments of the transmitting device.

The invention is not limited to the examples shown, and the features of the exemplary embodiments may be used in any advantageous combination.

The invention has been described herein in connection with various embodiments. However, other variations to the disclosed embodiments can be understood and effected by those skilled in the art in practicing the claimed invention, from a study of the drawings, the disclosure, and the appended claims. Throughout this specification the word "comprising" does not exclude other elements or steps, and the indefinite article "a" or "an" does not exclude a plurality. A single processor or other unit may fulfill the functions of several items recited in the embodiments of the present application. Some measures are usually described in different embodiments, but this does not indicate that these measures cannot be combined advantageously. A computer program may be stored/distributed on a suitable medium, such as an optical storage medium or a solid-state medium supplied together with or as part of other hardware, but may also be distributed in other forms, such as via the internet or other wired or wireless telecommunication systems.

Claims

1. Transmission apparatus (3) for generating a filterbank multicarrier FBMC signal (2) from a payload signal (1), the transmission apparatus comprising at least one filtering unit (5),

wherein the transmitting device (3) is adapted to generate at least one resource block (100, 101, 210, 211, 220, 221) from a time-frequency resource grid corresponding to the payload signal (1), wherein each resource block (100, 101, 210, 211, 220, 221) is a specific spectral region for a specific time slot and comprises one spectral middle region (102, 103) and at least one spectral edge region (104a, 104b) located at a spectral edge of the resource block (100, 101, 210, 211, 220, 221),

wherein the at least one filtering unit (5) is adapted to generate the spectral mid-region (102, 103) of each resource block (100, 101, 210, 211, 220, 221) by filtering a first part of a signal (1d) derived from the payload signal (1), thereby generating a double sideband modulated first part of the FBMC signal (2),

wherein the at least one filtering unit (5) is adapted to generate the at least one spectral edge region (104a, 104b) of each resource block (100, 101, 210, 211, 220, 221) by filtering at least a second part of the signal (1d) derived from the payload signal (1), thereby generating a single sideband modulated second part of the FBMC signal (2).

2. The transmitting device (3) as defined in claim 1, wherein the single sideband modulated second part of the FBMC signal (2) comprises:

-a spectral cut-off edge corresponding to a starting edge of the base band signal of the bottom layer,

-a non-cut-off edge,

wherein the at least one filtering unit (5) is adapted to generate the at least one payload region of the spectral border region (104a, 104b) such that

-the non-cut-off edge of the second part of the FBMC signal (2) is on a spectral middle region (102, 103) on the side of the spectral edge region (104a, 104b), and

-the cut-off edge of the second part of the FBMC signal (2) is on a non-spectral middle region (102, 103) on the side of the spectral border region (104a, 104 b).

3. The transmitting device (3) according to claim 1 or 2,

wherein the double sideband modulated first part of the FBMC signal (2) of the spectral middle region (102, 103) is spectrally partially overlapping with the single sideband modulated second part of the FBMC signal (2) of the spectral edge region (104a, 104b), and

wherein the single sideband modulated second part of the FBMC signal (2) does not exceed signal components of the spectral edges of the spectral edge regions opposite the spectral middle regions (102, 103).

4. The transmitting device (3) according to claim 1 or 2,

wherein each spectral edge region (104a, 104b) comprises:

-at least one payload section comprising said second part of said FBMC signal (2), and/or

-at least one zero-filled segment comprising at least one zero-filled or no-signal, and

wherein, if at least one payload segment and at least one zero padding segment are both included within the edge region of the spectrum, the at least one payload segment and the at least one zero padding segment have the same duration and are arranged consecutively in time.

5. The transmitting device (3) as defined in claim 4, wherein each spectral border section (104a, 104b) comprises:

at least two payload sections, and/or

At least two zero-padding segments, and

wherein, if at least two payload segments and at least two zero-padding segments are both comprised within a spectrum border region, the at least two payload segments and the at least two zero-padding segments are temporally alternately arranged within the spectrum border region (104a, 104 b).

6. The transmitting device (3) according to claim 1, 2 or 5, wherein the transmitting device (3) further comprises:

-an encoding unit (60) adapted to symbol map said payload signal (1) resulting in a symbol mapped payload signal (1a), and/or

-a resource mapping unit (61) adapted to resource map the symbol mapped payload signal (1a) or a signal (1a) derived from the payload signal (1) resulting in a resource mapped payload signal (1b), and/or

-a modulation unit (62, 82) adapted to modulate the resource mapped payload signal (1b) or a signal (1b) derived from the payload signal (1) resulting in a modulated payload signal (1c), and/or

-a layer mapping unit (63) adapted for MIMO layer mapping of the modulated payload signal (1c) or a signal (1c) derived from the payload signal (1) resulting in a layer mapped payload signal (1 d).

7. A receiving device (4) for receiving a payload signal (1) according to a filter bank multi-carrier, FBMC, signal (2) comprising at least one resource block (100, 101, 210, 211, 220, 221), the receiving device comprising at least one filtering unit (6),

wherein resource blocks (100, 101, 210, 211, 220, 221) are specific spectral regions for specific time slots, and each resource block (100, 101, 210, 211, 220, 221) comprises a spectral middle region (102, 103) comprising a double sideband modulated first part of the FBMC signal (2), and

at least one spectral edge region (104a, 104b) located at a spectral edge of each resource block (100, 101, 210, 211, 220, 221) comprising a single sideband modulated second part of the FBMC signal (2),

wherein the at least one filtering unit (6) is adapted to filter the double sideband modulated first part of the FBMC signal (2) thereby generating a first part of a signal (2a) derived from the FBMC signal (2), and

wherein the at least one filtering unit (6) is adapted to filter the single sideband modulated second part of the FBMC signal (2) thereby generating a second part of the signal (2a) derived from the FBMC signal (2).

8. Receiving device (4) according to claim 7, wherein the double sideband modulated first part of the FBMC signal (2) of the spectral middle section (102, 103) spectrally partially overlaps with the single sideband modulated second part of the FBMC signal (2) of the spectral edge section (104a, 104b), and

wherein the single sideband modulated second part of the FBMC signal (2) does not exceed signal components of the spectral edges of the spectral edge regions (104a, 104b) opposite the spectral middle regions (102, 103).

9. The receiving device (4) according to claim 7 or 8, wherein each spectral border section (104a, 104b) comprises:

10. The receiving device (4) according to claim 9, wherein each spectral border section (104a, 104b) comprises:

at least two payload sections, and/or

At least two zero-padding segments, and

11. The receiving device (4) according to claim 7, 8 or 10, wherein the receiving device (4) comprises:

-a layer demapping unit adapted for MIMO layer demapping said first part of a signal (2a) derived from said FBMC signal (2) and a second part of said signal (2a) derived from said FBMC signal (2), resulting in a first part of a layer demapping signal and a second part of said layer demapping signal, and/or

-a demodulation unit (72, 92) adapted to demodulate the first part of the layer demapping signal, the second part of the layer demapping signal or a signal (2a) derived from the FBMC signal (2), resulting in a first part of a demodulated signal (2b) and a second part of the demodulated signal (2b), and/or

-an equalizer (73, 94) adapted to perform a double sideband equalization on the first part of the demodulated signal (2b) or a signal (2b) derived from the FBMC signal (2) resulting in a first part of an equalized signal (2c), and/or to perform a single sideband equalization on the second part of the demodulated signal (2b) or a signal (2b) derived from the FBMC signal (2) resulting in a second part of the equalized signal (2c), and/or

-a resource demapping unit (76) adapted to resource demapp the equalized signal (2c) or a signal (2c) derived from the FBMC signal (2) resulting in a resource demapped signal (2d), and/or

-a decoding unit (77) adapted to symbol demap the resource demapping signal (2d) or a signal (2d) derived from the FBMC signal (2) resulting in the payload signal (1).

12. A communication system comprising a first transmitting device (3) according to any of claims 1 to 6, a second transmitting device (3) according to any of claims 1 to 6, and a receiving device (4) according to any of claims 7 to 11,

wherein the first transmitting device (3) is adapted to transmit a first payload signal (1) comprising a first resource block (100), the first resource block (100) comprising a first spectrum border region (104a),

wherein the second transmitting device (3) is adapted to transmit a second payload signal comprising a second resource block (101), the second resource block (101) comprising a second spectrum border region (104b),

wherein the first transmitting device (3) and the second transmitting device (3) are adapted to simultaneously transmit the first resource block (100) and the second resource block (101) spectrally adjacent, and

transmitting the spectral border sections (104a, 104b) of the first resource block (100) and the second resource block (101) on the same frequency, wherein at least one payload segment of the first spectral border section (104a) overlaps with at least one zero-padding segment of the second spectral border section (104b) and at least one payload segment of the second spectral border section (104b) overlaps with at least one zero-padding segment of the first spectral border section (104a),

wherein the receiving device (4) is adapted to receive the first resource block (100) and the second resource block (101) and to regenerate the first payload signal (1) and the second payload signal therefrom.

13. A method for generating a filter bank multi-carrier, FBMC, signal (2) from a payload signal (1), comprising the steps of:

-generating (230) at least one resource block (100, 101, 210, 211, 220, 221) from a time-frequency resource grid corresponding to the payload signal (1), wherein each resource block (100, 101, 210, 211, 220, 221) is a specific spectral region for a specific time slot and comprises one spectral middle region (102, 103) and at least one spectral edge region (104a, 104b) located at a spectral edge of the resource block (100, 101, 210, 211, 220, 221),

-filtering (231) a first part of a signal derived from the payload signal (1) to generate a double sideband modulated first part of the FBMC signal (2) to generate the spectral mid-region (102, 103) of each resource block (100, 101, 210, 211, 220, 221), and

-filtering (232) a second part of the signal derived from the payload signal (1) to generate a single sideband modulated second part of the FBMC signal (2), thereby generating the at least one spectral edge region (104a, 104b) of each resource block (100, 101, 210, 211, 220, 221).

14. A method for receiving a payload signal (1) in accordance with a filter bank multi-carrier, FBMC, signal (2) comprising at least one resource block (100, 101, 210, 211, 220, 221), wherein a resource block (100, 101, 210, 211, 220, 221) is a specific spectral region for a specific time slot, each resource block (100, 101, 210, 211, 220, 221) comprising:

-a spectral middle region (102, 103) comprising a double sideband modulated first part of said FBMC signal (2), and

-at least one spectral border section (104a, 104b) located at a spectral border of each resource block (100, 101, 210, 211, 220, 221), wherein the at least one spectral border section (104a, 104b) comprises a single sideband modulated second part of the FBMC signal (2),

wherein the method comprises the steps of:

-filtering (240) the double sideband modulated first part of the FBMC signal (2) thereby generating a first part of a signal derived from the FBMC signal (2),

-filtering (241) the single sideband modulated second part of the FBMC signal (2) thereby generating a second part of the signal derived from the FBMC signal (2), and

-regenerating (242) the payload signal (1) of the signal derived from the FBMC signal (2).

15. A computer-readable storage medium, having stored thereon a computer program or instructions, which, when read and executed by a computer, causes the computer to perform the method of claim 13 or 14.