CN1065688C - Unipolar series resonant converter - Google Patents
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- CN1065688C CN1065688C CN95102223A CN95102223A CN1065688C CN 1065688 C CN1065688 C CN 1065688C CN 95102223 A CN95102223 A CN 95102223A CN 95102223 A CN95102223 A CN 95102223A CN 1065688 C CN1065688 C CN 1065688C
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Abstract
The present invention relates to a high-efficiency static series resonant converter for converting power between two AC and/or DC circuits and a method thereof. The high-efficiency static series resonant converter comprises a resonant circuit, a blocking switch and a damped inductor, wherein the resonant circuit is connected with a chain current synthesizer for generating a serial of single-electrode chain current pulses with the duration time sections of a controllable zero current and a non-zero current; the blocking switch enables the oscillation of the resonant circuit to be stopped when each chain current pulse is started, and then, the damped inductor is used for clamping. Each chain current pulse is switched off by resonance oscillation from natural commutation to be ended. Actually, the chain current pulses are square waves and have high duty cycle, which causes that a peak current value is reduced to the minimum. By conversion in actual zero voltages and zero currents, the conversion loss is reduced to the minimum.
Description
The present invention relates to a kind of power inverter and a kind of in the method for positive energy exchange and transform power between utility network and the load for example between two power circuit, particularly relate to a kind of Unipolar series resonant converter, be used for direct current (DC) being provided or exchanging (AC) power output by exchanging (AC) or direct current (DC) power supply in high-power many kilowatts system.
Usually, converter is used for electric loading is connected with power supply.For example, the same Uninterrupted Power Supply of converter, arc furnace and induction motor drive unit use together.At work, converter and load generation meeting thereof cause harmful harmonic current of due to voltage spikes on the net in electric utility.These spikes can damage the equipment of other users of received power from this electrical network.The due to voltage spikes that computer is subjected to being produced by these harmonic currents especially easily damages.
Usually using filter between utility network and the converter and between converter and the load, but filter is very expensive, all very high at primitive apparatus and operating cost.For example, one five horsepowers induction motor is spent 150 dollars, and converter is spent 2000 dollars, and filter will be spent 1000 dollars.Like this, engineers is devoted to improve the design of converter to reduce the original cost of induction motor drive unit.In various patents and publication, disclosed various early stage controlled resonant converters, Mohan for example, what Undeland and Robbins showed: power electronics: converter, use and design (John Wiley ﹠amp; Sons, 1989), the 154-200 page or leaf.
Generally, traditional controlled resonant converter has at least by the i.e. input and output switching device that links together of " resonance " circuit of a resonant circuit.Usually connect the input and output switching device with filter.Switching device is many group semiconductor switch devices, for example (order of Zeng Jiaing is listed at cost), diode, thyristor, door auxiliary cutoff thyristor (GATT), gate level turn-off thyristor (GTO) insulated gate bipolar transistor (IGBT) and mos field effect transistor (MOSFET).
The resonant circuit of traditional controlled resonant converter helps to reach so-called " soft switch ".In carrying out soft switch, semiconductor is called " Zero Current Switch " with zero current in fact and (ZCS) carries out switch, or is called " zero voltage switch " with no-voltage in fact and (ZVS) carries out switch, or carries out switch with the combination of ZCS and ZVS.As a result, the switching loss that is produced in soft switch is lower than traditional " firmly " switching circuit, and this low switch loss helps high-speed switch (approximately 20KHz is relative with 1 kilo hertz with hard switching).Like this, in controlled resonant converter, obtained higher switching frequency.
The controlled resonant converter that can carry out high-frequency soft switch is normally used for making in the input and output of the converter voltage and current Harmonic Waves distortion minimum on both.High-frequency soft switch also can be saved the low-order harmonic filter of huge costliness.Thereby the magnetic relevant with the power electronics conversion process of energy and the size and the weight of static parts have also reduced.
At the low side of power bracket, for example several hectowatts or still less have a variety of harmonic converters.But in high-power many kilowatts application, on the circuit layout of device and complexity, have only selection seldom to adopt for converter design person.Thereby designing can be very difficult with the low cost high power converter of high conversion efficiency work.
There are two class high power resonant vibration converters to prove success, particularly:
1 series resonant converter and
2 parallel resonance converters
This combination of two kinds is also recommended.The basic difference of these two kinds of converters is power is transferred to load by converter modes.For the parallel resonance converter, the resonant capacitor in several resonant circuits of load end is in parallel.For the humorous parallel operation of series connection, load end is in series with the resonant circuit capacitor.In the serial or parallel connection controlled resonant converter, load both can also can be by switch and other memory element with the direct connection of resonant capacitor and had been connected indirectly.
On the imagination, resonant circuit is as a chain between the input and output of converter.The control resonant circuit is with generation-series of pulses, and this pulse can be pulse and a periodic width constant or that change.The fundamental frequency of these pulses is referred to herein as " chain frequency ", is selected as being higher than the frequency of input and output voltage or electric current.Converter receives input power with an incoming frequency, and input power is converted to a row pulse, is called " chain power " at this.This chain power is changed then once more, to obtain to have the power output of a selecteed output frequency.Both can be DC power (that is, having the electric current of zero frequency and the power of voltage) for input power, power output or its.
The various layouts of early stage controlled resonant converter are used various semiconductors.The semiconductor of least cost is the controlled rectifier that strengthens, and is also referred to as thyristor.Thyristor just just is used to controlled resonant converter when two conditions of work of needs, that is, if;
1, the electric current that flows through device is turn-offed by natural commutation;
2, device is subjected to enough reverses biased under enough duration (turn-off time).
If the chain frequency is so high so that the device turn-off time causes the unacceptable duty factor of chain curtage pulse, then thyristor is unsuitable for the high power resonant vibration converter.Yet present thyristor has the upper frequency limit above audiorange (about 20KHz), and two above-mentioned if desired these thyristors of condition of work also can be used for very powerful application.If these two conditions also are not gratifying, just must use more expensive controlled stopcock, for example GTO, power MOSFET T and IGBT.Different with the thyristor that has only a controlled turn-on time, GTO, MOSFET and IGBT have controlled connection and controlled turn-off time, by simply applying and the gate drive signals of going to disappear triggers.
In the parallel resonance converter, the chain spike train is made up of one pole (or unidirectional) potential pulse usually, and the controlled stopcock that need turn-off with zero switching voltage usually.In United States Patent (USP)s in 1989 4,864,483, Divan has described the example of this parallel resonance converter.
In series resonant converter, the chain spike train is made up of AC or one pole (unidirectional) current impulse.The existing series resonant converter of several use AC chain current impulse is disclosed by following United States Patent (USP):
3，953，779?Schwarz(1976)
4，096，557?Schwarz(1978)
4，495，555?Eikelboom(1985)
People (1985) such as 4,523,269 Baker
4，648，017?Nerone(1987)
People (1987) such as 4,679,129 Sakakibara
4，695，933?Nguyen(1987)
4，727，469?Kammiller(1988)
4，853，832?Stuart(1989)
Because the chain pulse is to make the current impulse of thyristor with zero-current switching, operating characteristic claims " natural commutation ", does not then need more expensive controlled stopcock (for example, GTO, IGBT).In order to allow flowing of these AC chain current impulses, the input and output device all must be made up of bidirectional switch, for example, and two thyristors that reverse parallel connection connects.For example, the series resonant converter of this three-phase AC input and output that are designed to feed back has the switch element of 12 pairs of reverse parallel connections.As United States Patent (USP) 5,010,471 is described, by the improvement project that Klaassens and Lauw invented.Roughly double by means of the peak value of handle by the AC chain electric current of existing series resonant converter, Klaassens and Lauw replace the full-bridge form of input and output switching device with the half-bridge form.The Klaassens/Lauw converter only need have half of switch element number of full-bridge series resonance converter now as a result, and does not consider that bidirectional switch still is the right single-way switch of reverse parallel connection.
Because the series resonant converter with the current impulse of AC chain uses bilateral switching element, or the right unidirectional switch elements of reverse parallel connection, the saturable reactor series connection embeds each switch.This saturable reactor has avoided the known dv/dt of thyristor to lead interference, that is, by positive pole to the excessive rate of change of cathode voltage and the thyristor of the non-scheduled time that causes lead.A large amount of saturable reactors and common capacitive damper in parallel, the both has improved cost, size and the volume of converter.And then, the switch element that these saturable reactors force the designer to use to have the reverse blocking voltage capability.The designer also must bring up to the turn-off time that sets above the manufactory by thyristor to the minimum duration of the space section of chain current impulse.Another shortcoming is, the loss that is produced when the leading of switch element.Because the voltage when electric current begins to flow through switch element on the switch element is non-vanishing, will produce these and lead loss.
At United States Patent (USP) 4,942, recommended the DC chain series resonant converter of a kind of use one pole (unidirectional) chain current impulse rather than the current impulse of AC chain among 511 (Lipo and the Murai).This Lipo/Murai converter provides a bias current for the resonance current pulse.Because the chain electric current is an one pole, just only need unidirectional switch elements.Like this, as Klaassens/Lauw half bridge series resonance converter, the Lipo/Murai converter only need have half of the required unidirectional switch elements quantity of series resonant converter now.
In the Lipo/Murai converter, even each pulse period of chain electric current gets back to zero, the thyristor of unidirectional switch elements can not be subjected to constant reverse biased yet.This situation forces thyristor to remain on the zero current under the duration of the turn-off time of being longer than manufactory's setting.Like this, the Lipo/Murai converter has just been upset the second above-mentioned thyristor working condition (2).As a result, when with existing series resonant converter (having the pulse period width that equates and mean value on the whole pulse period), the Lipo/Murai converter must produce the chain current impulse that has high peaks.Another selection as the Lipo/Murai converter is to use more expensive controlled stopcock element, rather than thyristor.
Although soft switch series resonant converter has more performance than the converter that uses the hard switching circuit, exist extremely difficult improvement to need for the series resonant converter technology.For example, one of factor of the business success of obstruction series resonant converter is that the chain current impulse must have high peak value, according to the type of the series resonant converter that uses, the peak value of chain current impulse can reach three to nine times of peak value of the maximum output current that load allows.
The phenomenon of this high chain current impulse peak value is to cross the sinusoid current impulse that resonance produced of resonant circuit and cause owing to using all-pass.Submit to by Murai, Nakamra, Lipo and Aydemir in the article " Pulse-split Cencept in Series Resonant DC Link PowerConversion for Induction Motor Drives " of 1991 commercial Application society conference (Industrial Application Society Meeting) and recommended a solution.United States Patent (USP) 4,942,511 as them is described, and Lipo and Murai attempt to improve converter circuit by the waveform of revising the chain current impulse.The Lipo/Murai converter uses a saturable reactor that has a bias current to limit the peak value of resonance current pulse.Yet the Lipo/Marai converter still can make the thyristor that will work to the second above-mentioned situation generation phase mutual interference, that is, thyristor be not applied in enough reverses biased in the duration fully.As a result, the use of thyristor that is used for the converter of Lipo/Murai still can cause the excessive rate of the peak value and the mean value of chain current impulse.Because the chain electric current is still too high, because of the price of converter is directly proportional with the chain current value, then the Lipo/Murai converter is very expensive.
The United States Patent (USP) 4,477,868 of Steigerwald discloses the series resonant converter of another kind of type, can be the peak-limitation of chain current impulse on suitable value.But the Steigerwald converter it so happened that is limited to non-feedback application, and can only DC input and output power.The Steigerwald converter requires input power to show as current source.The Steigerwald converter uses expensive controlled stopcock element (GTO) rather than thyristor to come the DC input current waveform is transformed to the square wave of alternation.
In a word, the converter that has three kinds of main types.First is general straight line pattern converter, stand very high switching loss.Second kind, controlled resonant converter is developed and is used for high-power applications, for example the Schwarz converter.Controlled resonant converter relies on resonant circuit to reduce switching loss, but they still will stand the loss of high peak current.Lipo/Murai resonant monopole converter belongs to this type.The 3rd, develop quasi resonant convertor to obtain the optkmal characteristics of linearity and controlled resonant converter, for example the parallel resonance converter of developing by Divan.
Like this, just require to produce: improved series resonant converter and between single-phase, three-phase and/or DC power supply and/or load, carry out the method for energy exchange and power transfer, to overcome and not to be subjected to above-mentioned restriction and shortcoming.
Main purpose of the present invention provides a kind of improved series resonant converter, it is than the more cheap favorable characteristics that but still keeps series resonant converter of former static power converter, for example, two-way and four-quadrant operation, carry out the Power Conversion of voltage (boosting) from low to high, generation is to the sinusoidal output voltage of the insensitive balance of unbalanced load and allow the dynamic change of supply power voltage.
Another object of the present invention provides a kind of series resonant converter, is used for DC power or AC power (no matter being single-phase or heterogeneous) are transformed to DC power or single-phase heterogeneous AC power efficiently.
Further purpose of the present invention provides a kind of improving one's methods of Power Conversion of carrying out between two circuit, these two circuit can be for example utility power network and load with reverse feeding ability.
Another object of the present invention provides a kind of series resonant converter and a kind of method of carrying out Power Conversion between two circuit, and this method can make the switching loss of all used in converter switch elements drop to minimum.
Another purpose of the present invention provides a kind of series resonant converter and a kind of method of carrying out Power Conversion between two circuit, flexibly Quality Initiative current impulse height, width and periodic width.
A further object of the present invention provides a kind of series resonant converter, still keeps high efficiency when working under being lower than full load condition.
According to a scheme of the present invention, a kind of Unipolar series resonant converter is provided, be used between first and second circuit, carrying out energy exchange and Power Conversion.Unipolar series resonant converter of the present invention belongs to the type of quasi resonant convertor.This converter comprises that first and second switching devices are used to connect each first and second circuit.Converter has a resonant circuit that is connected between first and second switching devices.Resonant circuit has a resonant capacitor and resonant inductor that is connected in series.One chain electric current synthesizer links to each other with resonant capacitor.Synthesizer response synthesizer control signal comprises the chain electric current of the utmost point chain current impulse of itemizing with generation.Each chain current impulse has zero-sum non-zero section.Can be at the zero-sum non-zero current section that continues each the chain current impulse of single inner control.Converter also has a blocking swtich with the resonant capacitor series connection, is used in each one pole chain current impulse of starting the vibration of resonant circuit being stopped.Converter also comprises a chain electric current damping device that links to each other with synthesizer, is used for during energy exchange the chain electric current being restricted to a predetermined value.
According to another aspect of the present invention, provide a kind of method of between first and second circuit, carrying out Power Conversion.This method comprises: to the step that the chain electric current synthesizes, this chain electric current comprises the square wave one pole chain current impulse of row by resonance oscillations starting and end, and each pulse all has a null section and a non-zero-amplitude section.In controlled step, the null section of each chain current impulse and the duration of non-zero-amplitude section are controlled as predetermined value.
In accordance with yet a further aspect of the invention, provide a kind of chain electric current synthesizer and a kind of controller that is used to control the switch of above-mentioned Unipolar series resonant converter.
The present invention can separately or concentrate has above-mentioned feature and purpose.Those skilled in the art can understand these and other purpose, feature and advantage of the present invention from following explanation and accompanying drawing.
Fig. 1 is illustrated in the block diagram of finishing a kind of structure of the of the present invention Unipolar series resonant converter of three groups of AC in the AC with two-way, four-quadrant operation;
Fig. 2 is illustrated in the block diagram of finishing a kind of configuration of the one pole spannon series resonant converter of the present invention in single-phase DC or AC output and the three-phase AC output with two-way, four-quadrant operation;
Fig. 3 is illustrated in the block diagram of finishing a kind of configuration of the Unipolar series resonant converter of the present invention in single-phase DC or AC input or the three-phase AC output with two-way, four-quadrant operation;
Fig. 4 is the block diagram of a configuration of Unipolar series resonant converter of the present invention, and the three-phase AC that is used to have diode bridge is to AC work, and this diode bridge can be removed to be used for the work of unidirectional DC to AC.
Fig. 5 is a kind of configuration schematic diagram of interchange chain electric current synthesizer of the present invention;
Fig. 6 is the block diagram that is used for a configuration of controller of Unipolar series resonant converter of the present invention;
Fig. 7 is a series of oscillograms of the expression waveform relevant with converter among Fig. 1-4, comprises gate signal timing logic that is used for converter switches and the converter operating state of representing Z pattern, I pattern, F pattern and T pattern.
Fig. 8-the 16th, the schematic diagram of the chain electric current synthesizer of Fig. 1-4 is illustrated in the current path of the time shown in Figure 7 of the mode of operation that is used for following converter with thick black line:
Fig. 8 is illustrated in t
0Stable state Z
sPattern;
Fig. 9 represents the Z of transient state
tPattern (t
1To t
2);
Figure 10 is illustrated in t
2Transient state Z
tPattern;
Figure 11 represents I pattern (t
4To t
5);
Figure 12 represents F
sEquilibrium mode (t
5To t
6)
Figure 13 represents F
tTransient mode (t
6To t
7)
Figure 14 is illustrated in t
7F
tTransient mode;
Figure 15 represents F
tTransient mode (t
7To t
8);
Figure 16 is illustrated in t
9The T pattern.
Figure 17 is a kind of block diagram of configuration of the output voltage error detector portion of Fig. 6 controller, and expression is used for the work as adjustable voltage source and adjustable current source;
Figure 18 is a kind of block diagram of configuration of input voltage error detector part of the controller of Fig. 6;
Figure 19 is a series of oscillograms of the expression waveform relevant with converter shown in Figure 1, and the expression line is to line output voltage and chain current impulse;
Figure 20 is the block diagram that can be used on a configuration of the of the present invention bilateral and non-dissipation voltage clamp of Fig. 1-4 illustrated embodiment in any.
Fig. 1 represents to constitute according to the present invention Unipolar series resonant converter 22 is used for carrying out energy exchange between first and second circuit 24 and 25 first embodiment.Circuit 24 and 25 can be: power supply, for example utility power network, industrial power network, be used for onboard system electrical network, airborne vehicle, boats and ships and the analog of vehicle; Energy storing device; Or load with reverse feeding ability.
For convenience of description, suppose that first circuit 24 is electrical networks, second circuit 25 be can reverse feeding load.In the embodiment of converter 22, first and second circuit 24,25 all are heterogeneous circuit, are three-phase circuits at this.Below described another embodiment express the adaptability of converter, also single-phase AC power of conversion efficiently and DC power (it is also referred to as is " zero frequency " AC power).Definition
Term " one pole " is meant that the direction of the chain current impulse of flowing through converter 22 all is to flow with identical direction, and no matter the direction of flow of power, to meet the power-balance equation that is used for converter 22.Pulse can be set to positive or negative to meet predetermined benchmark as required on first and second circuit 24,25.This process is referred to herein as " setting of one pole chain current impulse ".Obviously, through-put power is equivalent to energy exchange between them between first and second circuit 24,25.
For term as used herein, the letter " L " and " C " that have various footmarks represent inductor and capacitor respectively, the preferred embodiments of the present invention realize with three types switch element, institute's target letter representation: " D " is diode, and " T " is a thyristor; " S " is controlled stopcock, adds the specific switch of footmark representative thereon.Controlled stopcock is defined as: can control the switch element that it turns on and off by applying and remove its gate drive signals respectively, for example; Double-pole contact transistor, gate level turn-off thyristor (GTO), insulated gate bipolar transistor (IGBT) and mos field effect transistor (MOSFET), or their structural equivalents known to those skilled in the art.
Obviously, the described thyristor of preferred embodiment can replace with the controlled stopcock element with several remodeling as required.For example, for MOSFET or IGBT, can be by diode be in series to connect choked flow to cross the reverse current of switch element and prevent to stride across the excessive reverse biased of switch element with switch element.If replace above-mentioned thyristor just not need such additional diode with GTO.Though the turn-off time of thyristor is slower than controlled stopcock element, and would rather be with thyristor without the expensive controlled stopcock element of same size so that more economical converter 22 to be provided.First embodiment
Suppose at first the Unipolar series resonant converter of describing 22 be from as first circuit 24 of input to power flow direction as the second circuit of output.Yet converter 22 also can be operated under the state that allows the backward power flow direction, and this is classified as reversible transducer.Converter 22 comprises the first and second termination capacitor device assemblies of forming low pass filter 26 and 28, is used for cutting off the high frequency chain electric current arteries and veins from circuit 24 and 25.Filter 26 and 28 is connected in parallel with each circuit 24 and 25.First filter 26 has three lines-line C4 capacitor 30,32,34, and second filter 28 has three lines-line C
BCapacitor 35,36,38.
First switching device 40 has and is denoted as 41,42,43,44,45,46 thyristor TA12, T
A21, T
A31, T
A12, T
A22, T
A32Three groups of roads.Second switch device 50 has and is denoted as 51,52,53,54,55,56 thyristor T
B12, T
B21, T
B31, T
B12, T
B22, T
B32At this, first switching device 40 is also referred to as the input switch device, and second switch device 50 is an output switch apparatus.Input and output switching device 40 and 50 does not require bilateral switching element, for example, the reverse parallel connection thyristor to or the controlled stopcock element of differential concatenation right, and need them in the former series resonant converter.The required thyristor of thyristor structure of switching device 40,50 is less than former converter, thereby can make converter 22 than former converter more economically.
Converter 22 is resonant circuits, promptly is connected in series in the resonant circuit and 60 between switching device 40 and 50.Resonant circuit 60 has a L
R Resonant inductor 62 and a C
RResonant capacitor 64.The chain current i
RFlow to the second switch device from first switching device 40 by resonant circuit 60 and conductor 65,66, and constitute the loop by conductor 68.Filter 26 and 28 prevents the chain current i
RAny high frequency composition pass the input and output line of first and second circuit 24,25.Voltage on the output of first switching device 40 strides across conductor 65 and 68, is called as busbar voltage V
AVoltage on the input of second switch device 50 strides across conductor 66 and 68, is called as busbar voltage V
B
Converter 22 comprises a chain electric current synthesizer, is used for the chain current i
RSynthesize the electrode current pulse (see figure 7) of itemizing, each pulse comprises a controlled zero current section and the non-zero current section with clamp part, as following further description.For convenience, the many contacts 72,74,75,76,78 of above-mentioned synthesizer 70 usefulness indicate, and synthesizer 70 is connected across C
R Resonant capacitor 64 and for example controlled T of obstruction switch
ROn resonance shutdown switch or the blocking-up thyristor 80.T
RBlocking-up thyristor 80 usefulness conductors 66 connect C
R Resonant capacitor 64.
Chain electric current synthesizer 70 has one and is connected and has T
RThe C of thyristor
RCapacitor 64 node and the D between the node 78 of synthesizer 70
TTerminating diode 82.Chain electric current synthesizer 70 has a non-power consumption terminating set, as L
TTermination inductor 84, it is with the T between node 76 and 78
T End thyristor 86 is in series.Synthesizer 70 has: two controlled stopcock elements, a S1 trigger switch 88 and a S who is connected between node 72 and 74 who is connected between node 72 and 76
BDamper switch 90.The non-energy-dissipating device of another of synthesizer 70 is chain member L
ITrigger inductor 92, it is with the P that is connected between node 74 and 75
B Damper diode 94 is in series.Node 75 is with conductor 66 and T
RThyristor 80 nodes are connected.
Converter 22 comprises a non-power consumption L
BThe chain current clamp is a damping device, electric current damping circuit device 95 for example, and its node 72 with synthesizer 70 links to each other with 75.i
BDamping current flows through inductor 95, and by a damping current transducer for example ampere meter 96 monitored.When damping circuit device 95 was represented as the device that is separated with synthesizer 70, obvious synthesizer of the present invention can constitute and comprise damping circuit device 95.Converter 22 also has input and output sensor cluster 97 and 98 and in monitoring the voltage and current that flows to the power of second circuit 25 from first circuit 24 respectively.Sensor cluster 97 and 98 can be the existing electric current and the voltage sensor of any kind, for example ampere meter and voltmeter, or equivalent known to the branch art personnel of this area.
Except S
IOutside the switch 88, whole switch main parts of synthesizer 70 can have the thyristor 41-46 that is lower than input and output switching device 40,50 and the current rating of 51-56 rated value, and it has the conveyer chain current i
RCapacity.The electric current of the little mark of a complete cycle duration of the conveyer chain current impulse of the synthesizer switch except that SI switch 88, promptly 1/5th of one-period or still less.Second embodiment
Fig. 2 represents the spannon Unipolar series resonant converter 100 that constitutes according to the present invention.Those of converter 100 and converter 22 identical parts have identical label, those have been carried out the parts revised slightly then added 100 on the label of the corresponding component of its Fig. 1.For example, converter 100 has N
AThe star connection power supply 124 of neutral point 121 and have N
BCarry out Power Conversion between the star connection load 125 of neutral point 123.Converter 100 has the ability of four-quadrant operation, and provides bidirectional power to flow between circuit 124 and 125.
As a further example, the input filter 126 of Y-connection has a N between capacitor 130,132 and 134
ANeutral point connecting line 127, different with the triangle capacitor arrangement of the filter 26 of Fig. 1, output filter 128 also has similar band N
BNeutral point connects 129 structure.Conductor 102 is N
ANeutrality point 127 links to each other with neutral point 129.Chain-dotted line among Fig. 2 is expressed: N
ANeutral point 121 and 127 can connect together, and N
BNeutral point 123 and 129 also can connect together.
The converter 22 of Fig. 1 can allow bidirectional power to flow and four-quadrant operation.Converter 22 both had been not limited to have the converter applications of the characteristic relevant with existing three-phase inverter, also was not limited to circuit layout shown in Figure 1.For example, first and second circuit 24,25 can be single-phase, heterogeneous AC power or DC power.
Fig. 3 represents the 3rd embodiment of the Unipolar series resonant converter 200 of formation according to the present invention.Have identical label with the parts of converter 22 corresponding converters 200, those parts of revising slightly then are to add 200 on the label of the corresponding component of Fig. 1.For example, corresponding with Fig. 1, converter 200 carries out Power Conversion between single-phase AC or the dc-input power 224 and second three phase mains 25.As described above, converter 200 has resonant circuit 60, T
RBlock thyristor 80 and the chain electric current synthesizer 70 that has damping circuit device 95.
Fig. 4 represents the 4th embodiment that is used for the mobile Unipolar series resonant converter of unidirectional power of the formation according to the present invention.Use identical label with the parts of above-mentioned converter 22 corresponding converters 300, carried out the parts revised slightly and then added 300 on the label of the corresponding component in Fig. 1.The diode switch device 340 that converter 300 usefulness are not too expensive replaces the transistor bridge-type input switch device 40 of Fig. 1.It is the flow of power of a direction of load 325 that converter 300 is designed to from first circuit 24 to second circuit, and promptly unidirectional power flows.Diode switch device 340 can comprise a voltage check device 397, rather than the voltage and current sensor cluster 97 of Fig. 1 and 2, above-mentioned voltage check device 397 is made up of their equivalent known to existing voltage detector or those skilled in the art.
Referring to Fig. 5, the interchange embodiment of shown chain electric current synthesizer 270 can be constituted the synthesizer 70 in the converter 22,100,200 and 300 of Fig. 1-4 respectively.Exchanging synthesizer 270 uses GATT thyristors (GATT), has an auxiliary cutoff thyristor (GATT) and/or the GTO of its short turn-off time (10 μ s or shorter) and be used for synthesizer 70 simpler circuit so that a ratio to be provided.Synthesizer 270 has a T who replaces Fig. 1
RThe D of thyristor 80
RBlocking diode 280.Synthesizer 270 has a same T
TThe single-phase L of thyristor 286 series connection
IInductor 292 is with C
RCapacitor 64 and D
RThe node of diode 280 links to each other with node 272.T
IThyristor 188 replaces the S of Fig. 1
I Switch 88, and L
RInductor 62 is C
RCapacitor 64 nodes link to each other with node 272.T
TAnd T
ITransistor 286 and 288 is finished the S with chain electric current synthesizer 70 shown in Figure 1
I Switch 88 and T
TThyristor 86 identical functions.Operation principle
The work of the converter 22 of Fig. 1 illustrates the operation principle of converter 22,100,200 and 300 through discussion, has also expressed the details of synthesizer 70 among Fig. 1.Suppose that it is that the input of A1, A2 and A3 is the output of B1, B2 and B3 with the label that links to each other with threephase load 25 that converter 22 has AC power supplies 24 continuous labels.Load 25 can be a passive load, for example resistor, inductor or capacitor, or their combination.And load 25 also can be motor, and this motor can be added on output B1, B2 and the B3 voltage owing to back electromotive force (electromotive force) characteristic of motor.Those skilled in the art are as can be seen: the two-way embodiment of Fig. 3 can make power flow to input A1, A2, A3 from output B1, B2 and B3.The following describes the various controlling schemes of the power delivery from the power supply to the load.
For example, when exchanging, energy in Fig. 1, represents closed current circuit between power supply 24 and load 25 with thick black line.Flow through the thyristor T of input switch device 40 in this closed path current in loop
A11And T
A32, and flow through the thyristor T of output switch apparatus 50
A31And T
B12L
BDamping circuit device 95 also is the part of this current circuit, with existing DC chain transformaiton utensil identical effect is arranged.A. the generation of chain current impulse: USGL controller
Referring to Fig. 7, each converter 22,100,200 and 300 all has a controller 398 of being made up of the first and second pilot controller levels.The first order of controller 398 comprises a main thyristor 6 selection logic (" MTSL ") controllers 400, and the second level comprises a Unipolar series resonant converter switch gate logic (" USGL ") controller 500.Fig. 6 represents its structure, after the work that is subjected to the converter arranged by the switching sequence table of USGL controller 500 decision has been described, will describe the general work principle of MTSL controller 400 in detail.
USGL controller 500 provides gate signal, except the shutoff of the thyristor that turn-offed by natural commutation, according to the timing logic concentrated area of Fig. 7 signal 502 is offered all converter switches element (T
AAnd T
BThe 241-244 of thyristor 41-46,51-56 and input and output switch apparatus 40,50 and 240; T
RAnd T
TThyristor 80 and 86; And S
IAnd S
BSwitch 88 and 90).The timing of switching signal also can be described with reference to Fig. 8-16.Can with commercially beneficial simulation and/equivalent known to digital logic component or those skilled in the art finishes USGL controller 500.
If respect following decision then USGL controller 500 will offer all converter switches elements to gate signal 502:
1. be used for by meeting S
ISwitch 88 triggers chain current impulse i
RTiming; With
2. select decision to be used for the current i of chain electric current
RThe input and output switching device 40,50,240 and the T in path
AAnd T
BThyristor.
With reference to Fig. 7, the process that the chain current impulse takes place is described.The chain current i
RBe defined as flowing through L
RThe electric current of resonant inductor 62.Best chain current i
RComprise unipolar pulse, each pulse has a zero current section and a non-zero current section.Preferably zero-sum non-zero current section both can be in the duration Be Controlled and guarantee that MIN switching loss is by Zero Current Switch and/or zero voltage switch.
Best, the chain current impulse takes place with stable manner under the power supply of regular and irregular and loaded work piece state.At this, stability is meant: (that is: the L of resonant circuit 60, synthesizer 70 when these chain parts are flow through in continuous current impulse
TAnd L
IInductor, and L
BDamping circuit device 95) energy that prevents to be stored in the time in the chain part is set up or is broken to put on the skin and ruin.Especially, across C
RVoltage on the resonant capacitor 64 is the unit of measurement of this stored energy, preferably can not become excessive when then finishing in each pulse period or destruction.
As a given implementation, the cycle of chain current impulse can be less than the cycle at the voltage and current waveform of input and output place of converter.Thereby, suppose at a complete pulse in the cycle:
1, because C
AAnd C
BThe same C of filter capacitor 30-38
R Resonant capacitor 64 is compared greatly then, and the line in power supply 24 and load 25-line voltage is constant; With
2, because inductor 95 and L
R Resonant inductor 62 is compared greatly then at L
BCurrent i on the damping circuit device 95
BBe constant.
For the suitable work of converter 22 not only these hypothesis need, and it is used to principle of the present invention is described and those skilled in the art are misread tight description in a kind of simple and clear mode.
The chain current i
RV is driven by the chain driving voltage.Have only selected thyristor to be switched on to allow the chain current i when switching device 40 and 50
RDuring circulation, chain driving voltage V
LDBe only non-zero.Chain driving voltage V
LKDetermined by following part:
1. the line in power supply 24 and load 25-line voltage; With
2. be selected for the chain current i
RInput and output device 40 and 50 thyristor.
When triggering thyristor 41-46 and 51-56, be used for the chain current i
RDriving voltage V
LDBe voltage difference:
V
LD=V
A-V
B
Now, the T among Fig. 1 is flow through in consideration in the loop of representing with thick black line
A11, T
A32, T
B31, T
B12Thyristor 41,46,53 and 54 chain current i
R, because the thyristor of input and output switching device is used to transmission line choke i
R, inlet highway voltage V
AWith output busbar voltage V
BBe:
V
A=V
A1-V
A3
V
B=V
B3-V
B1
Wherein, (V
A1-V
A3) and (V
B1-V
B3) be in fact respectively line-line the voltage in power supply 24 and the load 25.
Even chain driving voltage V
LDBe pulse change one by one, suppose positive and negative values, because both line-line voltage of power supply 24 and load 25 is bounded, its maximum also is bounded.The line of power supply 24 and load 25-line voltage also is bounded, because:
1. converter is pressurizeed by a reliable voltage response, or
2. the control of the thyristor in switching device 40,50 is according to the characteristic curve of one group of reference signal, below will be to this discussion.
Because supposition (not needing) voltage V
AAnd V
BBe constant, also can suppose; V during the non-zero current section of chain current impulse
LDAlso be constant.
Fig. 7 represents: at the timing logic of the used gate signal of two complete cycles of the waveform of the duration of work scheduled volume of converter shown in Figure 1 22 and various switch element.For the first pulse train driving voltage V
LDBe positive, then bear for second pulse.Chain current impulse i
REach complete cycle four kinds of basic mode of operations are all arranged, be called:
1.Z-pattern, during chain electric current I R is zero as zero current section Z.
2.I-pattern, during the chain current impulse is triggered by resonance oscillations as trigger current section I.
3.F-pattern is passed through L in chain current impulse when the harmonic circuit vibration stops
BThe damping circuit device current i of damping circuit device 95
LBDuring the clamp as straight non-zero current section F.
4.T-pattern is returned as by resonance oscillations during zero as the electric current section T that finishes in the chain current impulse.
In Fig. 7, chain current impulse i
RWaveform table reveal this four kinds of mode of operations.The non-zero current section comprises I section, F section and T section.The duration of zero current section Z and non-zero current section (I+F+T) can both be controlled individually in the duration.
Fig. 7 also expresses the sequential chart of the switch that is used to turn on and off each converter 22 so that the gate signal timing logic of each switch element to be described.In Fig. 7, use the arrow indicator cock time near each switch element name.When receiving a control signal with shutoff rather than conducting, switch element is marked with angle asterisk on the signal.When the electric current by each thyristor turns back to zero, produce thyristor and turn-off, in Fig. 7, represent with angle asterisk on two by natural commutation.Shown in Figure 7, all are defined as " Zero Current Switch " (ZCS) at the switch that zero switching current place produces, and the switch that produces at zero switching voltage place is defined as " zero voltage switch " (ZVS).
Fig. 7 represents to flow through the electric current of thyristor, that is: T
RThyristor 80 transmission current i
TR, T
TThyristor 86 transmission current i
TT, both thyristor chain current i of input and output switching device 40,50
RWith the switching device 40 of leading preset time and 50 specific T
AAnd T
BThyristor depends on and is used for will further being discussed this below with the specific controlling schemes of power supply 24 to load 25 delivering powers.
The work of B.Z-pattern
The Z-pattern of work is divided into stable state Z shown in Figure 8
sPattern and transient state Z shown in Figure 9
tPattern.When turn back to zero and T at the chain electric current that previous impulse duration circulated
AOr T
BWhen thyristor switching equipment 40 or 50 not conductings, stable state Z
sPattern takes place.At transient state Z
tIn the pattern, the action of being born is the triggering of preparing the non-zero current section.At Z
sThe state of all switch elements during the pattern shows in Fig. 7, at moment to:T
A, T
B, T
TThyristor and S
ISwitch is not triggered (being indicated by last asterisk), and S
BSwitch and T
RThyristor is conducting.
With reference to Fig. 8, at Z
sDuring the pattern, S
ISwitch 88 disconnects, and passes through L
BThe current i of damping circuit device 95
LBBe to pass through L
IInductor 92, DB diode 94 and S
B" the unidirectional afterflow " of switch 90.Under these states, C
R Resonant capacitor 64 non-conducting electric currents, and be under the constant and across C
RCapacitor 64 is positive V
CRVoltage.By selecting L
R, L
IAnd C
RAppropriate value, V
CRVoltage can be higher than chain driving voltage V
LDMaximum.
With reference to Fig. 9, by connecting S
ITrigger switch 88, Z
TPattern is at moment t
1Beginning.Select t constantly
1Control the duration of zero current section Z.Work as S
ISwitch 88 is at T
1During conducting, because C
RAnd L
LIThe resonance oscillations of harmonic circuit produces current i
TRTo begin to flow through T
RThyristor 80, positive resonant capacitor voltage V
CRReduce.Owing to passing through bigger L
BThe current i of damping circuit device 95
LBPass through D when constant
BDiode 94 and L
IThe current i of inductor 92
DBReduce current i
TRAt moment t
1Rise.Like this, at moment t
1, current i
DB, current i
TRWith resonance condenser voltage V
CRState be to be subjected to by C
RAnd L
IThe resonance oscillations of the circuit of forming, thereby this state meets following condition:
i
DB=i
LB-V
CR(Z
s)sin[WI，R(t-t
1)]／Z
I，R
i
TR=i
LB-i
DB
V
CR=V
CR(Z
s)cos[W
I，R(t-t1)]
Wherein, W
I, R=(L
IC
R)
-1/2
Z
I，R=(L
I／C
R)
+1／2
V
CR(Z
s) resonant capacitor voltage during the ZS pattern.
As can be seen, converter 22 can be designed to: at resonant capacitor voltage V
CRBecome the maximum chain driving voltage V that can stand less than chain part
LD, maxBefore, current i
DBTurn back to zero.If desired, this state can be obtained and as based on a design constraint according to the characteristic impedance of following formula from these relations:
Z
R，I＜[V
CR，min(Z
ssin(α)]／i
LB
Wherein:
α=arccos[V
LD，max／V
CR，min(Z
s)]
Like this, owing to pass through D
BThe current i of diode 94
DBReduce and at moment t
1Pass through T
RThe current i of thyristor 80
TRRise.
At moment t
2, current i
DBGet back to zero and current i
TRBe clamped to damping current i
LBValue on.At moment t
zVoltage V
CRBe still positive, D under perfect condition then
B Diode 94 is reverse biased and S
BSwitch 90 can be turned off, that is, and and at zero current (ZCS) with under no-voltage (ZVS).Yet, because at voltage V
CRBecome and be lower than chain driving voltage V
LDStop the chain current i before
RCirculation is at moment t
3The predetermined thyristor T of actuating switching device 40,50
AAnd T
BJust can not make these thyristor conductings.
The work of C.I pattern
With reference to Fig. 7 and 11, at moment t
4, when the voltage on these thyristors is zero (ZVS), the chain current i
RBegin to flow through T
AAnd T
BThyristor.This favourable zero voltage switch of input and output switching device has just produced harmonic capacitor voltage V
CRControlled reduction, and become the feature that the existing series resonant converter that uses the current impulse of AC chain can not have.
At moment t
4Afterwards, chain current i
RRise and voltage V
CRReduce, it is defined as triggering is the I pattern.During the I pattern, as shown in figure 11, by C
RAnd L
R Resonant circuit 60 produces resonance oscillations, can represent the state of converter with following equation:
L
R(di
R／dt)=V
LD-V
CR
C
R(dV
CR／dt)=-i
TR
Wherein:
i
TR=i
LB-i
R
Work as current i
RDuring rising, i
RIt is zero up to arriving that thyristor current flows reduces (above-mentioned C grade formula), and remain on the end up to the work of I pattern above freezing, promptly at moment ts.
The work of D.F pattern
Referring again to Fig. 7, at moment t
5, as thyristor current flows i
TRWhen turning back to zero, T
RThyristor 80 is owing to natural commutation is turn-offed.And at moment t
5, the chain current i
RBe fixed to damping current i
LBValue on the work of beginning F pattern.With the Z mode class seemingly, the F pattern comprises two continuous mode of operations; F shown in Figure 12
sF shown in equilibrium mode and Figure 13-15
TTransient mode.
Referring to Figure 12, as chain current impulse i
RBe fixed to damping circuit device current i
LBWhen last, F
sEquilibrium mode is at moment t
5Beginning.Also be at moment t
5, voltage stops to reduce and at whole F
sRemain a steady state value during the equilibrium mode.Because at moment t
5Current i
TRTurn back to zero, V
CRSteady state value be held.At F
sDuring the pattern, resonant capacitor voltage V
RCNumerical value provide by following formula:
V
CR(F
s)=V
LD-Z
R，Ri
R，max
Wherein:
Z
R，R=(L
R／C
R)
+1／2
i
R, max=to i
LBOn maximum chain electric current.
Clamp is to produce the chain current i
RL
RAnd C
RThe characteristic impedance of resonant circuit 60 is to improve resonance oscillations during the I pattern.
At F
sDuring the pattern, resonant capacitor voltage V
CRTo not positive, allow the chain current i
RArrive zero and as the zero voltage switch during the coming T pattern.Above-mentioned to V
CR(F
s) instruction card illustrate: can be by selecting like this Z
R, RGuarantee this state:
Z
R，R＞L
LD，max／i
LB
Wherein, by at F
sBe fixed to damping current i during the equilibrium mode
LBOn, i
R, maxEqual i
LB
These three needs explanations at that point.At first, as resonant capacitor voltage V
CRFrom at moment t
0Beginning when reducing, it is at moment t
5Reach minimum value, F
sThe beginning of pattern.At whole F
sDuring the pattern, V
CRVoltage remains on this minimum value up to moment t always
6F
sThe end of pattern.For V
CR(F
s) former given explanation is at whole impulse duration resonant capacitor voltage V
CRMinimum value, and since underlying cause its be limited:
1. the damped inductor current i of Zui Da chain electric current
LBLimit; With
2. because both line-line voltage of power supply 24 and load 25 is limited then chain driving voltage V
LDBe restricted to the maximum line-line voltage that inputs or outputs.
As second explanation, because the chain current i
RBe fixed to damping current i
LBAnd resonant capacitor voltage V
CRBe constant then the resonance oscillations of resonant circuit 60 at moment t
5Be stopped.By T
RThe shutoff of thyristor 80 causes stopping by the resonance oscillations of circuit 60.When the chain current i
RWhen flowing through converter 22 (the thick black line among Fig. 1 and 11), 25 power delivery takes place from power supply 24 to load and the resonance oscillations of resonant circuit 60 stops, this is a unavailable feature in the former converter.During this flow of power, many parts of chain electric current synthesizer 70 are transmission current not.Certainly, whole load currents had only S
ITrigger switch must be specified, and effective cost savings are provided.
As the 3rd, F
TPattern can begin at any time, and then the duration of the duration of F pattern and non-zero current section is controlled.
At moment t
6, the F pattern begins.In order to stop the chain current i
RFlow, resonant circuit 60 is stopped.The chain current i
RBe converted into and flow through resonant capacitor 64, D
TDiode 82 and S
BSwitch 90.
With reference to Figure 13, in the first step of this transfer process, at any required moment t
6Trigger T
TThyristor 86.Trigger T
TThyristor 86 has just started C
RAnd L
TResonant circuit.C
RAnd L
TResonance oscillations drives the resonant capacitor voltage V of page or leaf
CRAt moment t
7Be raised to zero, second step that is used for this transfer process starts (Figure 14-15),, follows S that is
BThe zero voltage switch of switch 90 is S
IThe shutoff of switch 88 (indicating) by the asterisk among Fig. 7.Two switches all are created on the no-voltage (ZVS).
At moment t
6And t
7Between, L
TAnd C
RThe resonance oscillations of resonant circuit is not subjected to the influence of the curtage in converter 22 other parts fully.By T
RBlock thyristor 80 and S
BBlock switch 90 and obtain L
TAnd C
RThe isolation of resonant circuit.Thereby, at moment t
6And t
7Between the interval in resonance oscillations satisfy following formula:
V
CR=L
T(di
TT／dt)
C
R(dV
CR/ dt)=i
CR=i
TTThereby, pass through L
TThe maximum of the electric current of inductor 84 is provided by following formula:
i
TT，max=V
CR，max(F
s)／Z
T，R
Z
T，R=(L
T／C
R)
+1／2
Wherein, Z
T, RBe L
TAnd C
RThe characteristic impedance of resonant circuit.
In order to prevent to surpass damping current i by the electric current of any chain part inductor and switch element
LB, Z
T, RCharacteristic impedance should be satisfied following relationship:
Z
T，R＞V
CR，max(F
s)／i
LB
By the V that provides more than replacing with this formula
CR(F
s), this relation draws following Z
T, RAnd Z
R, RBetween relation:
Z
T，R＞Z
R，R+V
LD，max／i
LB
For at S
IBefore being disconnected, switch 88 provide time enough to make S
BSwitch 90 closures (for the microsecond level of present coml IGBT) are used for L by selecting a high induction reactance
TInductor 84 can be regulated V
CRRate of change.t
6And t
7Between the time interval can draw by above-mentioned resonance oscillations equation, to be provided for the exact formulas in this time interval:
T(t
6，t
7)=[π(L
TC
R)
+1／2]／2
At moment t
7, S
BSwitch 90 is closed, resonant capacitor voltage V
CRBe zero and remain on above freezing up to S
ISwitch 88 is broken as.With reference to Figure 14, at S
BAnd S
IBetween the startup of switch, because electric current flows through L
TInductor 84, S
ISwitch 88 and S
BThe short circuit paths of the reverse parallel connection diode of switch 90, V
CRVoltage remains on above freezing.At S
BAnd S
IBetween the startup of switch, S
ISwitch 88 chain current i
RWith LT inductor current i
TTBoth are till the stable disconnection of switch S I.
Like this, S
ISwitch 88 is set to peak current and equals maximum chain current i
RWith maximum L
TInductor current i
TTSum.But, because current i
TTBe by switch S in the short duration (for a microsecond level of commercial effective power switch)
ITransmission, then average current can be ignored and is higher than chain circuit i
RMean value that part of.Thereby, S
ISwitch 88 transmission extra current i
TtTo compare with the chain current cycle be extremely short time, for being 60 μ levels second for the designed converter of under the frequency modulation of 20KHz, working.
Even the most business-like power switch component can stand this rising of peak current fully and not need to improve rated value, a large amount of schemes can be avoided any problem.For example, S
ISwitch 88 can be by two paralleling switch (not shown) that element replaces, and one is exclusively used in transmission S
BAnd S
IExtra current i between the startup of switch
TTThis special switch can be at moment t
6And t
7Between conducting and the time t
1Turn-off.The average current rated value of this special switch is very little, as the Tab phenolphthaleinum road at moment t
1Begin shutoff and conducting moreover all can be under no-voltage.
As shown in figure 15, then at moment t
7Switch S
IDisconnection, the chain current i
RBe converted into and flow through C
RResonant capacitor 64.Resonant capacitor voltage V
CRWith the chain current i
RAll be subjected to the resonance oscillations from two resonant circuits: C
RAnd L
TResonant circuit is by T
TThyristor 86 and C
R, L
R, L
IResonant circuit starts.After moment TS, resonant capacitor electric current I CR is:
i
CR=i
R+i
TT
Current i
RAnd i
TTBoth and current i
CRCan only be assumed on the occasion of because they are by unidirectional thyristor transmission, that is, input and output thyristor T
A, T
BAnd T
TThyristor 86.As a result, resonant capacitor voltage V
CRFurther improve.As voltage V
CRBecome and be higher than chain driving voltage V
CDThe time, because C
R, L
R, L
IResonant circuit influence the chain current i
RReduce, as shown in the formula described:
(L
R+L
L)(di
R／dt)=V
LD-V
CR
The work of E.T pattern
With reference to Fig. 7, carving t
8, as resonant capacitor voltage V
CR surpasses chain driving voltage V
LDThe time T pattern begin, make the chain current i
RBegin its decay.As shown in figure 16, when the chain current i
RThe T pattern is at moment t when reaching zero
9Finish.At moment t
9, input and output switching device 40 and 50 t
AAnd t
BThyristor is turn-offed by natural commutation.During the T pattern, the chain electric current passes through by L
TInductor 84 and C
RThe resonance oscillations of the resonant circuit that resonant capacitor 64 is formed and turn back to zero gradually, as among Figure 15 by shown in the thick black line.At C and L
TThe duration of oscillation of resonant circuit, current i
TTAlso turn back to zero.Damping circuit device current i
LBPass through S
BSwitch 90 and D
BDiode 94 accelerates to inertia afterflow (free-wheel) gradually.
At moment t
10, resonant capacitor voltage V
CRStop to rise and remain one constant on the occasion of.At moment t
10, the T pattern finishes, and the pulse period is done, along with new Z
sPattern work, the new pulse period begins.The whole process that is used to take place new chain current impulse can repeat to set up the utmost point chain current impulse of itemizing.
F. exchange the work of GATT or GTO
Chain electric current synthesizer
Those skilled in the art can resemble and revise GATT or the GTO of USGL controller 500 to control synthesizer shown in Figure 5 270, the T of GATT or CTO known
TAnd T
IThyristor 286,288 all resembles the T of above-mentioned synthesizer 70
T Thyristor 86 and S
ISwitch 88 is worked like that.
T
TThyristor 288 and S
ISwitch 88 conductings simultaneously are for example at the t of Fig. 7
1And t
11T when electric current flows through it and arrives zero
1Thyristor 288 is turn-offed by natural commutation.For example, the TI thyristor 288 of GATT is at t
9Turn-off.If use GTO, then USGL controller 500 is at t
7Give the T of GTO
IThyristor sends a cut-off signals.
No matter be the GTOT that GATT also is
TThyristor 286, all resemble Fig. 7 described and above-mentioned thyristor 86 is described by like that logical and shutoff.D
RBlocking diode 280 is led as general-purpose diode according to biased diode 280.In unidirectional afterflow (free-wheeling) pattern at time interval t
0-t
1And t
9-t
11Flow through by L during this time
BDamping circuit device 95, D
RDiode 280, L
IInductor 292 and T
TThyristor 286 formed loops.G. one pole chain current impulse
Z in each pulse
sDuring the pattern, resonant capacitor voltage V
CRConstant positive value draw by following formula:
V
CR(Z
s)=｜V
LD｜+KZ
RI，Ri
R，max
Wherein: Z
RI, R=[(L
R+ L
L)/C
R]
+ 1/2
i
R, max=be clamped to maximum chain electric current
V
LD=V
LDAbsolute value
0＜K＜1
Be during the T pattern, to make the chain electric current get back to zero L
R, L
IAnd C
RThe characteristic impedance of resonant circuit.COEFFICIENT K is always positive, and maximum is 1 and is FS pattern phase chain driving voltage V
LDWith resonance condenser voltage V
CRThe function of value.If V
CdBe zero, K reaches minimum value.Thereby, in order to guarantee Z
sResonant capacitor voltage V during the pattern
CRBe higher than chain driving voltage V
LDMaximum, disclose by the trouble analysis verified of experiment: must be Z
RI, RBe chosen as selected Z
R, RAbout 1.3 to 1.8 times of value.Provided Z in the past
R, RThe requirement of selection.
The T pattern is the chain current i in other patterns
RAll switch elements on during whole Z pattern, apply a constant reverse biased.Total reverse biased preferably equals (V
CR-V
LD) and can pass through Z
RI, RSelection be set at any required value.
Though T
RThyristor 80 can be along with S
IThe conducting of switch 88 is triggered to start Z
sPattern, but had better after the T pattern is finished, trigger T immediately
R, promptly when the chain current i
RAt moment t
10Turn back to when needing, trigger T immediately
RWork as switch S
IDuring conducting, because across T
ROn voltage at T
RAlmost nil during the beginning conducting, then this work helps T
RZero voltage switch.But total reverse biased is only shared by the thyristor of input and output switching device 40 and 50.
At last, should see: the non-power consumption parts transmission of chain electric current synthesizer 70 is hanged down rms (root mean square) electric current and is produced low-loss.Owing to be the disresonance vibration of these chain parts, will produce this advantage during the F pattern.Power transmission of 25 from power supply 24 to load, otherwise or.During the F pattern, be to flow through L by electric current
BDamping circuit device 95 and S
ISwitch 88 is finished.During the F pattern, L
B95 transmission of inductor DC electric current, then L
BInductor does not have the skin effect losses of AC induction, and can cause these losses in always by the converter before the current impulse of resonance (AC) vibration generation chain.H. the stability of chain current impulse
Otherwise the appropriate characteristics of prerequisite converter is from power supply 24 to load 25 or the stability of the chain current impulse of through-put power.As described above, for each pulse period completely, resonant capacitor voltage V
CRReach confined positive and negative maximum.Because the maximum current in any inductor of chain part can not surpass damping circuit device current i
LB, just in the chain part of converter, avoided energy to set up and destroy.Like this, dash (as shown in Figure 7) and carry out with a kind of stable manner by means of producing the utmost point chain electric current of itemizing by converter 22 through-put powers.I. the peak value of chain current impulse
Clearly, by damping circuit device L
BOn amplitude, limited the peak value of chain current impulse.L
bThe inductance value of inductor 95 is higher to guarantee current constant ground work in the duration of the expected duration of being longer than the chain electric current complete pulse cycle.By selecting the T of input and output switching device 40,50
AAnd T
BThe capacity of thyristor is controlled and is passed through L
BThe i of inductor 95
LBElectric current is with the chain electric current.During the F pattern, the chain current i
RBe fixed to and flow through damping circuit device L
BCurrent amplitude i
LBL
BThis clamp behavior of inductor 95 gives chain current impulse i the waveform of approximate square wave
R, rather than the sinusoidal waveform in the former series resonant converter.
For the suitable power delivery under the state of operating at full capacity, converter 22 can be designed as: at whole complete pulse period cochain current impulse i
RMean value to equaling the required maximum load current of operating at full capacity at least.For example, if converter 22 is designed to same i
O, maxMaximum electric current at full capacity have the specified input and output voltage of equating, then converter 22 can be designed as and allows to equal at least i
O, maxThe maximum average chain current i of electric current at full capacity
R, aveLike this,
i
R，ave=i
O，max
Because chain current impulse i
RBe approximate square wave, for the rated value of converter 22, chain current impulse peak value i
R, peakFor:
i
R，peak=i
R，ave／D=i
o，max／D
Wherein, D was counted the given pulse duty of the ratio of whole pulse period admittedly by the duration of non-zero current section (I, F and T pattern).
Commercial favourable, the thyristor with inverter grade of 1200 blocking voltage rated values can be used to have the input and output switching device 40,50 of the converter 22 of 480V line-line voltage rating.This thyristor provides the turn-off time to the zero section duration of about 14 μ seconds.Like this, the converter 22 that is constituted according to the present invention can have the modulating frequency of counting the 16KHz of D as about 0.77 duty admittedly.From above-mentioned relation, chain current peak i
R, peakIt approximately is 1.3 times the maximum current of operating at full capacity.
For former converter, this factor is 3 to 9 orders of magnitude, far above 1.3 value of converter 22.Like this, the current delivery composition of former converter must be much larger than current rating, and has improved their expense, because I
2The R thermal losses, initial stage element cost and job costs are all high.
Series resonant converter in the past send near sinusoidal the chain current impulse so that the whole non-zero current section of pulse be synthesized by resonance oscillations.This peak value and the relation between mean value and maximum electric current at full capacity with regard to producing the chain electric current in the former converter, for:
i
R，peak=(π／2)(i
R，ave)=(π／2D)[i
(O，max)]
Thereby, even for identical duty factor D, owing to the factor of pi/2 makes the chain current peak of the required chain current peak of former converter greater than converter 22.If consider the actual design scheme, because the duration of zero current section is bound to improve, this factor causes reducing of duty factor D greater than pi/2.Just can avoid the reducing of this duty factor in the former converter as long as sacrifice modulating frequency by the duration of improving the pulse period.J. Ren Xuan satiable inductor device
In the actual design of before this converter, each thyristor of input and output switching device comprises the time rate of damper element (not shown) with the positive and negative blocking voltage of restriction on these thyristors, like this, and the predetermined conducting of the thyristor of just avoiding.These damper elements generally include the tandem compound of a resistor that is connected in parallel with thyristor with the satiable inductor device of thyristor series connection and small capacitor and.
Use the reverse parallel connection thyristor to form the bidirectional switch main part before series resonant converter in, every pair of thyristor must have a satiable inductor device, and in embodiment of the present invention, only in switching device 40,50, use unidirectional switch elements, promptly be used for the single thyristor of a unidirectional switch elements.Like this, L
R Resonant inductor 62 has reduced T in the switching device 40,50
AAnd T
BThe time rate of change of the forward blocking voltage of thyristor.
But, if the higher time reduction rate of some application requirements, then single L
RSSatiable inductor device 299 can same L
R Resonant inductor 62 series connection is placed, rather than as former converter the (see figure 5) saturated inductor be in series with each thyristor of switching device.
In addition, in the converter 22 of Fig. 1, this L
RS Satiable inductor device 399 can be connected between node 75 and the conductor 66 (seeing Figure 20) by connection.Work as L
RSSatiable inductor device 399 ' be connected node conductor 66 and T
RIn the time of between the positive pole of thyristor 80, another the suitable position that is used for the saturated inductor of converter 22 dots in Figure 20.This saturated inductor 299,399,399 ' reduced S
IThe conduction loss of switch 88.Satiable inductor device 399 ' has also reduced T
RThe reverse recovery current of thyristor 80.
With reference to Fig. 7, SI switch 88 is at t
1, t
11Conducting triggers by C to start
R Resonant capacitor 64 and L
IThe Z of the resonant circuit that inductor 92 is formed
tPattern.Promptly can between conductor 66 and node 75, also the C that has additional induction reactance can provided
R/ L
IInsert a satiable inductor device (not shown) on the resonant circuit.This additional induction reactance has reduced to pass through S when its conducting
IThe current changing rate of switch 88.
Input and output switching device 40,50 thyristor T
AAnd T
BAs unidirectional switch elements.In order to prevent thyristor T
AAnd T
BNon-predetermined conducting, by inserting a same L
RThe L of resonant inductor 62 series connection
RSChoose satiable inductor device 199 wantonly and prevent that anodal (reapplied) rate of change (those skilled in the art are called " adding dv/dt conducting phenomenon again ") that adds again to cathode voltage from reaching excessive value, as shown in Figure 5.L
RSInductor 199 also can be included in the converter 22,100,200 and 300 of Fig. 1-4.
In contrast, former converter need have by the reverse parallel connection thyristor the bilateral switching element formed as the input and output switching device, and has further improved the cost of element.Converter before these needs the series connection of saturable reactor to insert each bidirectional switch device, then a three-phase AC is just needed 12 satiable inductor devices to the AC converter.For fear of voltage jump on the thyristor of chain electric current not, need to use the thyristor that has higher blocking voltage rated value, have undesirable turn-off time always.Thereby need to improve duration of the zero current section of chain electric current in the former converter.
In addition, former converter is by using 12 induction reactance for avoiding voltage jump in the inductance of resonant inductor induction reactance non-leading on the thyristor.Yet these low induction reactance values require thyristor to be subjected to the higher influence that adds the dv/dt value again, impel the zero current section duration to be increased on the turn-off time of thyristor manufacturer defined.Owing to do not need to use the reverse parallel connection thyristor right in the input and output switching device in the former converter, described converter 22,100,200 and 300 just is not subjected to the restriction of these constraints.
As above in the face of Z
sResonant capacitor voltage V during the pattern
CR(Fig. 7 and 8) is described, when zero current is increased to the shutoff of manufacturer's regulation with duration of section more than, the T that all will turn-off
AAnd T
BThyristor all is subjected to the constant reverse biased that a duration equals this regulation turn-off time.This feature can not be used for former DC chain transformaiton device MTSL controller
MTSL controller 400 is made requirement and how to be passed through one pole chain current impulse i with power
RFlow through the decision that is thought of as the basis of converter.Can constitute MTSL controller 400 by the equivalent known to commercially beneficial simulation and/or digital logic device or those skilled in the art." master " is meant the main T of input and output switching device to term
AAnd T
BThyristor 41-46, the T of 51-56 and 241-244 rather than chain electric current synthesizer 70
RAnd T
TThyristor 80 and 86.
In the following description, main T
AAnd T
BThyristor also is denoted as the thyristor T shown in Fig. 1 and 2
AmnAnd T
Bmn(variable m and n equal footmark 1,2 or 3).According to the needs of power delivery, MTSL controller 400 is selected: the thyristor of which input and output switching device 40,50,240 is used for chain current impulse i with composition
RCurrent path.For illustrative purposes, the converter 22 of Fig. 1 will be used to describe the work of MTSL controller 400.The A error detector
First task of MTSLK control 400 is the input and output node A in correspondence
mAnd B
mGo up error-detecting to the input and output voltage waveforms.MTSL controller 400 has an error detector 402, and it is used to finish two first basic functions, particularly:
1. come the shaping output waveform according to the reference signal of a desirable output waveform of representative by control output voltage or output current; With
During the non-zero current section by control flows through L
BThe current i of buffer inductor 95
LBSo that in fact with a reference value i
LB, REFIn fact with a reference value i
LB, REFBe complementary to come chain current impulse i
RBe clamped to a desirable peak value.
Utilize the detector 404 of an output voltage error test section or error detector 402, example can be finished the output waveform shaping feature as shown in Figure 17.Utilize the detector 406 of an input voltage error-detecting part or error detector 402, example can be finished the function of chain current impulse clamp as shown in Figure 18.
From seeing that the input voltage error-detecting figure shown in the detector 406 may be obvious that: MTSL controller 400 can be designed to finish extra function.For example, MTSL controller 400 can be designed to the waveform shaping on the converter input so that realize the control of input power factor.MTSL controller 400 also can be designed to finish the thyristor T of restriction chain member and input and output switch module 40,50
AAnd T
BVoltage rating.
Realize output waveform shaping and i
LBThese two kinds of functions of Current Control relate to a kind of modulator approach, and this method is used for by Quality Initiative current impulse i
RControl the power transfer of z through converter 22.Many known modulation techniques can be used the technical staff in this area, for example pulse width modulation, pulse frequency modulated, pulse area modulation, pulse frequency modulated, pulse area modulation, with integration period modulation as mention in front by Mohan, the discussion in the textbook that Undeland and Robbins showed: power electronics: converter, application and design.For these modulation technique open loop circuits and closed loop circuit is possible.In closed loop circuit figure, detect the error of actual output variable (voltage or electric current) according to a reference signal.The purpose of this modulator approach is this error to be reduced to be minimum within an acceptable restriction.
Though all these modulation techniques all are applicable to converter of the present invention, closed loop circuit pulse area (" CL/PA ") modulation technique is best.It is maximum that the flexibility of the chain current impulse that this CL/PA modulation technique just produces between input and output switching device 40,50 reaches.Utilize the zero section that CL/PA modulation can the Quality Initiative current impulse and the amplitude and the duration of non-zero section.Even, utilize the CL/PA modulator approach to make converter 22 can keep peak efficiency less than the duration of work under the full-load conditions.Because along with the load 25 of needs is reduced to less than full load power, the amplitude of chain current impulse and/or frequency and switching loss can be reduced, so can keep high efficiency.In previous controlled resonant converter since the amplitude of pulse and the duration of zero-sum non-zero section be uncontrollable, so such flexibility is impossible.(1) output voltage waveforms control
The CL/PA modulation technique utilizes a kind of short-cut method that detects the zone of chain current impulse can finish the output voltage waveforms shaping feature of MTSL controller 400, the i.e. time integral of chain current impulse.Determine chain current impulse zone by the output voltage that detects between two lines, rather than detect the chain current i
RItself.Because output B
1, B
2And B
3By termination, this capacitor filtering group has reduced the chain current i by capacitor filtering group 128
RHigh fdrequency component, so the output voltage between two lines is a yardstick of weighing pulse area.
With reference to figure 6 and 17, the detector 404 of error detector 402 receives the V from the voltage sensor part 410 of output transducer assembly 98
BmnOutput voltage sensor signal 408 between line.V
BmnSensor signal 408 is represented between the output line on the output node or terminal B
mAnd B
nBetween virtual voltage.MT-SL controller 400 can have a reference signal generator 412, and it produces the reference signal V of output voltage and electric current respectively
Bmn, REFAnd i
Bn, REFSignal generator 412 has a Voltage Reference part 414, and it produces a V
Bmn, REFOutput voltage waveforms reference signal 416.This V
Bmn, REFWith reference to main number 416 corresponding to output voltage waveforms between the line of a hope.On the other hand, output can be positioned at away from the position of converter 22 and can be an a kind of part of higher level controller (not shown) with reference to selector 412.
For the voltage source operation, that is to say for load 25 converters 22 to show as a voltage source that detector 404 makes switch 418 closures and switch 440 is opened.In this voltage source mode, by an adder unit 420 with V
Bmn, REFDeduct V in the reference signal 416
Bmn Sensor signal 408 is determined an E according to following formula
BmnOutput voltage error signal 422:
E
Bmn=V
Bmn, REF-V
BmnCan obtain every phase signals of three-phase voltage error signal 412, output voltage V between these adder unit 420 line takings from adder unit 420
B12, V
B23And V
B31Signal 408 respectively with V
B12, REF, V
B23, REFAnd V
B31, REFReference signal 416 poor.
For " voltage error modulation ", E
BmnOutput voltage error signal 422 signals 422 must be through the CL/PA modulated process.Because converter 22 is to provide load electric power according to output voltage pattern reference signal 422, so voltage error modulation ratio chain current impulse area modulation is more direct and more accurate.This voltage error modulator approach makes converter 22 show as a voltage source for load 25.
By utilizing the chain current impulse of high frequency, converter 22 can show as current source fast to load 25.Because converter can be designed to have a kind of modulating frequency, this frequency is higher than the frequency of output voltage or electric current widely, so the current source operation of converter 22 is possible.Though for utilizing current signal, 22 outputs of control change device make the output current error reduce to minimum, and still can applied voltage error modulation system.
For the current source operation, MTSL controller 400 is selected the output current reference signal by opening switch 418 and Closing Switch 440 from reference signal generator 412.Reference signal generator 412 also is that a current reference part 424 is arranged, and it produces an i
Bm, REFOutput current wave reference signal 426.This i
Bm, REFThe output current wave of a hope of expression, rather than an output voltage waveforms.Output transducer device 98 has a current sensor part 428, and its basis is at output node B
mOn line current produce an i
Bn Current sensor signal 430.
Figure 17 illustrates: when MTSL controller 400 was chosen in the current source mode and moves, the error-detecting circuit can comprise that a ratio adds difference quotient (" PD ") controller 432.PD controller 432 can get up to be implemented with software, combination of hardware, and is known as the technical staff in this area.This PD controller 432 has increased the response speed of precision and controller 398 widely.By small inductor device (marking) is plugged on output transducer device 98 and B
1, B
2, and B
3Can obtain the difference quotient part of PD controller 432 between the load end simply.Voltage between lines on the both sides of these inductors can be measured, and voltage difference can be determined so that the derivative signal of desirable line current directly is provided.
With reference to Figure 19, for example understand two node B for converter 22
1And B
2On voltage V
B12, utilize the effect of CL/PA modulator approach on online output voltage waveforms.Chain current impulse i
R, B12Diagram shows with at node B
1And B
2The relevant chain current impulse i of last output
RDistribute and distance.In Figure 19, also show reference voltage V
B12, REFSo that voltage between lines V is described
B12Follow the tracks of V
B12, REFThe mode of reference waveform.In Figure 19, also illustrated certain a bit at this moment E
B12Error.(2) input power factor control and the control of buffering inductive current
Second basic function of MTSL controller 400 is to flowing through L chain current impulse peak clamping
BThe i of buffer inductor 95
LBCurrent value.With reference to Figure 17 and 19, the input voltage error detector 406 of error detector 402 detects i by examining signal 442 according to one
LBThe error of electric current 96 is finished this second function.Reference signal 442 is represented the selective value of a damping current, and this damping telecommunications can be passed through an i
LBReference signal generator 444 is produced.Error signal 450 is provided for the information of Control Countermeasure needs so that select T
AmnThe input thyristor, the input thyristor is with the conveyer chain current i
RAbove-mentioned discussion has illustrated the T that selects output switch apparatus according to the voltage error modulator approach
BmnThe principle of thyristor.Be used to select T
AmnThe principle of input thyristor proves: except error signal is according to damping current and the input current waveform, can use a kind of similar modulator approach.
MTSL controller 400 is provided with reference current signal generator 442, and this generator 442 produces an i
LB, REFDamping current reference signal 444.This i
LB, REFReference signal 444 is corresponding to buffer current i
LBDesirable amplitude.It is also corresponding to chain current impulse i during F-mode operation (seeing Fig. 7)
RDesirable peak value.On the other hand, this damping current can be positioned on the position away from converter 22 with reference to selector 442, and can be an a kind of part of more high-grade controller (not shown).
Input voltage error detector 406 receives from i
LBAn i of current sensor 96
LBDamping current sensor signal 446.This i
LBL is flow through in 446 representatives of damping current sensor signal
BThe actual current i of inductor 95
LBDetector 406 has an adder unit 448, and it is used for by from i
LB, REFDeduct i in the reference signal 444
LBSensor signal 446 is so that determine an E according to following formula
LBError signal 450:
E
LB=i
LB，REF-i
LB
By control i
LBDamping current, chain current impulse i
RAmplitude can be controlled to any value i through selecting
LB, REFThe chain current i
RThe peak value that is restricted to a selection can help to reduce to be used for the rated value of each element of converter 22.
Detector 406 has a ratio and difference quotient (" PD ") controller 460, and this controller 460 can be as above-mentioned PD controller 432.This PD controller 460 has increased the accuracy and the response speed of controller 398.By small inductor device (not shown) being plugged on input pickup device 97 and input node A
1, A
2And A
3Between can obtain the difference quotient part of PD controller 460 easily.The voltage between lines of the both sides of these inductors can be detected and voltage difference can be determined so that the desirable derivative signal of line current directly is provided.PD controller 460 is representing the incoming line current i
A1, i
A2And i
A3Conditional input current signal 462 offer a current add apparatus 464 again.
Though reference signal generator 442 can comprise the current reference signal (not shown) that is similar to the reference signal that is produced by output reference signal generator 412, E
LBDamping current error signal 450 can be used to for each input current i
A1, i
B2And i
A3Synthesize i
B1, REF, i
B2, REFAnd i
B3, REFReference signal.
This synthetic input current reference signal is finished following two kinds of purposes simultaneously:
1. the buffer inductor current error is reduced to minimum value: and
2. be controlled at converter input node A
1, A
2And A
3On power factor.
Finish first purpose by the adder of detector 406.By the real component and the idle component of synthetic input current are finished second purpose that input power factor is controlled respectively.Meritorious reference signal for real component homophase or input current can be by V
AmnInput voltage sensor signal 456 obtains simply.Signal 456 multiply by E
LBError signal 450 is so that reduce to error signal 450 minimum value simultaneously and set up a reference signal 468 that is used for the homophase of input current.Idle reference signal for the idle component of out of phase or input current reference is mainly set up by the reference signal 468 of homophase is offered a phase shifting equipment 470.This phase shifting equipment 470 makes 90 ° of reference signal 468 phase shifts of homophase so that produce a reactive current reference signal 472.Signal 472 with variable gain amplifier 474 receptions of adjustable gain COEFFICIENT K from phase shifter.This amplifier gives signal 472 gain coefficient K so that be that adder unit 464 produces the reactive current reference signal 476 of an amplification.By adjusting the value of gain coefficient K control input power factor to a selection.For example, the gain coefficient K by amplifier 474 is set to zero and can be implemented in that power factor equals 1 on the input of converter 22.
By the sensor signal 456 of the actual input voltage of representative is provided for adder 464, synthetic signal 462,468 and 476 is used for input voltage error-detecting logical circuit.This logical circuit provides an output signal for the input voltage detector 406 that comprises an input voltage error signal 478, and this output signal is the output of adder unit 464.Therefore, when closed and switch 418 was opened when mode switch in current source 440, the error originated from input of detector 406 detected logical circuit and is similar to and detects 404 output errors detection logical circuit.Yet, because sensor signal 456 and 458, and the buffer current i through selecting
LB, input voltage error detector 406 includes the information of the power factor on the input that is controlled at converter 22.By comprising that between adder unit 448 and multiplier 466 ratio, integration and a difference quotient (" PID ") controller (not shown) can improve the response of damping current control.The design of PID controller is known for the technical staff in this area.B. chain current impulse trigger
400 second tasks of MTSL controller are to start to trigger a new chain current impulse i
RWith reference to figure 6, MTSL controller 400 has a chain current impulse triggering pilot controller part or trigger 480 is used to produce enabling signal 482.This enabling signal 482 is provided for USGL controller 500 so that start new chain current impulse i of triggering by several other ones of MTSL controller 400
R
The duration of enabling signal 482 control zero current sections, promptly be used for S
IThe triggering of the Continuity signal of switch 88.As shown in FIG. 7, at time t
3The time, the T of switching device 40,50
AAnd T
BThyristor is switched on through Zero voltage transition (ZVS).When the chain current i
RAlong with electric current flows through T
AAnd T
BThyristor (being also referred to as the beginning of triggering or I-pattern) is when beginning to increase, at time t
4Last Z-pattern finishes.Preferably the duration of Z-pattern is at least than T
AAnd T
BThe turn-off time of thyristor is longer, because the Z-pattern is from the shutoff of these main thyristors.
In order to keep the high efficiency that is not less than under the full load service conditions, the duration of zero current section (Z-pattern) can decide on the maximum of input and output voltage error signal 478,422, and these error signals are input signals of trigger 480.For example, zero current section (Z-pattern) then duration can be adjusted as long as output and error originated from input signal 422,478 are retained in the threshold level that is lower than a selection and just can not produce new chain current impulse.C. chain current impulse distributor
The 3rd task of MTSL controller 400 is: for a heterogeneous input, at input node A
1, A
2, A
3To between distribution claim current impulse i
RWith at output node B
1, B
2, B
3To between distribution claim current impulse i
RWith reference to figure 6, MTSL controller 400 has chain current impulse distributor pilot controller part or distributor 484, and this distributor receives from the enabling signal 482 of exciter part 480 with from the error signal 422 and 476 of error detector 402.
According to these input signals and the definite circuit through selecting, distributor 484 is determined on a pair of input node and each the chain current impulse i on a pair of output node
RDistribution.Node of distributor 484 generations selects signal 486 to indicate by fixed that a pair of input and output node of distributor will transmit pulse i
RRealize that this to utilize the logic of the equivalent structure of comparator and they be known for the technical staff in this area.
Distributor 484 is the first steps in a kind of main thyristor system of selection, this method be used for selector switch device 40,50 which to T
AAnd T
BThyristor is with conveyer chain current impulse i
RFor example, if distributor is determined a pair of output node B
2And B
3With the conveyer chain current impulse, can select a pair of in two pairs of thyristors to come to transmit pulse i so by output switch apparatus
RFor example, promptly can pass through a pair of T
B21And T
B32Thyristor 52,56 also can pass through a pair of T
B22And T
B31Thyristor 55,53 offers a pair of output node B to electric current
1And B
2Another pilot controller (below will describe) is carried out one second and last step (the 4th task of MTSL controller 400) of main thyristor system of selection, and which selects will be pulse i to thyristor
RSend node B to
2And B
3
Select the input and output node to using various definite circuit by distributor 484.For example, for a kind of heterogeneous converter, this distributor 484 can utilize a maximum voltage error information.Under a maximum voltage error information, the output node B that distributor 484 selections have the maximum voltage error
1, B
2Or B
3, and the T of output switch apparatus 50
BThyristor is triggered so chain current impulse i
RFlow through node through selecting.The node that can determine to have the maximum voltage error by the output of the output voltage error signal 422 of detector 404.
Distributor 484 also can utilize a maximum voltage error criterion to control the T of input switch device 40
AThe triggering of thyristor, thereby pulse i
RSelecteed input node A flows through
1, A
2Or A
3Utilize the input voltage error signal 478 that produces by detector 406 to determine which input node has maximum voltage error by distributor 484.
According to the voltage law of Kirchhoff, the summation of input voltage between lines is that the summation of zero-sum output voltage between lines is zero.Therefore the summation of voltage error signal is zero on output, and similarly the summation of the voltage error signal on input also is zero.Because chain current impulse i
RFlow through C
AInput filter condenser device 26 and flow through C
BOutput filter capacitor device 28 is so maximum voltage error criterion side by side makes voltage error reduce to minimum value.D. chain current impulse road electrical equipment
The 4th task of MTSL controller 400 is the final steps in the main thyristor system of selection, this method be used to select input switch device 40 which to T
AThe a pair of T of that of thyristor and output switch apparatus 50
BThyristor is with conveyer chain current impulse i
R, with reference to figure 6, MTSL controller 400 has a chain current impulse router pilot controller part or router four 88, and this router four 88 is used to select T
AAnd T
BThyristor is right, and these thyristors are to will be pulse i
RSend to respectively by distributor 484 selected input and output nodes.Router four 88 produce that a thyristor is selected signal 490 in case indication by router determined which will transmit pulse i to the input and output thyristor
RSelect main thyristors to so that relative reference voltage reduces the error of virtual voltage by router four 88, as by error detector 402 determined reference voltages.
Can utilize various selection circuit and select the input and output main thyristor right by router four 88.For example, for a kind of heterogeneous interchanger, router four 88 can use filtering capacitor charging criterion, this criterion be based on judgement about whether filter 26 and 28 capacitor by new chain electric current stream pulse i
RCharge or discharge.This criterion can be based on the symbol of voltage error, the pulse i of the filter capacitor of flowing through
RDirection according to thyristor being realized by road electrical equipment 488 selected those.Because chain current impulse string is an one pole, so flowing through the direction of hope of the chain current impulse of filtering capacitor 26 and 28 is set up by single-way switch, this feature is different from conventional series resonant converter, and the chain electric current (AC) that this routine converter needs bidirectional switch to adapt to alternate flows.
Consider above-mentioned example, wherein distributor 484 is selected output node B
2And B
3To coming the conveyer chain current impulse, because at output node B
2And B
3On line between output voltage V
B23Remaining two the voltage (V of error ratio
B31And V
B12) error higher.Road electrical equipment 488 can be selected T
B21And V
B3252,56 pairs of thyristors also can be selected T
B22And T
B3155,53 pairs of thyristors come pulse i
RSend node B to
2And B
3If be connected on the voltage V on these leads
B23Be positive, but less than V
B23, REFReference voltage signal 416 (Figure 17), C so
B Output filter capacitor 38 must be recharged so that reduce voltage error, given chain current impulse i
RDirection be when pointing to load 25, road electrical equipment 488 is selected T
B21And T
B32If 52,56 pairs of thyristors are voltage between lines V
B23Greater than V
B23, REFReference signal 416, C so
BFiltering capacitor 38 need be discharged and select another to thyristor promptly by road electrical equipment: T
B22And T
B32Thyristor 55,53.Usually, if voltage error E
B23=V
B23, REF-V
B23Symbol be positive number, road electrical equipment 488 is selected T so
B21And T
B32This is to thyristor 52,56.Otherwise road electrical equipment 488 is selected second couple of thyristor T
B22And T
B31
Basically router four 88 is determined the route of chain electric current so that reduce error according to the symbol of voltage error signal, for example, and error E
B12E
B12V between the symbol of error signal 422 and line
B12The symbol of output voltage sensor signal 408 indicates whether to need to give load end B
1And B
2Provide energy or from load end B
1And B
2Extract energy as shown in Figure 19, as one pole chain current impulse i
RFor node B
1And B
2Distribution, timing and route be pulse i with respect to as shown in Figure 19
R, B12The time, actual output voltage V
12Follow reference voltage V
B12, REF
In a word, one pole chain current impulse i
RCan be at output node B
1And B
2Go up and determined route two-wayly.For example, select T
B11And T
B22Thyristor 51,55 is output node B
1And B
2Determine the chain current i
RIf route force the chain electric current along with select T
B21And T
B12The direction that the current direction of thyristor 52,54 is opposite flows.As a result, depend on the chain current impulse i that flows through output switch apparatus
R, B12Route, output voltage V 12 can increase also as shown in Figure 19 and can reduce.
In the converter design of reality, use the quantity of chain current impulse to be far longer than in the quantity shown in Figure 19, in Figure 19 in order to illustrate that CL/PA modulation methods ratio juris has been simplified.Utilize a large amount of pulses, promptly high chain power frequency, actual output voltage present the waveform near sine level and smooth and that have low harmonics distortion.To heterogeneous output, utilize more chain current impulse i
R, many to output node because these pulses can be assigned to.For the three-phase inverter among Fig. 1 22, one pole chain current impulse i
RBe assigned to three different chain current impulse paths:
1. be used for node, B
2And B
3I
R, B23
2. be used for node B
3And B
1I
R, B31With
3. be used for node B
1And B
2I (Figure 19)
R, B12
Though utilize hardware, software or the known equivalents structure that hardware and software combines can be realized router four 88 by the technical staff in this area, but realize that by digital logic element the logical circuit of router four 88 is best, this is known for a person skilled in the art, the T that router four 88 can utilize identical filtering capacitor charging criterion and error calculation method to select input switch device 40
AmnThyristor is right.E. select chain driving voltage (V
LD) limiter
The 5th task of MTSL controller 400 is preferably only when wishing to be used for next chain current impulse i
RChain driving voltage V
LDBe performed when surpassing a maximum voltage limit through selecting.The chain driving voltage V of restriction
LDBe controlled at the voltage strength on the thyristor in the input and output switching device 40,50 on the chain member.With reference to figure 6, MTSL controller 400 has a chain driving voltage limiter pilot controller part or chain voltage limitator 492 is finished this function.Limiter 492 produces the startup of a restriction and selects signal 494, and this signal 494 is provided for USGL controller 500 as an input.The original selection of being undertaken by distributor 484 and router four 88 of thyristor can be replaced by chain demand limiter 492, and does not reduce the effect of output voltage waveforms shaping and chain current clamp function significantly.
The principle of the most preferred embodiment that chain demand limiter 492 will be described is discussed below.
Passing through converter 22 energy-delivering methods all T of switching device 40,50 from the one-period of chain current impulse to one-period
AAnd T
BThyristor is subjected to certain blocking voltage, and all chain members also are subjected to certain voltage, and the maximum of these voltages has determined the voltage rating of these rod changer assemblies.The V of these maximums and power supply 24 and load 25
LL, maxMaximum voltage between lines is directly proportional, and also with C
RV on resonant capacitor 64 two ends
CR, maxMaximum voltage is directly proportional.
For example, to three-phase AC-AC series resonant converter 22, the T on switching device 40,50
AOr T
BA V on the thyristor two ends
BBMaximum back bias (negative electrode is to anode) is provided by following formula under worst case:
V
BB，max=V
LL，max+(V
LD，max+V
CR，max)／4
The V of resonant capacitor voltage
CR, maxMaximum occurs in Z as shown in Figure 7
sDuring-the pattern, and provide by following formula:
V
CR，max=V
LD，max+Z
RI，Ri
R，max
I wherein
RBe the chain current impulse, Z
RI, RBe by L
R, C
RAnd L
1The characteristic impedance of the resonant circuit that constitutes, and Z
RI, R=[(L
R+ L
I)/C
R]
+ 1/2(seeing Figure 14)
By control buffer current i
LBCome i
RMaximum adjust to a relevant needed peak value of maximum current that is absorbed with load.By Quality Initiative driving voltage V
LDControl i
LBElectric current.Therefore, consider above-mentioned two kinds of relations, by restriction chain driving voltage V
LDMaximum obviously can reduce the T of switching device 40,50
AAnd T
BThe voltage rating that thyristor is required and the voltage rating of all chain components.
1 converter with reference to the accompanying drawings is by V
AAnd V
BBusbar voltage (V
LD=V
A-V
B) difference can be identified for next pulse i
RV
LDThe chain driving voltage.Can determine V by utilizing transducer 452 and 410 (Figure 17-18) on input and output side, to measure voltage between lines
AAnd V
BBusbar voltage.
For under all service conditionss effectively control, under normal and improper service conditions, by limiter 492 V
LDVoltage limit to one maximum.Can utilize several diverse ways control V by limiter 492
LDMaximum.In conjunction with the power-balance formula that is used for converter 22 these methods are described.
With reference to figure 7, during the non-zero current pulse section when power is transmitted by chain, chain driving voltage V
LD=V
A-V
BCan be assumed that and be actually because the result of filtering capacitor 26 and 28.The power-balance formula that electric current obtains being used for the non-zero current section of any single chain current impulse is multiply by on the both sides of this formula: according to:
P
LD=P
A-P
B
Wherein:
P
LD=V
LDi
R=by damping circuit device L
BInstitute's power absorbed;
P
A=V
Ai
R=the power that produces by power supply: and
P
B=V
Bi
R=by the load power absorbed.
Because each unidirectional chain current impulse i
RFlow in the same direction to conductor 66 with conductor 65, so always positive at the above-mentioned power-balance formula medium chain electric current that provides.By selecting some T of input switch device 40
AThyristor comes the conveyer chain current impulse, can control busbar voltage V
AFor positive, negative or be zero.
When selecting T
AThyristor is busbar voltage V thus
AWhen being positive, P so
ABe positive, and power supply 24 produce powers.If select T
AThyristor and make V
ABear, so P
ABe similarly negative and absorb energy by power supply 24.Equal 1,2 or 3 for K, can select T
AThyristor is so that by triggering a pair of thyristor T
AK1And T
AK2Make the chain short circuit on input switch device 40.If chain on input switch device 40 by short circuit, V so
ABusbar voltage is zero, P
AAlso be zero, and prevent that power supply 24 from participating in the energy transport process.
Same, if select the T of output switch apparatus 50
BmnThyristor comes the conveyer chain electric current, thereby V
BBusbar voltage and P
BBe positive, negative or zero.Load 25 absorbs energy, produce power accordingly so, or is prevented from participating in the energy transport process.Therefore,, descend K to equal 1,2 or 3 relatively, by triggering thyristor to T for output switch apparatus 50
Bk1And T
Bk2If the maximum voltage between lines for example on the input and output side of converter 22 is selected is that every unit is 1.0p.u, so can be driving voltage V by the chain short circuit current of handle on input switch device 40 or output switch apparatus 50
LDBeing restricted to per unit is 1.0p.u.
In the average energy of transmitting by converter 22, four kinds of energy delivery states can take place, i.e. two kinds of normal states and two kinds of improper states.In normal energy delivery state, first state is the energy delivery state of forward, and power supply 24 produces the energy that is absorbed by load in this state.Under the situation that this first kind of forward energy transmitted, P
A, V
A, P
BAnd V
BAll be positive.Second kind of normal energy transmit mode is a kind of backward energy transmit mode, and power supply 24 absorbs the energy that is produced by load 25 during this state.Under the situation that second kind of backward energy transmits, P
A, V
A, P
BAnd V
BAll bear.Because the chain driving voltage is defined as V
LD=V
A-V
BAnd because V
AAnd V
BValue be restricted to the maximum (by making brilliant brake gear 40,50 short circuits of input and output) of 1.0p.u, so under the first and second normal energy transmit modes, chain driving voltage V
LDAlso be restricted to the 1.0p.u maximum.
In two kinds of improper energy delivery states, first kind of abnormal condition takes place when power supply 24 and load 25 produce powers, and when power supply 24 and load 25 absorption energy second kind of abnormal condition takes place.For these positive deadly conditions, P
AAnd P
BBe opposite on symbol, and so busbar voltage V
AAnd V
BSame is opposite on symbol.Work as V
AAnd V
BWhen busbar voltage has opposite symbol, be driven voltage V
LD=V
A-V
B, reach a maximum 2.0p.u in the worst case.
Fortunately be, if V
LDBe limited to a maximum and for example be 1.0p.u, can not recruit the greater loss of system control.During this improper energy delivery state, work as V
LDT by selector switch device 40,50 in the time of may surpassing 1.0p.u
AAnd T
BThyristor is so that force V
AOr V
BBusbar voltage is the zero V that prevents
LDVoltage surpasses this maximum.This prevents that step from can realize with three kinds of diverse ways.
At first, consider this improper situation, wherein power supply 24 and load 25 produce powers, so V
ABe positive and V
BBear.In this case, chain driving voltage V
LDBe positive, it also makes i according to following formula
LBDamping circuit device electric current increases:
L
B(di
LB／dt)=V
LD
Yet, in order to increase i
LBElectric current needn't make power supply 24 and load 25 both produce powers.Force i
LBThe second way that electric current increases needs the T of selector switch device 40.50
AAnd T
BTherefore some thyristor of thyristor has only power supply 24 produce powers, and load is participated in energy transfer process by short circuit so that prevent it.In this case, V
ABe positive, V
BBe zero, because V
LDRemain positive, so it forces i
LBElectric current increases.
At last, in order to force i
LBThe third possibility that group Buddhist nun inductor current increases is to force load 25 produce powers, and power supply 24 is participated in energy transfer process by short circuit so that prevent it.
Same, during any special chain current impulse, can force i with three kinds of methods
LBDamping circuit device electric current reduces:
1. force power supply 24 and load 25 all to absorb energy;
2. force power supply 24 to absorb energy, participate in energy transfer process so that prevent it and make load 25 short circuits: and
3. force load 25 absorption energy and make power supply 24 short circuits participate in energy transfer process so that prevent it.
Work as V
LDBe to increase or reduce i in the time of may surpassing 1.0p.u
LBElectric current is because any method in these three kinds of methods can prevent V
LDSurpass 1.0p.u, so if MTSL controller 400 is only used second kind and the third method, and without first method, so to i
LBNot very big loss of the control of damping circuit device electric current.Thereby, in order to control i
LBAnd V
LD, preferably force power supply 24 or load 25 to produce or the absorption energy, and another is by short circuit.In chain voltage limitator 492, can realize this logical circuit with hardware, software or with known hardware and software is combined of the technical staff in this area.Select T by router four 88
AAnd T
BAfter the thyristor, limiter 492 is checked chain driving voltage V
LD=V
A-V
BThe value that is produced.If V
LDVoltage surpasses 1.0p.u, and limiter 492 makes the chain short circuit change T by the thyristor that is used on input switch device 40 or the output switch apparatus 50 so
AAnd T
BSelection course, this short circuit forces V respectively
AOr V
BBe zero.Therefore, limiter 492 restriction chain driving voltage V
LDIn order to avoid surpass the maximum of 1.0p.u, thereby for chain component and main T
AAnd T
BThe overvoltage infringement of thyristor is prevented from making the resonant capacitor voltage clamp.
Figure 20 has illustrated the converter 22,100,200 among Fig. 1,2,3,4 and 5 and the alternative embodiment of 300 chain part, and it can be plugged between the input and output switching device.For example, with reference to figure 1, converter 22 can comprise a voltage clamp device bilateral and non-loss, as one
VCR Voltage clamping circuit 600, this clamp device and C
R Resonant capacitor 64 is connected in parallel.
Thereby in order to comprise clamp circuit 600, the circuit of converter 22,100,200 or any most preferred embodiment of 300 does not promptly need modification, and chain component and it interconnect and does not also need modification.Though clamp circuit 600 is illustrated as a device that separates with synthesizer 70, it is evident that synthesizer of the present invention can be configured and comprise this clamp circuit 600.Except the protection voltage limit feature of chain driving voltage limiter 492, clamp circuit 600 is limited in all switches and the needed voltage rating of thyristor that uses in the converter 22.
V
BB，max=V
LL，max+(V
LD，max+V
CR，max)／4
V wherein
LL, maxIt is maximum voltage between lines.
Preferably the clamp of resonant capacitor voltage is bilateral.That is to say that clamp circuit 600 is V
CRThe positive polarity of voltage and negative polarity clamp.Because resonant capacitor voltage V during the Z-pattern of operation
CRReach a positive peak and at F
sReach a negative minimum during the-pattern, as shown in FIG. 7, so bilateral clamp is by preferred.
Comprise V in order to illustrate
CRThe favourable part of voltage clamping circuit 600 is considered the maximum voltage between lines V on the input and output side of converter 22
LL, maxBe 1.0p.u, and maximum chain current i
RAlso for 1.0p.u. changes (ZCS) in order to guarantee Zero voltage transition (ZVS) and/or zero current, and in order to cause at i
LBFluctuation in the damping circuit device electric current can the selectivity characteristic impedance, for example, and Z
R, R=1.3p.u and Z
RI, R=1.5p.u.Given these values and do not have voltage clamping circuit 600, the maximum of resonant capacitor voltage will reach:
V
CR, max=+2.5p.u is at Z
sDuring-the pattern; With
V
CR, max=-2.3p.u is at F
sDuring-the pattern, suppose to include the chain driving voltage limiter 492 of Fig. 6 so that V
LDThe chain driving voltage is restricted to the maximum of 1.0p.u.Yet in order to produce chain current impulse iR well and the suitable converter that passes through transmits energy, resonant capacitor voltage V
CROnly can be limited to than the bigger a little value of 1.0p.u so that be the T in the switching device 40,50
AAnd T
BThyristor obtains an enough back bias voltage.For example, if the maximum voltage between lines of 1.0p.u is corresponding to the effective value voltage of a 480V, so resonant capacitor voltage V
CR, maxMaximum to be restricted to 1.3p.u be enough.
To illustrate below with voltage clamping circuit 600 V
CRThe resonant capacitor voltage clamp is this principle that is worth to 1.3p.u.Consider with the polarity shown in Figure 20 C
CCapacitor 614 is pre-charged to the dc voltage V of a 1.3p.u through selecting
CC
The curve of Fig. 7 illustrates: during the Z-pattern, and resonant capacitor voltage V
CRRise to a maximum on the occasion of.Along with V
CRReach 1.3p.u, D
P1And D
P2Diode 606 and 608 beginning conductings, it makes C
CDamped capacitor 614 is resonant capacitor voltage V
CRClamp.Similarly, owing to resonant capacitor voltage V during the I-formula
CRBe reduced to a negative minimum value, work as V
CRReach the V of 1.3p.u
CCDuring damped capacitor voltage, R
N1And D
N2Diode 602 and 604 beginning conductings.Work as V
CRThe amplitude of resonant capacitor voltage is during less than 1.3p.u, because all diodes of clamp circuit 600 are in the current blocking state basically, so clamp circuit 600 is automatically inoperative.
When passing through damped capacitor voltage V
CCMake resonant capacitor voltage V
CRDuring clamp, C
CDamped capacitor 614 is in fact by C
R Resonant capacitor 64 charges, and too much time V
CCCan rise to a unacceptable voltage level.S
D1And S
D2Discharge switch 610 and 612 has been avoided this damped capacitor voltage, and this damped capacitor voltage is to work as Z
t(see figure 7) was at t when pattern began
1t
2The time closed S
1Before the switch 88 or with closed S
1Closing Switch produced switch 88 simultaneously.In fact discharge switch 610 and 612 closure occur in zero switching voltage (ZVS).Work as S
D1And S
D2When switch 610 and 612 closures, C
CThe V of capacitor 614
CCVoltage is discharged into L
BIn the damping circuit device 95. Discharge switch 610 and 612 can remain closed up to damped capacitor C
CSelected voltage level be resumed till, be 1.3p.u at this.Turn-off S
D1And S
D2Switch occurs in zero switching voltage (ZVS) once more, so that be released in resonant capacitor voltage V
CROn clamp.At this very moment, the further characteristic of this converter can be with top the same in conjunction with the described characteristic of Fig. 7.Advantage
Converter of the present invention, particularly equally matched with the static converter of previous form on expense by the illustrated converter of the converter 22,100,200 and 300 of Fig. 1-4, static converter is not generally taken into account the feature that series resonant converter arouses attention.These features comprise: two-way and four-quadrant serviceability, from low pressure to high pressure transmitted power (boosting mode operation), produce sinusoidal output voltage that is not subjected to the balance that unbalanced load influences and the dynamic change of allowing supply voltage.
Converter from Fig. 1-4 relatively, obvious converter of the present invention can be advantageously with DC or the single-phase input power of AC, or heterogeneous input power transform DC or single-phase power output of AC or heterogeneous power output.
As another advantage, converter of the present invention can be reduced as the peak value of chain current impulse minimum and can control it.Chain current impulse peak value is reduced to minimum value compares with previous converter and has reduced the expense of all rod changer assemblies widely.For example, under the condition of full load operation, converter of the present invention can peak limiting and the ratio of the mean value of chain current impulse; Therefore, only surpass n/one of a unit at this quantitative values of whole pulse period, rather than resemble experience by previous converter be a multiple.
As another advantage, converter of the present invention can make that needed switch number in input and output switching device 40,50 reduces to minimum in traditional full wave bridge type series resonant converter.Therefore, converter of the present invention has used most economical effective switch in device 40,50, that is: unidirectional, single T
AAnd T
BThyristor, rather than expensive controlled stopcock or bidirectional switch, this bidirectional switch comprise that the single-way switch of reverse parallel connection or differential concatenation connection is right.In addition, in order to prevent the irregular thyristor conducting that makes, the converter of the present invention series connection saturated inductor of need between the input and output switch, not pegging graft, this inductor is that the bidirectional switch of previous full-bridge and half-bridge converter is needed.
Because the voltage rating of switch and energy-storage travelling wave tube is reduced to minimum value, so converter of the present invention is configured than previous converter more economically.For example, among the embodiment in Figure 20, converter of the present invention can satisfy loss-free design standard by the maximum voltage on the restriction resonant capacitor two ends.This limited features also is restricted to n/one who inputs or outputs voltage between above-mentioned max line to maximum blocking voltage, rather than resembles and be the multiple of above-mentioned voltage the previous converter.
The method that the present invention also provides a kind of power controlling to flow, promptly at a power supply 24, unidirectional or two-way flow of power between 124 or 224 and loads 25,125 or 325, described method can guarantee the conversion loss of minimum by utilizing zero current conversion (ZCS) or Zero voltage transition (ZVS) for all converter switches.
Method of the present invention provides the flexibility control of chain current impulse characteristic, and it comprises the width of pulse height, pulse duration and each pulse period, that is to say, the width of the zero-sum non-zero section in each cycle is controlled.This flexibility method can advantageously be used to keep the high efficiency of converter when converter is being lower than operation under the condition of full load.
Illustrated and described principle of the present invention according to several preferred embodiments.It is evident that for the technical staff in this area: the present invention can carry out modification to its structure and part on the basis that does not break away from this principle.For example, can use the chain electric current of other structure synthetic 1070 and 270, and the MTSL of other structure and USGL controller, input and output transducer, filter and switching device.I require all these modification to belong within the hold in range and spirit of following claim.
Claims (72)
1. Unipolar series resonant converter that is used for positive energy exchange between first and second circuit comprises:
First and second switching devices, they and corresponding first and second circuit connection;
A resonant circuit that is connected between first and second switching devices, this resonant circuit have a resonant capacitor and a resonant inductor, and they are connected in series; With
A chain electric current synthesizer that is of coupled connections with this resonant capacitor, synthesizer control signal that is used to produce a chain electric current of this synthesizer response, this chain electric current comprises the current impulse of a series of one pole chain, described chain electric current is the electric current that flows to described second switch device from described first switching device through described resonant circuit, this synthesizer has a blocking swtich that is connected in series with resonant capacitor, and it is used for exciting each one pole chain current impulse to make the resonant circuit nonoscillatory.
2. according to the Unipolar series resonant converter of claim 1, it is characterized in that: chain electric current synthesizer comprises at least one switch, and a switch conduction is arranged at most during energy exchange.
3. according to the Unipolar series resonant converter of claim 2, it is characterized in that: chain electric current synthesizer comprises at least one inductor element, and it is used for changing each synthesizer switch when at least a situation of zero current and no-voltage.
4. according to the Unipolar series resonant converter of claim 2, it is characterized in that: further comprise a nothing power consumption voltage clamp device that is connected in parallel with resonant capacitor, it is used to limit the voltage of each converter switches.
5. according to the Unipolar series resonant converter of claim 4, it is characterized in that: the voltage clamp device comprises: a bridge circuit device, this bridge circuit device is made up of the controlled discharge switch that each diode of first pair of diode, second pair of diode and a pair of and second pair of diode is connected in parallel, with a DC damped capacitor that is connected with the bridge circuit device, this Biodge device and resonant capacitor are connected in parallel.
6. according to the Unipolar series resonant converter of claim 1, it is characterized in that: blocking swtich comprises a thyristor, and this thyristor is turn-offed by natural commutation by resonance oscillations.
7. according to the Unipolar series resonant converter of claim 1, it is characterized in that: each all comprises the thyristor bridge circuit first and second switching devices.
8. according to the Unipolar series resonant converter of claim 7, it is characterized in that: this converter further comprises a controller that is used for the generator gate signal, this gate signal is used for making the thyristor conducting of first and second switching devices and is turn-offed by natural commutation by resonance oscillations when no-voltage and zero current.
9. according to the Unipolar series resonant converter of claim 1, it is characterized in that: synthesizer comprises at least one diode and at least one discharge switch, and each diode produces conducting when no-voltage, and each discharge switch is switched on and turn-offs when no-voltage.
10. according to the Unipolar series resonant converter of claim 1, it is characterized in that: chain electric current synthesizer comprises a chain electric current damping device that is connected with synthesizer, and it is used to make chain current impulse clamp.
11. the Unipolar series resonant converter according to claim 1 is characterized in that: further comprise:
A plurality of transducers, they are used to monitor the electric current and the voltage of the chain electric current and first and second circuit, and these transducers produce the sensor signal of these monitoring targets of response; With
The controller of a response sensor signal, it is used to produce synthesizer control signal.
12. the Unipolar series resonant converter according to claim 1 is characterized in that: further comprise a saturated inductor, an element connected in series in this saturated inductor and the set of pieces of forming by resonant inductor and blocking swtich.
13. the Unipolar series resonant converter according to claim 1 is characterized in that: the resonant circuit and first and second switching devices are connected in series.
14. the Unipolar series resonant converter according to claim 1 is characterized in that:
Each comprises a bridge circuit device of being made up of a plurality of thyristors first and second switching devices, gate signal of each thyristor response;
First and second filters and corresponding first and second circuit connection;
Blocking swtich comprises a thyristor that is turn-offed by natural commutation by resonance oscillations;
Chain electric current synthesizer comprises:
At least one discharge switch, discharge switch conducting at the most during energy exchange, each discharge switch turn-on and turn-off when no-voltage:
At least one diode, each diode produces conducting when showing no-voltage in fact;
A chain electric current damping device that is connected with synthesizer: and
At least one inductor element, it is used for when no-voltage and changes each synthesizer switch during at least a situation during zero current;
Converter also comprises a nothing power consumption voltage clamp device that is connected in parallel with resonant capacitor, it is used to limit the voltage of a plurality of converter switches, this voltage clamp device comprises a bridge circuit device and a DC damped capacitor, this bridge circuit device is by first pair of diode, second pair of diode, form with a pair of controlled discharge switch that is connected in parallel with each diode second pair of diode, and the DC damped capacitor is connected with clamp bridge circuit device, and this bridge circuit device and resonant capacitor are connected in parallel; With
Converter further comprises a controller that is used for the generator gate signal, and this gate signal makes the thyristor conducting of first and second switching devices when being used for no-voltage and zero current actually, and is turn-offed by natural commutation by resonance oscillations.
15. the Unipolar series resonant converter according to claim 14 is characterized in that: the resonant tank and first and second switching devices are connected in series.
16. the Unipolar series resonant converter according to claim 1 is characterized in that: the resonant circuit and first and second switching devices are connected in parallel.
17. the Unipolar series resonant converter according to claim 16 is characterized in that:
First and second circuit comprise the grounding system of a shared common neutral current potential;
Converter further comprises: the first short circuit thyristor, and it is used for selectively resonant circuit being connected with the neutral point current potential and second short circuit thyristor, and it is used for selectively blocking swtich being connected with the neutral point current potential.
18. the Unipolar series resonant converter according to claim 1 is characterized in that:
First circuit comprises a DC system with two conductors;
Converter further comprises one first termination capacitor device filter, and it is connected between two DC conductors of first circuit; With
First switching device comprises first thyristor that the DC conductor of and first circuit is connected in series: and one be connected two fly-wheel diodes between the DC conductor.
19. the Unipolar series resonant converter according to claim 1 is characterized in that: first circuit comprises that an AC system and first switching device comprise:
A diode bridge device, it has two the DC outputs and an AC input that is connected with first circuit that have two DC bridge output conductors;
One first termination capacitor device filter, it is connected between two bridge output conductors;
First thyristor that is connected in series with a bridge output conductor, and one be connected two fly-wheel diodes between the bridge output conductor.
20. a Unipolar series resonant converter that is used for positive energy exchange between first and second circuit comprises:
First and second switching devices, they and corresponding first and second circuit connection;
A resonant circuit that is connected between first and second switching devices, this resonant circuit have a resonant capacitor and a resonant inductor, and they are connected in series; With
A chain electric current synthesizer that is connected with this resonant capacitor, synthesizer control signal that is used to produce a chain electric current of this synthesizer response, described chain electric current is the electric current that flows to described second switch device from described first switching device through described resonant circuit, this chain electric current comprises the current impulse of a series of one pole chain, each pulse comprises a non-zero current section and the adjacent pulse of being separated by a zero current section, and zero-sum non-zero current section is controllable in the duration; With
A blocking swtich of connecting with resonant capacitor.
21. the Unipolar series resonant converter according to claim 20 is characterized in that: chain electric current synthesizer 10 comprises at least one switch, switch conduction at the most during energy exchange.
22. the Unipolar series resonant converter according to claim 21 is characterized in that: chain electric current synthesizer 10 comprises at least one inductor element, changes each synthesizer switch when it is used at least a situation when no-voltage and zero current.
23. the Unipolar series resonant converter according to claim 21 is characterized in that: further comprise a nothing power consumption voltage clamp device that is connected in parallel with resonant capacitor, it is used to limit the voltage of each converter switches.
24. Unipolar series resonant converter according to claim 23, it is characterized in that: the voltage clamp device comprises: a bridge circuit device, this bridge circuit device is by first pair of diode, second pair of diode, form with a pair of controlled discharge switch that is connected in parallel with each diode second pair of diode, with a DC damped capacitor that is connected with the bridge circuit device, this bridge circuit device and resonant capacitor are connected in parallel.
25. the Unipolar series resonant converter according to claim 20 is characterized in that: blocking swtich comprises a thyristor that is turn-offed by natural commutation by resonance oscillations.
26. the Unipolar series resonant converter according to claim 20 is characterized in that: each all comprises the thyristor bridge circuit first and second switching devices.
27. Unipolar series resonant converter according to claim 26, it is characterized in that: this converter further comprises a controller that is used for the generator gate signal, this gate signal makes the thyristor conducting of first and second switching devices when being used for actually no-voltage and zero current and is turn-offed by natural commutation by resonance oscillations.
28. Unipolar series resonant converter according to claim 20, it is characterized in that: synthesizer comprises at least one diode and at least one discharge switch, to producing conducting, and each discharge switch is switched on and turn-offs when no-voltage each diode in no-voltage.
29. the Unipolar series resonant converter according to claim 20 is characterized in that: chain electric current synthesizer comprises a chain electric current damping device that is connected with synthesizer, and it is used to make chain current impulse clamp.
30. the Unipolar series resonant converter according to claim 20 is characterized in that, further comprises:
A plurality of transducers are used to monitor electric current and the voltage of chain electric current with first and second circuit, and these transducers produce the sensor signal of these monitoring targets of response; With
The controller of a response sensor signal, it is used to produce synthesizer control signal.
31. the Unipolar series resonant converter according to claim 20 is characterized in that: further comprise a saturated inductor, an element connected in series in this saturated inductor and the set of pieces of forming by resonant inductor and blocking swtich.
32. the Unipolar series resonant converter according to claim 20 is characterized in that: the resonant circuit and first and second circuit are connected in series.
33. the Unipolar series resonant converter according to claim 20 is characterized in that:
Each comprises a bridge circuit device of being made up of a plurality of thyristors first and second switching devices, gate signal of each thyristor response;
First and second filter apparatus and corresponding first and second circuit connection;
Blocking swtich comprises a thyristor that is turn-offed by natural commutation by resonance oscillations;
Chain electric current synthesizer comprises:
At least one discharge switch, discharge switch conducting at the most during energy exchange, each discharge switch turn-on and turn-off when no-voltage;
At least one diode, each diode produces conducting during no-voltage actually;
A chain electric current damping device that is connected with synthesizer; With
At least one inductor element, it is used for when no-voltage and changes each synthesizer switch during at least a situation during zero current;
Converter also comprises a nothing power consumption voltage clamp device that is connected in parallel with resonant capacitor, it is used to limit the voltage of a plurality of converter switches, this voltage clamp device comprises a bridge circuit device and a DC damped capacitor, this bridge circuit device is by first pair of diode, second pair of diode, form with a pair of controlled discharge switch that is connected in parallel with each diode second pair of diode, and the DC damped capacitor is connected with clamp bridge circuit device, and this bridge circuit device and resonant capacitor are connected in parallel; With
Converter further comprises a controller that is used for the generator gate signal, and this gate signal makes the thyristor conducting of first and second switching devices when being used for no-voltage and zero current actually, and is turn-offed by natural commutation by resonance oscillations.
34. the Unipolar series resonant converter according to claim 33 is characterized in that: the resonant circuit and first and second circuit are connected in series.
35. humorous according to the one pole series connection of claim 20 is parallel operation, it is characterized in that: the resonant circuit and first and second circuit are connected in parallel.
36. the Unipolar series resonant converter according to claim 35 is characterized in that:
First and second circuit comprise the grounding system of a shared common neutral current potential;
Converter further comprises: one first short circuit thyristor, and it is used for selectively resonant circuit being connected with the neutral point current potential and second short circuit thyristor, and it is used for selectively blocking swtich being connected with the neutral point current potential.
37. the Unipolar series resonant converter according to claim 20 is characterized in that:
First circuit comprises a DC system with two conductors;
Converter further comprises one first termination capacitor device filter, and it is connected between two DC conductors of first circuit; With
First switching device comprises first thyristor that the DC conductor of and first circuit is connected in series: and one be connected two fly-wheel diodes between the DC conductor.
38. the Unipolar series resonant converter according to claim 20 is characterized in that: first circuit comprises that an AC system and first switching device comprise:
A diode bridge device, it has the DC output and an AC input that is connected with first circuit that have two DC bridge output conductors;
One first termination capacitor device filter, it is connected between two bridge output conductors;
First thyristor that is connected in series with a bridge output conductor, and one be connected two fly-wheel diodes between the bridge output conductor.
39. a Unipolar series resonant converter that is used for positive energy exchange between first and second circuit comprises:
First and second switching devices, they and corresponding first and second circuit connection;
A resonant circuit that is connected in the middle of first and second circuit;
A chain electric current synthesizer that is connected with resonant circuit, synthesizer control signal that is used to produce a chain electric current of this synthesizer response; With
A chain electric current damping device that is connected with synthesizer, it is used for during energy exchange the value of chain current clamp to a selection.
40. the Unipolar series resonant converter according to claim 39 is characterized in that: chain electric current synthesizer comprises at least one switch, switch conduction at the most during energy exchange.
41. the Unipolar series resonant converter according to claim 40 is characterized in that: chain electric current synthesizer comprises at least one inductor element, changes each synthesizer switch when it is used at least a situation when no-voltage and zero current.
42. the Unipolar series resonant converter according to claim 40 is characterized in that: further comprise a nothing power consumption voltage clamp device that is connected in parallel with resonant capacitor, it is used to limit the voltage of each converter switches.
43. Unipolar series resonant converter according to claim 42, it is characterized in that: the voltage clamp device comprises: a bridge circuit device, this bridge circuit device is by first pair of diode, second pair of diode, form with a pair of controlled discharge switch that is connected in parallel with each diode second pair of diode, with a DC damped capacitor that is connected with the bridge circuit device, this bridge circuit device and resonant capacitor are connected in parallel.
44. the Unipolar series resonant converter according to claim 39 is characterized in that: each comprises the thyristor bridge circuit first and second switching devices.
45. Unipolar series resonant converter according to claim 44, it is characterized in that: this converter further comprises a controller that is used for the generator gate signal, this gate signal makes the thyristor conducting of first and second switching devices when being used for actually no-voltage and zero current and is turn-offed by natural commutation by resonance oscillations.
46. Unipolar series resonant converter according to claim 39, it is characterized in that: synthesizer comprises at least one diode and at least one discharge switch, each diode produces conducting actually during no-voltage, and each discharge switch is switched on and turn-offs when showing no-voltage real.
47. the Unipolar series resonant converter according to claim 39 is characterized in that: converter further comprises a blocking swtich that is connected in series with resonant capacitor.
48. the Unipolar series resonant converter according to claim 47 is characterized in that: further comprise a saturated inductor, an element connected in series in this saturated inductor and the set of pieces of forming by resonant inductor and blocking swtich.
49. the Unipolar series resonant converter according to claim 39 is characterized in that: blocking swtich comprises a thyristor that turn-offs from natural commutation by resonance oscillations.
50. the Unipolar series resonant converter according to claim 39 is characterized in that: further comprise:
A plurality of transducers are used to monitor the electric current and the voltage of the chain electric current and first and second circuit, and these transducers produce the sensor signal of these monitoring targets of response; With
The controller of a response sensor signal is used to produce the control signal of synthesizer.
51. the Unipolar series resonant converter according to claim 39 is characterized in that: the resonant circuit and first and second circuit are connected in series.
52. the Unipolar series resonant converter according to claim 39 is characterized in that:
Each comprises a bridge circuit device of being made up of a plurality of thyristors first and second switching devices, gate signal of each thyristor response;
First and second filter apparatus and corresponding first and second circuit connection;
Chain electric current synthesizer comprises:
At least one discharge switch, discharge switch conducting at the most during energy exchange, each discharge switch turn-on and turn-off during no-voltage actually;
At least one diode, each diode produces conducting during no-voltage actually;
A chain electric current damping device that is connected with synthesizer; With
At least one inductor element, it is used for when no-voltage and changes each synthesizer switch during at least a situation during zero current:
Converter also comprises a nothing power consumption voltage clamp device that is connected in parallel with resonant capacitor, it is used to limit the voltage of a plurality of converter switches, this voltage clamp device comprises a bridge circuit device and a DC damped capacitor, this bridge circuit device is by first pair of diode, second pair of diode, form with a pair of controlled discharge switch that is connected in parallel with each diode second pair of diode, and the DC damped capacitor is connected with clamp bridge circuit device, and this bridge circuit device and resonant capacitor are connected in parallel; With
Converter further comprises a controller that is used for the generator gate signal, and this gate signal makes the thyristor conducting of first and second switching devices when being used for no-voltage and zero current actually, and is turn-offed by natural commutation by resonance oscillations.
53. the Unipolar series resonant converter according to claim 52 is characterized in that: the resonant circuit and first and second circuit are connected in series.
54. the Unipolar series resonant converter according to claim 39 is characterized in that: the resonant circuit and first and second circuit are connected in parallel.
55. the Unipolar series resonant converter according to claim 54 is characterized in that:
First and second circuit comprise the grounding system of a shared common neutral current potential;
Converter further comprises: a blocking swtich that is connected in series with resonant capacitor, one first short circuit thyristor, it be used for selectively resonant circuit be connected with the neutral point current potential and one second short circuit thyristor, it is used for selectively blocking swtich being connected with the neutral point current potential.
56. the Unipolar series resonant converter according to claim 39 is characterized in that:
First circuit comprises a DC system with two conductors;
Converter further comprises one first termination capacitor device filter, and it is connected between two DC conductors of first circuit; With
The second switch device comprises first thyristor that a DC conductor with first circuit is connected in series; And one be connected two fly-wheel diodes between the DC conductor.
57. the Unipolar series resonant converter according to claim 39 is characterized in that: first circuit comprises that an AC system and first switching device comprise:
A diode bridge device, it has the DC output and an AC input that is connected with first circuit that have two DC bridge output conductors;
One first termination capacitor device filter, it is connected between two bridge output conductors;
First thyristor that is connected in series with a bridge output conductor, and one be connected two fly-wheel diodes between the bridge output conductor.
58. the method for a transform power between first and second circuit comprises the following steps:
Synthetic chain electric current of forming by the current impulse of a series of square wave one pole chain, this chain current impulse is excited by resonance oscillations and is terminated, and each pulse has a null section and a non-zero-amplitude section; With
Control the duration of the null section and the non-zero-amplitude section of each chain current impulse.
59. the method according to the positive energy exchange of claim 58 is characterized in that: this method further comprises the step of a plurality of switches that the conversion and first and second circuit link together; With
Controlled step comprises that control changes step suddenly, changes a plurality of switches when this switch process is used for actually no-voltage and zero current.
60. the positive energy exchange method according to claim 58 is characterized in that: synthesis step comprises the chain electric current that utilizes a kind of closed-loop path modulation technique synthetic.
61. the positive energy exchange method according to claim 58 is characterized in that: synthesis step comprises the chain electric current that is used for operating in a kind of adjustable current mode synthetic.
62. the positive energy exchange method according to claim 58 is characterized in that: synthesis step comprises the chain electric current that is used for operating in a kind of adjustable voltage mode synthetic.
63. the positive energy exchange method according to claim 58 is characterized in that: further comprise the step of the amplitude limitation to of each a chain current impulse selective value.
64. the positive energy exchange method according to claim 58 is characterized in that: conditioning step comprise rated maximum current according to a circuit in first and second circuit the amplitude limitation of each chain current impulse to a selective value that less than per unit is 1.5.
65. the positive energy exchange mode according to claim 58 is characterized in that: controlled step comprises the two-way flow between first and second circuit of permission power.
66. the positive energy exchange method according to claim 58 is characterized in that: controlled step comprise permission from a low-voltage level flows of first and second circuit to a higher electric pressure.
67. the positive energy exchange method according to claim 58 is characterized in that:
Synthesis step comprises the chain electric current that utilizes a kind of closed-loop path modulation technique synthetic;
This method further comprises the following steps:
According to the rated maximum current of a circuit in first and second circuit the amplitude limitation of each chain current impulse to a selective value that less than per unit is 1.5; With
A plurality of switches that the conversion and first and second circuit link together; With
Controlled step comprises step:
Between first and second circuit, provide from first and second circuit the low-voltage grade to one more the power bi-directional of voltage levels flow; With
Control is used for changing the switch process of a plurality of switches when showing no-voltage and zero current in fact.
68. the positive energy exchange method according to claim 59 is characterized in that, controlled step comprises the step of the voltage on each switch that is limited in a plurality of switches.
69. chain electric current synthesizer, it and one are by a resonant capacitor, a resonant inductor, the cascaded structure of forming with the blocking swtich of a damping device is connected, it has this synthesizer of chain electricity and is used for a kind of Unipolar series resonant converter, resonant capacitor and resonant inductor interconnect on one and a tie point, and resonant capacitor and blocking swtich interconnect on second tie point, and this chain electric current synthesizer comprises:
First, second and the 3rd node;
One is used on first node first tie point is connected to starting switch on the damping device;
A switch that is connected with first node; With
A damping circuit device that is connected with damper switch is used for by resonance oscillations damping chain electric current.
70. according to the chain electric current synthesizer of claim 69, it is used for a kind of converter with a blocking swtich of being made up of a diode, it is characterized in that:
Each comprises a thyristor starting switch and damper switch; With
Starting inductor is connected with second tie point.
71. according to the chain electric current synthesizer that is used for a kind of converter of claim 69, wherein converter has a blocking swtich of being made up of a diode, it is characterized in that:
Damper switch is connected between first and second nodes;
Starting inductor is connected with blocking swtich with chain electric current damping device on the 3rd node;
This synthesizer further comprises:
One on second node exciting inductor to be connected to the damper diode of starting switch;
A terminating diode that is connected on second node is used for being connected with second tie point; With
Being connected in series of termination sensor and termination thyristor, this termination thyristor is connected with second node, is connected with first tie point with the termination inductor.
72. controller that is used to control the switch of Unipolar series resonant converter, this converter has by a resonant capacitor, a resonant inductor, form cascaded structure with a blocking swtich, this cascaded structure is connected with a chain electric current damping device by a chain electric current synthesizer, this converter is used for positive energy exchange between first and second circuit, this converter have at least one with first and second circuit in a switching device that circuit is connected, this converter comprises transducer, these sensings are used for the electric current of monitoring stream overdamp device, the voltage and current that receives in the circuit from first and second circuit, with the voltage and current that passes to two first circuit in the circuit, this controller comprises:
An output reference signal device is used for providing an output voltage reference signal corresponding to a selective value for the voltage that transmits;
An output voltage error detector is used for detected output voltage being compared with the output voltage reference signal and relatively providing an output voltage error signal according to this;
A damping current reference signal device, being used for corresponding selective value is that stream provides a damping current reference signal for the buffering that flows through damping device;
An input voltage error detector is used for according to the input voltage and the electric current that detect, and detected damping current and damping current reference signal produce an input voltage error signal;
A chain current impulse starter is used for producing an enabling signal according to output voltage error signal and input voltage error signal;
A chain current impulse distributor is used for producing a node selection signal according to input and output voltage differential signal and enabling signal;
A chain current impulse router is used for according to the input and output voltage error signal, and enabling signal and node are selected signal to produce a switch and selected signal; With
A responding to switch is selected the Unipolar series resonant converter switch gate logic part of signal, is used to produce many gate signals, and this gate signal is used to control blocking swtich, chain electric current synthesizer and switching device.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN95102223A CN1065688C (en) | 1995-03-13 | 1995-03-13 | Unipolar series resonant converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN95102223A CN1065688C (en) | 1995-03-13 | 1995-03-13 | Unipolar series resonant converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1131357A CN1131357A (en) | 1996-09-18 |
| CN1065688C true CN1065688C (en) | 2001-05-09 |
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Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN95102223A Expired - Fee Related CN1065688C (en) | 1995-03-13 | 1995-03-13 | Unipolar series resonant converter |
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| Country | Link |
|---|---|
| CN (1) | CN1065688C (en) |
Families Citing this family (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| DE102005051232A1 (en) * | 2005-10-26 | 2007-05-03 | Sms Demag Ag | Control device for alternating current reduction furnaces |
| CN101526561B (en) * | 2008-09-22 | 2011-11-30 | 珠海赛比特电气设备有限公司 | High frequency single-polarity heavy current pulse detection circuit |
| US9030847B2 (en) * | 2010-09-17 | 2015-05-12 | Fairchild Korea Semiconductor Ltd. | Inverter and driving method thereof |
| CN103033697B (en) * | 2012-09-06 | 2015-07-08 | 漆良波 | Capacitor aging test circuit and aging system |
| CN103248338B (en) * | 2013-04-01 | 2016-01-13 | 华中科技大学 | A kind of circuits for triggering of reverse switch transistor |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1099915A (en) * | 1993-08-31 | 1995-03-08 | 电子科技大学 | Constant-frequency zero-voltage edge resonance switch convertor |
-
1995
- 1995-03-13 CN CN95102223A patent/CN1065688C/en not_active Expired - Fee Related
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1099915A (en) * | 1993-08-31 | 1995-03-08 | 电子科技大学 | Constant-frequency zero-voltage edge resonance switch convertor |
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| CN1131357A (en) | 1996-09-18 |
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