CN106506422B - A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal - Google Patents
A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal Download PDFInfo
- Publication number
- CN106506422B CN106506422B CN201611059414.7A CN201611059414A CN106506422B CN 106506422 B CN106506422 B CN 106506422B CN 201611059414 A CN201611059414 A CN 201611059414A CN 106506422 B CN106506422 B CN 106506422B
- Authority
- CN
- China
- Prior art keywords
- signal
- spread spectrum
- 6psk
- vector sequence
- coherent demodulation
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/22—Demodulator circuits; Receiver circuits
- H04L27/233—Demodulator circuits; Receiver circuits using non-coherent demodulation
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
- H04B1/709—Correlator structure
Landscapes
- Engineering & Computer Science (AREA)
- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
The present invention provides a kind of non-coherent demodulation methods of 6PSK modulated spread spectrum signal.6PSK modulated signal is converted to two-way digital orthogonal baseband signal by this method, forms the real and imaginary parts of 6PSK complex base band signal, and 18 6PSK complex base band signals constitute 1 spread spectrum vector sequence, and 1 spread spectrum vector sequence represents 4 digital bit information；Spread spectrum vector sequence inputs the correlator matrix being made of 16 correlators, carries out related operation at the local vector sequence of conjugate relation with spread spectrum vector sequence with 16, exports the maximum correlator label of related function amplitude；According to the mapping relations of correlator label and spread spectrum vector sequence, digital information entrained by 6PSK modulated spread spectrum signal is obtained.The present invention does not need to restore receiver local carrier-phase, and allowing demodulator local carrier and reception signal carrier, there are certain frequency errors, is suitble to the reception of burst signal.
Description
Technical field
The present invention relates to communication technique field, in particular to a kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal.
Background technique
6PSK modulated spread spectrum signal is a kind of signal transmission form of satellite mobile communication, under Low SNR
Transmitting paging information, (formula 1) are its complex signal expression formulas:
In formula (1), h (t) is that the impact of baseband filter is corresponding (its transfer function is square root raised cosine function), akIt is
Modulation symbol.akIt is defined as follows:
Every group of 6PSK modulated spread spectrum signal occupies 78 baud durations, when wherein 1-2 baud and 75-78 baud are protection
Section, 3-74 are that information transmits the period.Figure (1) is the planisphere of 6PSK modulated spread spectrum signal, and the label in figure indicates modulation condition
(the V in table (1)k), each state can regard a vector as, and table (1) is the corresponding relationship of number of state indexes and phase.
Table 1
V in table (1)kIt is determined by formula (3).
S in formula (3)j(i) i in is determined by formula (4):
In formula (4), TRUNC indicates round numbers, and table (2) is the mapping relations of the i and k that are obtained according to formula (4), from table (2)
It is found that the duration of i is 4 bauds.
Table 2
SjIt is by the S in formula (3)j(i) spread spectrum signal sequence formed, each sequence have 18 kinds of states (being shown in Table (3)), often
A SjSequence corresponds to 4 information coding bits (being shown in Table (4)).
Table 3
| Encoded information | Spread spectrum signal sequence Sj |
| 0000 | S0 |
| 0001 | S1 |
| 0010 | S2 |
| 0011 | S3 |
| 0100 | S4 |
| 0101 | S5 |
| 0110 | S6 |
| 0111 | S7 |
| 1000 | S8 |
| 1001 | S9 |
| 1010 | S10 |
| 1011 | S11 |
| 1100 | S12 |
| 1101 | S13 |
| 1110 | S14 |
| 1111 | S15 |
Table 4
In summary: every group of 6PSK modulated spread spectrum signal transmits 4 information bits, and 4 information bits constitute a spread spectrum
SjSequence；Each spread spectrum SjSequence includes 18 kinds of states, and every kind of state occupies 4 baud durations, a phase of corresponding 6PSK modulation
Position；If every kind of state is regarded as a vector, each spread spectrum SjSequence is the sum of 18 vectors (see formula (5)).
Formula (6) is the real signal expression formula of 6PSK signal.In formula (6), A (t) is signal amplitude function, depends on base band and filters
The transfer function h (t) of wave device；ωi=2 π fiIt is the angular frequency of signal carrier；θ (k) is the instantaneous phase of signal, by modulation symbol
akIt determines, changes by 6PSK modulation system, period of change is 4 bauds.
S (t)=A (t) cos [ωiT+ θ (k)] (formula 6)
Table (5) is the frame structure of 6PSK spread spectrum signal transmitting.Frame number is 0-63 in table, is recycled in cycles；When opposite
Gap number is the number of a certain section of time slot in 24 time slots of every frame；FCCH frame is synchronous with clock for receiving unit frequency；6PSK
Frame is used for transmission 6PSK modulated spread spectrum signal.39 bauds of each time slot frame length, baud rate 23.4KB/s.Each 6PSK frame accounts for
With 2 time slots, 78 bauds, to send a SjSequence (represents 4 bit informations).
Table 5
Summary of the invention
For the demodulation for solving the problems, such as above-mentioned 6PSK modulated spread spectrum signal, the present invention provides a kind of 6PSK modulated spread spectrum signal
Non-coherent demodulation method, comprising:
Down coversion, sampling, cumulative, baseband filtering are carried out to 6PSK modulated spread spectrum signal, form digital orthogonal baseband signal；
Digital orthogonal baseband signal constitutes 6PSK complex base band signal, and every 18 complex base band signals constitute a spread spectrum vector sequence
Column；
Each spread spectrum vector sequence and 16 local vector sequences carry out related operation, calculate 16 correlation function amplitudes
Absolute value；
16 correlation function amplitude absolute values are made decisions, output generates the correlator label of amplitude peak；
According to the mapping relations of the correlator label of amplitude peak and spread spectrum vector sequence, 6PSK modulated spread spectrum signal is obtained
Entrained digital information.
Preferably, in a kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal, the 6PSK modulation is expanded
Frequency signal is indicated by following formula: s (t)=A (t) cos [ωit+θ(k)].Wherein, A (t) is signal amplitude function, by adjusting
Device baseband filter processed determines that frequency response function is square root raised cosine function；ωiIt is the angular frequency of signal carrier；θ
(k) be signal instantaneous phase, by 6PSK modulation system change.
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, the down coversion is by following public affairs
Formula indicates:
Wherein, ω0Local frequency, nominal value and ω are received for demodulatoriIt is identical.S in formulaI(t) and sQ(t) expression formula
Previous item is required down-converted component.
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, down-conversion signal sample frequency
It is 8 times of signal baud rate, i.e. 1 baud, 8 sampled points；After 4 samplings are cumulative, 1 baud, 2 sampled points are reduced to, 4 samplings are tired
Device is added to play low-pass filter.
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, baseband filter frequency response
Function is square root raised cosine function, and the digital orthogonal baseband signal being generated by it is made of real and imaginary parts, is indicated by following formula:
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, the complex base band signal by
It is indicated with following formula:
Sj' (n)=I (n)+jQ (n)=B (n) ej(ΔωnΔt+θ(k))。
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, the real part of complex base band signal,
Imaginary part inputs 144 grades of shift registers in 16 correlators respectively, and 18 tap outputs of shift register constitute spread spectrum arrow
Sequence is measured, is divided into 8 sampled datas between each tap.
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, used in 16 correlators
16 local vector sequences and spread spectrum vector sequence are at conjugate relation.
Preferably, in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, on the basis of frame synchronizing signal,
The correlation function range value of each correlator is exported at the time of input spread spectrum vector sequence is synchronous with local vector sequence.
Preferably, it in the non-coherent demodulation method of the 6PSK modulated spread spectrum signal, is obtained by 2 grades of amplitude judgements
The correlator label of correlation function amplitude peak is generated, wherein the 1st grade of judgement obtains correlation function amplitude for each correlator
Maximum value, the maximum value of correlation function amplitude of the 2nd grade of amplitude judgement for obtaining 16 correlators.
Using the non-coherent demodulation method of 6PSK modulated spread spectrum signal of the invention, the present invention is had the advantages that
Do not need restore receiver carrier phase, while allow demodulator carrier wave and receive signal carrier there are certain frequency errors；
Compared with coherent demodulation mode, signal does not need to restore header used in carrier wave, eliminates carrier recovery time, is suitble to burst letter
Number reception；Under Low SNR, the peak value that still can accurately detect input spread spectrum vector sequence (arrives see figure (5-A)
Scheme (5-E)), to accurately realize data demodulation；Algorithm is simple, and calculation amount is small, it is easy to accomplish.
Detailed description of the invention
Figure (1) is the planisphere of 6PSK modulated spread spectrum signal；
Figure (2) is the functional block diagram of the embodiment of the present invention；
Figure (3) is the flow chart of the embodiment of the present invention；
Figure (4) is the correlator matrix principle figure of the embodiment of the present invention；
Figure (5-A), (5-B), (5-C), (5-D), (5-E) are the embodiment of the present invention under the conditions of different signal-to-noise ratio (SNR),
The correlation function magnitude squared value peak value of correlator Output matrix；Wherein figure (5-A) be signal-to-noise ratio be 20dB under the conditions of as a result,
Figure (5-B) is under the conditions of signal-to-noise ratio be 5dB as a result, figure (5-C) is result under the conditions of signal-to-noise ratio is 0dB, to scheme (5-D) be letter
Make an uproar than to be under the conditions of -5dB as a result, figure (5-E) is result under the conditions of signal-to-noise ratio is -10dB；
Figure (6) is the correlation function range signal data decimation schematic block circuit diagram of the embodiment of the present invention；
Figure (7) is the correlation function range signal data decimation circuit timing diagram of the embodiment of the present invention；
Figure (8) is the amplitude decision circuit functional block diagram of the embodiment of the present invention.
Specific embodiment
The present invention is described in further detail below in conjunction with the drawings and specific embodiments.It is wanted according to the following instructions with right
Book is sought, advantages and features of the invention will be more clear.The attached drawing in explanation is all made of reduced form and using non-accurate below
Ratio, only to facilitate, lucidly aid in illustrating the embodiment of the present invention.
Figure (2) is the functional block diagram of the embodiment of the present invention, and figure (3) is the flow chart of the embodiment of the present invention.The present invention proposes
A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal, specifically includes the following steps:
Step 1: input signal down coversion.The input signal of the demodulator is 6PSK modulated spread spectrum signal s (t), number
Expression is learned as shown in formula (6).S (t) and orthogonal local oscillation signal sin ω0T and cos ω0T multiplication (ω0Nominal value and ωiIt is identical,
There are the error delta ω of very little, Δ ω=ω in practical situationsi-ω0), quadrature mixing signals s shown in production (7)I(t)、
sQ(t)。
In formula (7), sI(t)、sQ(t) previous item is required down-converted component；Latter is high fdrequency component, will be by
Subsequent 4 sampling accumulator, baseband matched filter filter out.
Step 2: signal sampling.The quadrature mixing signals sI(t)、sQ(t) by sampled signal fSSampling, output number is just
Hand over mixed frequency signal sI’(m)、sQ' (m), fSFor input signal baud rate Ri8 times, i.e. peculiar 8 sampled points of 1 signal wave.
Step 3: digital orthogonal baseband signal is generated.The digital quadrature mixing signal sI' (m) and sQ' (m) tired by 4 samplings
After adding device, baseband matched filter (transfer function is square root raised cosine function) processing, digital orthogonal baseband signal I (n) and Q are exported
(n), formula (8) is its mathematic(al) representation；The sample rate of digital orthogonal baseband signal is reduced to 1 baud containing 2 sampled points；The orthogonal basis
Band signal I (n) and Q (n) constitutes the complex base band signal S of 6PSK signalj' (n) real and imaginary parts, formula (9) be its mathematical table
Up to formula；The variation of signal amplitude is as caused by the processing such as A/D transformation, cumulative, filtering in formula, but the property of signal does not have
Variation.
Sj' (n)=I (n)+jQ (n)=B (n) ej(ΔωnΔt+θ(k))(formula 9)
Step 4: related operation.The complex base band signal Sj' (n) input the correlator square that is made of 16 correlators
Battle array carries out related operation, exports the square value of 16 correlation function amplitudes, and figure (3) is the functional block diagram of correlator matrix.Plural number
Baseband signal Sj' the real part I (n) and imaginary part Q (n) of (n) input 144 grades of the two tunnel shift register of each correlator respectively, two
18 tap outputs of road shift register constitute the received spread spectrum vector sequence S of institutej' (i) (i=0,2,3 ... 17), each pumping
8 sampled datas are divided between head.Sj' (i) sequence and transmitting terminal Sj(i) sequence is corresponding, and Δ ω t is only had rotated in phase
Radian.If TkIt (i) is local vector sequence, i=0,2,3 ... 17, k=0,2,3 ... 15.Tk(i) sequence is Sj(i) sequence is total to
Yoke, i.e.,Table (5) is Tk(i) state table of sequence, table (6) is Tk(i) real part of sequence state, imaginary part mapping
Table, table (7) is Tk(i) mapping table of sequence and correlator label.Receive the spread spectrum vector sequence S of signalj' (i) and 16 locals
Vector sequence Tk(i) related operation (see formula (10)) are carried out, exports the square value P of the amplitude of 16 correlation functionsk(see formula
(11))。
Pk=| Rk|2K=0,1,2...., 15 (formula 11)
Due to Sj' (i) sequence is mutually orthogonal directions, when j is not equal to k, correlation function RkAmplitude very little；When j is equal to k, related letter
Number RkAs shown in (formula (12)), amplitude | Rk| reach peak value.
The correlation function amplitude square exported in the present invention with some correlator in correlator matrix | Rk|2Reach peak value to sentence
Other receiver has received some Sj' (i) sequence.Figure (5-A) is correlator matrix under the conditions of signal-to-noise ratio (SNR) is 20dB
The correlation function amplitude peak square value of output | Rk|2.Figure (5-A), (5-B), (5-C), (5-D), (5-E) are implementation of the present invention
Example is under the conditions of different signal-to-noise ratio (SNR), the correlation function magnitude squared value peak value of correlator Output matrix；Wherein scheme (5-A)
It is under the conditions of signal-to-noise ratio is 20dB as a result, figure (5-B) is under the conditions of signal-to-noise ratio is 5dB as a result, figure (5-C) is that signal-to-noise ratio is
Result, figure (5-D) under the conditions of 0dB are under the conditions of signal-to-noise ratio is -5dB as a result, it is -10dB condition that figure (5-E), which is signal-to-noise ratio,
Under result.
Table 6
| Tk(i) state | Real part (I) | Imaginary part (Q) |
| 0 | 1 | 0 |
| 1 | -0.5 | 0.866 |
| 2 | -0.5 | -0.866 |
| 3 | -1 | 0 |
| 4 | 0.5 | 0.866 |
| 5 | 0.5 | -0.866 |
Table 7
Table 8
Step 5: correlation function data is chosen.The spread spectrum vector sequence Sj' (i) serial input correlator matrix, only
In Sj' (i) sequence and Tk(i) (4 bauds, 8 sampled points) in that period when sequence alignment, 16 correlators meet just
Friendship relationship, output are only required correlation function value.Shown in the definition of data decimation signal K (l) such as formula (13):
The interval of definition of K (l) is the length (78 bauds) of a 6PSK spread spectrum letter frame in formula.The suitable switch of K (l)
Signal, it and PkIt is multiplied, obtains effective correlation function magnitude squared value Pk', as shown in formula (14):
Pk'=Pk× K (l) (formula 14)
Scheming (6) is correlation function range signal selecting circuit functional block diagram.As shown in figure (6), Pk8 bit shift register of serial input,
8 adjacent P of parallel outputkIt is worth 8 path switching circuits, switching circuit is controlled by K (l) signal.It is closed when K (l) is 0, Pk'
=0；It is opened as K (l)=1, Pk'=Pk.Figure (7) is the timing diagram for exporting related function amplitude signal circuit.Such as figure (7) institute
Show, the starting of each 6PSK spread-spectrum signal frame of frame synchronizing signal mark, which is determined by receiving FCCH frame (being shown in Table (6))；
Each 6PSK spread-spectrum signal frame occupies 78 bauds, wherein 3-74 baud corresponds to a Sj' (i) sequence；Correlator matrix meter
Calculate Sj' (i) sequence and Tk(i) correlation function of sequence, and the amplitude correlation function square value P that defeated each sampling generatesk；When every
When 71-74 baud of frame signal inputs correlator matrix, Sj' (i) sequence and Tk(i) sequence alignment, wherein some correlator produces
Raw correlation function peak value；Data decimation signal K (l) is on the basis of frame synchronizing signal, and every frame generates 1, and value is in 71-74 wave
The special period is 1, and other time section is 0；K (l) controls 8 way switch and exports Pk', i.e. the 8 of 71-74 baud period PkValue.
Step 6: correlation function amplitude judgement.Figure (8) is the functional block diagram of amplitude decision circuit.As shown in figure (8), phase
Close the correlation function range signal P of device Output matrixk' by 2 grades of amplitude judgements, determine the S having correctly receivedj(i) sequence.1st
Grade amplitude judgement is to every road correlation function range signal Pk' 8 numerical value be compared, choose maximum value W thereink=
[Pk']maxIt exports (k=0,1,2..15), WkThe output frequency of data is Pk' frequency 1/8.2nd grade of amplitude judgement is to 16 Wk
It is worth carry out amplitude comparison, chooses maximum value [Wk]max, output generates the correlator label Z of the amplitude peak correlation function, related
Device label Z and Sj(i) sequential labeling is corresponding, and expression has received some Sj(i) sequence.
Step 7: data are restored.According to the peak value correlator label Z, obtain being connect by the mapping relations that table (9) determine
The data information of receipts, table (9) are corresponding with the table (4) of transmitting signal.
| Peak value correlator label Z | Data information |
| 0 | 0000 |
| 1 | 0001 |
| 2 | 0010 |
| 3 | 0011 |
| 4 | 0100 |
| 5 | 0101 |
| 6 | 0110 |
| 7 | 0111 |
| 8 | 1000 |
| 9 | 1001 |
| 10 | 1010 |
| 11 | 1011 |
| 12 | 1100 |
| 13 | 1101 |
| 14 | 1110 |
| 15 | 1111 |
Table 9
Although the present invention is disclosed above with embodiment, so it is any to be familiar with this skill not to limit the present invention
Person, without departing from the spirit and scope of the present invention, when can be used for a variety of modifications and variations, therefore protection scope of the present invention is worked as
Subject to appended claims institute defender.
Claims (10)
1. a kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal characterized by comprising
Down coversion, sampling, cumulative, baseband filtering are carried out to 6PSK modulated spread spectrum signal, form digital orthogonal baseband signal；
Digital orthogonal baseband signal constitutes 6PSK complex base band signal, and every 18 complex base band signals constitute a spread spectrum vector sequence；
Each spread spectrum vector sequence and 16 local vector sequences carry out related operation, and it is absolute to calculate 16 correlation function amplitudes
Value；
16 correlation function amplitude absolute values are made decisions, output generates the correlator label of amplitude peak；
According to the mapping relations of the correlator label of amplitude peak and spread spectrum vector sequence, obtains 6PSK modulated spread spectrum signal and taken
The digital information of band.
2. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as described in claim 1, which is characterized in that the 6PSK tune
Spread-spectrum signal processed is indicated by following formula:
S (t)=A (t) cos [ωiT+ θ (k)],
Wherein, A (t) is signal amplitude function, is determined by modulator baseband filter, and frequency response function is more than square root rises
String function；ωiIt is the angular frequency of signal carrier；θ (k) is the instantaneous phase of signal, is changed by 6PSK modulation system.
3. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as described in claim 1, which is characterized in that the down coversion
It is indicated by following formula:
Wherein, A (t) is signal amplitude function；ωiIt is the angular frequency of signal carrier, ω0Local frequency, mark are received for demodulator
Title value and ωiIt is identical；Δ ω is ωiWith ω0Difference；θ (k) is the instantaneous phase of signal；S in formulaI(t) and sQ(t) expression formula
Previous item be required down-converted component.
4. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as claimed in claim 3, which is characterized in that down-conversion signal
Sample frequency is 8 times of signal baud rate, i.e. 1 baud, 8 sampled points；After 4 samplings are cumulative, it is reduced to 1 baud 2 samplings
Point.
5. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as claimed in claim 2, which is characterized in that baseband filter
Frequency response function is square root raised cosine function, and the digital orthogonal baseband signal being generated by it is indicated by following formula:
Wherein, I (n) is the road the I component of digital orthogonal baseband signal, and Q (n) is the road the Q component of digital orthogonal baseband signal, and B (n) is orthogonal basis
The amplitude function of band signal, Δ t are the time intervals of discrete data signal, and Δ ω is ωiWith ω0Difference, ω0For demodulator
Receive local frequency, nominal value and ωiIt is identical.
6. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as described in claim 1, which is characterized in that the plural number base
Band signal is made of real and imaginary parts, is indicated by following formula:
Sj' (n)=I (n)+jQ (n)=B (n) ej(ΔωnΔt+θ(k)),
Wherein, I (n) is the road the I component of digital orthogonal baseband signal, and Q (n) is the road the Q component of digital orthogonal baseband signal, and B (n) is orthogonal basis
The amplitude function of band signal,Δ t is the time interval of discrete data signal, and Δ ω is ωiWith
ω0Difference, ωiIt is the angular frequency of signal carrier, ω0Local frequency, nominal value and ω are received for demodulatoriIt is identical, θ (k)
It is the instantaneous phase of input signal,
7. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as claimed in claim 6, which is characterized in that complex baseband letter
Number real part, imaginary part input 144 grades of shift registers in 16 correlators, 18 tap output structures of shift register respectively
At spread spectrum vector sequence, 8 sampled datas are divided between each tap.
8. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as claimed in claim 7, which is characterized in that 16 correlators
Used in 16 local vector sequences and spread spectrum vector sequence at conjugate relation.
9. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as described in claim 1, which is characterized in that believed with frame synchronization
On the basis of number, the correlation function width of each correlator is exported at the time of input spread spectrum vector sequence is synchronous with local vector sequence
Angle value.
10. the non-coherent demodulation method of 6PSK modulated spread spectrum signal as described in claim 1, which is characterized in that pass through 2 grades of width
Degree judgement obtains the correlator label for generating correlation function amplitude peak, wherein the 1st grade of judgement obtains phase for each correlator
Close the maximum value of function amplitude, the maximum value of correlation function amplitude of the 2nd grade of amplitude judgement for obtaining 16 correlators.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201611059414.7A CN106506422B (en) | 2016-11-25 | 2016-11-25 | A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201611059414.7A CN106506422B (en) | 2016-11-25 | 2016-11-25 | A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN106506422A CN106506422A (en) | 2017-03-15 |
| CN106506422B true CN106506422B (en) | 2019-03-26 |
Family
ID=58327931
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201611059414.7A Active CN106506422B (en) | 2016-11-25 | 2016-11-25 | A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN106506422B (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107579942B (en) * | 2017-11-02 | 2020-04-10 | 电信科学技术第一研究所有限公司 | Demodulation method of APSK (amplitude phase Shift keying) modulation signal |
| DE102019101621B3 (en) * | 2019-01-23 | 2020-06-04 | Infineon Technologies Ag | COMMUNICATION DEVICE AND METHOD FOR RECEIVING DATA VIA A RADIO SIGNAL |
| CN112073116B (en) * | 2020-09-16 | 2022-04-29 | 电信科学技术第一研究所有限公司 | Frame structure of satellite carrier superposition signal and demodulation method thereof |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101083504A (en) * | 2007-07-23 | 2007-12-05 | 沖电气（新加坡）技术中心 | Demodulating equipment and its demodulating method |
| CN103780462A (en) * | 2014-01-22 | 2014-05-07 | 中国人民解放军理工大学 | Satellite communication signal modulation identification method based on high-order cumulants and spectrum characteristics |
-
2016
- 2016-11-25 CN CN201611059414.7A patent/CN106506422B/en active Active
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101083504A (en) * | 2007-07-23 | 2007-12-05 | 沖电气（新加坡）技术中心 | Demodulating equipment and its demodulating method |
| CN103780462A (en) * | 2014-01-22 | 2014-05-07 | 中国人民解放军理工大学 | Satellite communication signal modulation identification method based on high-order cumulants and spectrum characteristics |
Non-Patent Citations (2)
| Title |
|---|
| Performance Analysis of Orthogonal Coded Modulation Based on 6PSK and BPSK in Alerting Channel for GEO Mobile Satellite System;Gao, QA (Gao, Qian) 等;《2010 International Conference on Signal Acquisition and Processing》;20100210;第322-326页 |
| 相移键控信号盲解调的仿真分析;王启峰 等;《电视技术》;20111002;第35卷(第19期);第132-134页 |
Also Published As
| Publication number | Publication date |
|---|---|
| CN106506422A (en) | 2017-03-15 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN101946474B (en) | Impulse ultra-wideband radio communication system | |
| CN103248593B (en) | Offset estimation and removing method and system | |
| CN106506422B (en) | A kind of non-coherent demodulation method of 6PSK modulated spread spectrum signal | |
| KR100899825B1 (en) | Cdma system which uses pre-rotation before transmission | |
| CA2386418A1 (en) | Method and apparatus for carrier phase tracking | |
| JPH02105746A (en) | Differental phase transition keying modulator | |
| CN100576768C (en) | The compensation method of Doppler frequency shift in the MPSK mobile communication system | |
| CN109547059A (en) | A kind of Chirp-GFSK joint spread-spectrum modulation and demodulation system | |
| CN102025669B (en) | Short-wave data transmission method based on dual multisystem quasi-orthogonal spread-spectrum composite phase modulation | |
| JPH0621982A (en) | Method and apparatus for demodulation of gmsk signal | |
| CN101902420A (en) | Continuous phase differential phase-shift keying modulation and demodulation method in signs | |
| CN107579942B (en) | Demodulation method of APSK (amplitude phase Shift keying) modulation signal | |
| CN111314262B (en) | 16QAM carrier synchronization system in low signal-to-noise ratio environment | |
| CN103439718A (en) | Unambiguous tracking unit of high-order BOC modulation signals | |
| CN109412642B (en) | Signal modulation and demodulation method and phase hopping modulation and demodulation unit | |
| CN109756435B (en) | Method for estimating frequency offset of signal | |
| CN106130941A (en) | A kind of multi tate shelves adaptive de adjusting system for residual carrier modulation | |
| CN105407067A (en) | Recovery method of coherent carrier wave and timing of burst mode GMSK | |
| CN102932298B (en) | Dual-carrier ABSK communication system on basis of same narrow-band filter | |
| CN102857448B (en) | Short wave speed change communication system and multipath estimation and separation method used by same | |
| CN107426121A (en) | Training sequence design and application process and device for broad sense Frequency Division Multiplexing system | |
| CN109714146A (en) | A kind of secondary related frame synchornization method based on sliding window | |
| CN104821926A (en) | Frequency error estimation | |
| CN103647734B (en) | Channel for satellite mobile communication terminal is estimated and the method and device of equilibrium | |
| CN101039126B (en) | Method and system of phase deviation measurement for testing TD-SCDMA terminal |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| CB02 | Change of applicant information | ||
| CB02 | Change of applicant information |
Address after: 200032 Pingjiang Road, Xuhui District, Shanghai, No. 48 Applicant after: The first Research Institute of telecommunication science and technology Address before: 200032 Pingjiang Road, Xuhui District, Shanghai, No. 48 Applicant before: The First Research Institute of Telecommunication Technology |
|
| GR01 | Patent grant | ||
| GR01 | Patent grant |