CN106330793B - signal processing method and device - Google Patents
signal processing method and device Download PDFInfo
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Abstract
The invention discloses a signal processing method and a signal processing device, and belongs to the technical field of communication. The method comprises the following steps: calculating an IRC matrix on each subcarrier according to the first channel matrix; selecting elements of the same row and column in an IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter; forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter; and processing time domain sampling points of the received signal according to the time domain IRC linear convolution filter. The taps in the circular convolution filter are intercepted to obtain the linear convolution filter, and the signal is processed through the linear convolution filter, so that the taps passing through the signal processing are reduced, the processed signal can be output only by waiting for the time domain sampling points with the first preset value, and the complexity and the consumed time delay in the signal processing are reduced.
Description
Technical Field
the present invention relates to the field of communications technologies, and in particular, to a signal processing method and apparatus.
Background
with the development of the current communication technology, more and more scenes are needed to transmit signals. For example, when the user equipment is in a closed environment such as indoors or in a car, the signal needs to be processed by a relay node in the closed environment, and the processed signal needs to be forwarded to the base station. Since the signal quality is affected by the signal processing method, an appropriate signal processing method needs to be selected.
In the related art, the following method is adopted for processing signals: and amplifying the received signal through the wireless repeater, and forwarding the amplified signal to the base station.
in the process of implementing the invention, the inventor finds that the prior art has at least the following problems:
when processing signals, the received signals are amplified and noise interference is amplified at the same time, so that more noise interference exists in the forwarded signals, and the signal-to-noise ratio is lower when the user equipment side receives the signals.
Disclosure of Invention
in order to solve the problems in the prior art, embodiments of the present invention provide a signal processing method and apparatus. The technical scheme is as follows:
In a first aspect, a signal processing method is provided, the method including:
calculating an Interference Rejection Combining (IRC) matrix on each subcarrier according to a first channel matrix, where the first channel matrix is a channel matrix from a serving cell base station to each subcarrier of the relay node;
selecting elements of the same row and column in an IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter;
forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circular convolution filter;
and processing time domain sampling points of the received signals according to the time domain IRC linear convolution filter.
With reference to the first aspect, in a first possible implementation manner of the first aspect, the calculating, according to the first channel matrix, an interference suppression combining IRC matrix on each subcarrier includes:
calculating an interference noise correlation matrix Ruu;
multiplying the first channel matrix and a conjugate transpose matrix of the first channel matrix to obtain a first product;
adding the first product and the Ruu, and performing inverse operation on a result obtained by the addition;
And multiplying the result obtained by the inverse operation by a conjugate transpose matrix of the first channel matrix, and taking a second product obtained by the multiplication as an IRC matrix.
With reference to the first possible implementation manner of the first aspect, in a second possible implementation manner of the first aspect, the calculating an interference noise correlation matrix Ruu includes:
Calculating a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, where the second channel matrix is a channel matrix from the interfering cell base station to the relay node;
adding all the third products to obtain a first calculation result after addition;
Multiplying the noise power by the identity matrix to obtain a second calculation result;
and adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
with reference to the first possible implementation manner of the first aspect, in a third possible implementation manner of the first aspect, when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, the calculating an interference noise correlation matrix Ruu includes:
if the current subframe is positioned in the first subframe, multiplying the noise power by the unit matrix, and taking the obtained result as Ruu of the current subframe;
If the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
With reference to the first aspect, in a fourth possible implementation manner of the first aspect, the processing, according to the time domain IRC linear convolution filter, a time domain sample of a received signal includes:
when the time domain sampling point of the received signal is not the first preset value time domain sampling point after an OFDM (Orthogonal Frequency Division Multiplexing) symbol, performing linear convolution processing on the time domain sampling point of the received signal;
and when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
In a second aspect, there is provided a signal processing apparatus, the apparatus comprising:
a calculating module, configured to calculate an IRC matrix on each subcarrier according to a first channel matrix, where the first channel matrix is a channel matrix from a serving cell base station to each subcarrier of the relay node;
the selection module is used for selecting elements of the same row and column in the IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter;
The forming module is used for forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter;
And the processing module is used for processing the time domain sampling points of the received signals according to the time domain IRC linear convolution filter.
With reference to the second aspect, in a first possible implementation manner of the second aspect, the calculation module includes:
the first computing unit is used for computing an interference noise correlation matrix Ruu;
A second calculation unit, configured to multiply the first channel matrix and a conjugate transpose matrix of the first channel matrix to obtain a first product;
a third calculation unit, configured to add the first product to the Ruu, and perform an inverse operation on a result obtained by the addition;
And the fourth calculation unit is used for multiplying the result obtained by the inverse operation by the conjugate transpose matrix of the first channel matrix, and taking the second product obtained by the multiplication as the IRC matrix.
with reference to the second aspect, in a first possible implementation manner of the second aspect, the calculating unit is configured to calculate a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, where the second channel matrix is a channel matrix from an interfering cell base station to the relay node; adding all the third products to obtain a first calculation result after addition; multiplying the noise power by the identity matrix to obtain a second calculation result; and adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
with reference to the first possible implementation manner of the second aspect, in a second possible implementation manner of the second aspect, when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, the calculating unit is configured to multiply the noise power by the identity matrix when the interfering cell base station is currently in the first subframe, and use an obtained result as Ruu of the current subframe; if the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
with reference to the first possible implementation manner of the second aspect, in a third possible implementation manner of the second aspect, when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, the calculating unit is configured to multiply the noise power by the identity matrix when the interfering cell base station is currently in the first subframe, and use an obtained result as Ruu of the current subframe; if the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
with reference to the second aspect, in a fourth possible implementation manner of the second aspect, the processing module is configured to perform linear convolution processing on the time domain sampling points of the received signal when the time domain sampling points of the received signal are not the last first preset number of time domain sampling points of one OFDM symbol; and when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
The technical scheme provided by the embodiment of the invention has the following beneficial effects:
The method comprises the steps of calculating an IRC matrix on each subcarrier according to a first channel matrix, selecting elements of the same row and column in the IRC matrix on each subcarrier, carrying out inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter, forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter, and processing a time domain sampling point of a received signal according to the time domain IRC linear convolution filter. The taps in the circular convolution filter are intercepted to obtain the linear convolution filter, and the signal is processed through the linear convolution filter, so that the taps passing through the signal processing are reduced, the processed signal can be output only by waiting for the time domain sampling points with the first preset value, and the complexity and the consumed time delay in the signal processing are reduced.
Drawings
In order to more clearly illustrate the technical solutions in the embodiments of the present invention, the drawings needed to be used in the description of the embodiments will be briefly introduced below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and it is obvious for those skilled in the art to obtain other drawings based on these drawings without creative efforts.
Fig. 1 is a schematic diagram of an implementation environment of a signal processing method according to an embodiment of the present invention;
fig. 2 is a schematic diagram of an implementation environment of a signal processing method according to another embodiment of the present invention;
FIG. 3 is a schematic diagram of an implementation environment of a signal processing method according to another embodiment of the present invention;
FIG. 4 is a flow chart of a signal processing method according to another embodiment of the present invention;
FIG. 5 is a flow chart of a signal processing method according to another embodiment of the present invention;
fig. 6 is a schematic diagram of a filter structure between the transmitting and receiving antennas according to another embodiment of the present invention;
FIG. 7 is a schematic diagram of a circular convolution filter according to another embodiment of the present invention;
FIG. 8 is a schematic diagram of a linear convolution filter according to another embodiment of the present invention;
FIG. 9 is a schematic diagram of a signal time domain process according to another embodiment of the present invention;
FIG. 10 is a schematic diagram of a signal time domain process according to another embodiment of the present invention;
FIG. 11 is a schematic diagram of a signal time domain process according to another embodiment of the present invention;
fig. 12 is a schematic structural diagram of a signal processing apparatus according to another embodiment of the present invention;
fig. 13 is a schematic structural diagram of a relay node according to another embodiment of the present invention.
Detailed Description
in order to make the objects, technical solutions and advantages of the present invention more apparent, embodiments of the present invention will be described in detail with reference to the accompanying drawings.
Referring to fig. 1, a schematic diagram of a network architecture according to the method provided by the embodiment of the present invention is shown. As shown in fig. 1, the network architecture includes a serving cell eNB (Evolved NodeB), an interfering cell eNB, and a relay node. The serving cell eNB is a base station providing service to a User Equipment (UE), the interfering cell eNB is a base station that causes interference to signals adjacent to the serving cell, the number of the interfering cells eNB is at least one, and the number of the interfering cells is not specifically limited in this embodiment.
in addition, the relay node refers to a device responsible for receiving and forwarding signals, and the relay node may receive and forward signals transmitted by the serving cell eNB to the UE, and may also receive and forward signals of the UE to the serving cell eNB. When a plurality of interference cells exist around a serving cell where the UE is located, since the interference suppression capability of the UE itself is limited, the relay node having the interference suppression function nearby may perform interference suppression processing on the signal, so that the relay node forwards the signal with interference suppressed to the UE. Taking the number of the serving cell eNB as one and the number of the interfering cell eNB as two as examples, the association among the serving cell eNB, the interfering cell eNB and the relay node can be as shown in fig. 1. The left side of fig. 1 shows the case of no relay node being added, and the right side of fig. 1 shows the case of relay node being added.
when the UE is in a closed environment such as indoor or in a car, due to the existence of barrier isolation, signals from the base station to the UE are blocked, and the signal attenuation is large, so that the signal received by a user is strong and the signal interference of an adjacent interference cell is inhibited through the forwarding power gain of the relay node. Take the number of serving cell enbs as one and the number of interfering cell enbs as one. When the UE is in an indoor environment, the serving cell eNB, the interfering cell eNB and the relay node may be associated with each other as shown in fig. 2. When the UE is in a car environment, the association between the three may be as shown in fig. 3.
the embodiment of the invention provides a signal processing method, which is used for a relay node. The serving cell base station in this embodiment and subsequent embodiments may be a serving cell eNB, and the interfering cell base station may be an interfering cell eNB, which are not specifically limited in this embodiment and subsequent embodiments. Referring to fig. 4, the method flow provided by this embodiment includes:
401. and calculating an IRC matrix on each subcarrier according to the first channel matrix, wherein the first channel matrix is a channel matrix from the base station of the serving cell to each subcarrier of the relay node.
402. And selecting elements in the same row and column in the IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter.
403. and forming a time domain IRC linear convolution filter by the rear first preset value taps and the front second preset value taps in the time domain IRC circular convolution filter.
404. and processing time domain sampling points of the received signal according to the time domain IRC linear convolution filter.
The method provided by the embodiment of the invention comprises the steps of calculating an IRC matrix on each subcarrier according to a first channel matrix, selecting elements with the same row and column in the IRC matrix on each subcarrier, carrying out inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter, forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter, and processing a time domain sampling point of a received signal according to the time domain IRC linear convolution filter. The taps in the circular convolution filter are intercepted to obtain the linear convolution filter, and the signal is processed through the linear convolution filter, so that the taps passing through the signal processing are reduced, the processed signal can be output only by waiting for the time domain sampling points with the first preset value, and the complexity and the consumed time delay in the signal processing are reduced.
As an alternative embodiment, calculating the IRC matrix on each subcarrier according to the first channel matrix includes:
Calculating an interference noise correlation matrix Ruu;
Multiplying the first channel matrix and the conjugate transpose matrix of the first channel matrix to obtain a first product;
Adding the first product and Ruu, and carrying out inverse operation on the result obtained by the addition;
And multiplying the result obtained by the inverse operation by a conjugate transpose matrix of the first channel matrix, and taking a second product obtained by the multiplication as an IRC matrix.
As an alternative embodiment, the interference noise correlation matrix Ruu is calculated, which includes:
Calculating a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, wherein the second channel matrix is a channel matrix from the interference cell base station to the relay node;
adding all the third products to obtain a first calculation result after addition;
Multiplying the noise power by the identity matrix to obtain a second calculation result;
and adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
As an alternative embodiment, when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, calculating an interference noise correlation matrix Ruu includes:
if the current subframe is positioned in the first subframe, multiplying the noise power by the unit matrix, and taking the obtained result as Ruu of the current subframe;
If the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
as an alternative embodiment, processing time-domain samples of a received signal according to a time-domain IRC linear convolution filter includes:
when the time domain sampling point of the received signal is not the first preset value time domain sampling point after one OFDM symbol, performing linear convolution processing on the time domain sampling point of the received signal;
And when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
All the above-mentioned optional technical solutions can be combined arbitrarily to form the optional embodiments of the present invention, and are not described herein again.
The embodiment of the invention provides a signal processing method, which is used for a relay node. Referring to fig. 5, the method flow provided by this embodiment includes:
501. And calculating an IRC matrix on each subcarrier according to the first channel matrix, wherein the first channel matrix is a channel matrix from the base station of the serving cell to each subcarrier of the relay node.
the relay node searches for a neighboring Cell, detects Cell-specific Reference signals (CRSs) of the serving Cell and the neighboring interfering cells when the neighboring serving Cell and the neighboring interfering cells are searched, and estimates channel coefficients from the serving Cell base station and the neighboring interfering Cell base stations to the relay node according to the detection result. The serving cell base station, the interfering cell base station, and the relay node generally have multiple antennas, and a channel coefficient estimated according to the CRS exists between each antenna. For example, the CRS of the serving cell is detected, and according to the detection result, the channel coefficient from the first transmit antenna of the serving cell base station to the first receive antenna of the relay node is determined. And obtaining a first channel matrix according to the channel coefficient from each transmitting antenna of the base station of the service cell to each receiving antenna of the relay node. For example, taking the number of the transmitting antennas of the serving cell base station as three, and the number of the receiving antennas of the relay node as four as an example, a channel coefficient estimated according to the CRS of the serving cell exists between each transmitting antenna of the serving cell base station and each receiving antenna of the relay node, so as to obtain a 4 × 3 first channel matrix. For example, the resulting first channel matrix may be as follows:
The elements in the first channel matrix are complex numbers, and each element represents a channel coefficient from each transmitting antenna of the serving cell base station to each receiving antenna of the relay node. For example, the second column element in the third row of the H matrix is the channel coefficient from the second transmitting antenna of the serving cell base station to the third receiving antenna of the relay node.
When calculating the IRC matrix on each subcarrier according to the first channel matrix, the calculation process may be: calculating an interference noise correlation matrix Ruu, multiplying a first channel matrix and a conjugate transpose matrix of the first channel matrix to obtain a first product, adding the first product and Ruu, carrying out inverse operation on a result obtained by the addition, multiplying a result obtained by the inverse operation and the conjugate transpose matrix of the first channel matrix, and taking a second product obtained by the multiplication as an IRC matrix. Wherein, the above calculation process can be expressed by the following formula (1):
Since signals are transmitted in an OFDM manner, that is, a radio frame is divided into a plurality of subframes for transmission in a multi-carrier manner, when calculating the IRC matrix, the IRC matrix on each subcarrier and in each subframe needs to be calculated respectively. In the above formula (1), the parameter k denotes a subcarrier number, and k is 0.., and NFFT-1, and NFFT denotes the size of FFT (Fast Fourier Transform) or IFFT (Inverse Fast Fourier Transform) of OFDM. The parameter l0 represents the sequence number of the subframe, and the value range of l0 can be from 1 to the total number of subframes obtained after the radio frame is divided.
h (k, l0) represents the first channel matrix in the sub-frame l0 on the sub-carrier k, H (k, l0) H represents the sub-carrier k, the conjugate transpose of the first channel matrix in the sub-frame l0 represents the interference noise correlation matrix in the sub-carrier k, the sub-frame l0, RN (Relay Node) represents the Relay Node itself, and Wf (k, l0) represents the first channel matrix in the sub-carrier k and the sub-frame l 0.
The embodiment does not specifically limit the way of calculating the interference noise correlation matrix Ruu, and includes, but is not limited to, the following two calculation ways:
A first calculation mode, which is to calculate a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, wherein the second channel matrix is a channel matrix from an interfering cell base station to the relay node; adding all the third products to obtain a first calculation result after addition; multiplying the noise power by the identity matrix to obtain a second calculation result; and adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu. Wherein, the above calculation process can be expressed by the following formula (2):
The parameter I represents the ith interfering cell base station, I represents the total number of adjacent interfering cells, Gi (k, l0-1) represents a second channel matrix from the ith interfering cell base station to the relay node in the subframe l0-1 on the subcarrier k, represents noise power, I represents an identity matrix, and Gi (k, l0-1) H represents a conjugate transpose matrix of the second channel matrix.
In the first calculation method, when the interference noise correlation matrix is calculated, the second channel matrixes from the base stations of the interference cells to the relay nodes are multiplied by the corresponding conjugate transpose matrix and then accumulated, so that the complexity of the calculation process is high. When the estimated second channel matrix has errors, the calculation result obtained by equation (2) has large errors due to error accumulation because of the accumulation process in equation (2) above.
it should be noted that the above calculation method may be used in a situation where the number of antennas of the interfering cell base station is more than two, and when the number of antennas of the interfering cell base station is two and the interfering cell base station adopts a specific transmission mode, because the codebook on the interfering cell base station side in the above situation is small, in order to avoid a large calculation error caused by error accumulation when the first calculation method is adopted and reduce complexity of a calculation process, when calculating the interference noise correlation matrix Ruu, besides performing calculation according to the current second channel matrix, Ruu of the previous subframe may be used to calculate Ruu of the current subframe, which is not specifically limited in this embodiment. The designated Transmission Mode may be TM2(Transmission Mode 2), TM3, or TM 4. Based on the above principle, the following second calculation method can be referred to for the process of calculating the interference noise correlation matrix Ruu.
The second calculation method is as follows: if the current subframe is positioned in the first subframe, multiplying the noise power by the unit matrix, and taking the obtained result as Ruu of the current subframe; if the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
According to the sequence number of the sub-frame after the sub-frame is divided, if the current sub-frame is in the first sub-frame, Ruu of the current sub-frame can be calculated according to the noise power and the unit matrix. Wherein, the above calculation process can be expressed by the following formula (3):
in the above formula (3), the parameter k represents a subcarrier sequence number and represents noise power, I represents an identity matrix, and the parameter 1 represents that the sequence number of the current subframe is 1, that is, the current subframe is the first subframe.
if the current subframe is not in the first subframe, calculating the current subframe according to instantaneous values Ruu of interference noise correlation arrays of a previous subframe and a previous subframe, wherein the calculation process can be represented by the following formula (4):
in the above formula (4), l represents the sequence number of the subframe where the current subframe is located, the value of l is greater than 1, k represents that the current subframe is located on the kth subcarrier, and Ruu (k, l-1) can be calculated by the formula (2). Through the iteration process of the above formula (4), the interference noise correlation matrix in each sub-frame l0 on each sub-carrier k can be calculated
it should be noted that, when the number of antennas of the base station in the adjacent interfering cell is two and TM2 is used, the adjacent interfering cell signal in Alamoutai adopting space-time block coding appears in the cell, and the statistical property of interference suppression in the adjacent interfering cell is the same as the effect when the adjacent interfering cell transmits two layers of data streams. Under codebook-based precoding by TM3 and TM4, the statistical process for the previous Ruu is equivalent to traversing various possible neighboring cell precoding. When the statistical time is long enough, the final interference suppression effect is also equivalent to that two layers of data streams are transmitted by adjacent interference cells. Therefore, the interference noise correlation matrix calculated by the above equations (3) and (4) is equivalent to a conservative estimation.
After the interference noise correlation matrix is obtained by the second calculation method, the following formula (5) may be used to calculate the IRC matrix:
It should be noted that, in the related art, when calculating the IRC matrix on the UE side, correlation processing is generally required to be performed after receiving a signal of one subframe from an adjacent interfering cell to a relay node. Therefore, when Ruu is calculated, the second channel matrix needs to be estimated according to the CRS of the adjacent interfering cells in the current subframe, and Ruu of all the adjacent interfering cells is calculated according to the precoding mode of the second channel matrix and the adjacent interfering cells. Wherein the above process can be expressed by the following formula (6):
In the above equation (6), UE represents user equipment, parameter I represents the ith interfering cell base station, I represents the total number of neighboring interfering cells, Gi (k, l0) represents the subcarrier k, a second channel matrix from the ith interfering cell base station to the relay node in subframe l0 represents noise power, I represents an identity matrix, Gi (k, l0) H represents a conjugate transpose matrix of the second channel matrix, Wi (k, l0) represents a precoding matrix between the ith neighboring interfering cell and user equipment in its own range, and Wi (k, l0) H represents a conjugate transpose matrix of the precoding matrix.
this embodiment uses the second channel matrix in the previous subframe instead of using the second information in the current subframe to the matrix as in equation (6) when calculating Ruu. Since the Ruu can be calculated according to the second channel matrix in the previous subframe in the embodiment, it is not necessary to calculate Ruu according to the second channel matrix in the current subframe after the current subframe is received, and therefore, the time delay generated when the signal is processed can be reduced.
in addition, since the neighboring interfering cells may schedule UEs with completely different channel conditions on each RB (Resource Block) of each subframe, the precoding manners of the neighboring interfering cells may change in different subframes, and the change is usually random and irregular. Accordingly, the precoding matrix within the previous subframe of the neighboring interfering cell may be completely different from the precoding matrix within the current subframe. If the embodiment uses the precoding matrix in the previous subframe of the neighboring interfering cell when calculating Ruu, the calculation performance of the IRC matrix will be seriously degraded, and even negative gain will be caused. Based on the above principle, the present embodiment does not adopt the method of commonly calculating Ruu in the related art when calculating Ruu.
it should be noted that, since the formula (2) is equivalent to regarding the adjacent interfering cells as full rank transmission, when Ruu is calculated by the formula (2), there may be performance degradation in the calculation result, but no negative gain is caused. In addition, when Wi (k, l0) in equation (6) is a unitary matrix, equation (2) is exactly the same as equation (6). Therefore, the calculation result obtained by the above formula (2) corresponds to a conservative estimated Ruu.
502. and selecting elements in the same row and column in the IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter.
for convenience of explanation, the IRC matrices in this step and the subsequent steps refer to IRC matrices in the same sub-frame as an example, that is, when the IRC matrices in each sub-carrier are selected, the IRC matrices in each sub-carrier in the same sub-frame are selected.
After obtaining the IRC matrix on each subcarrier through step 501, an element may be selected from each IRC matrix, and the selected elements form a vector. When the elements are selected from each IRC matrix, the elements of the same row and column are selected. For example, taking the number of subcarriers as 5 as an example, the elements in the first row and the first column in the IRC matrix on the first to fifth subcarriers may be respectively selected, and the selected elements are arranged according to the selection order, so as to obtain a vector including 5 elements. Wherein, the above process can be shown as the following formula (7):
in the above formula (7), the parameter i, j represents the ith row and the jth column of the matrix. [ Wf (0) ] i, j represents the ith row and jth column of the IRC matrix on the 0 th subcarrier, [ Wf (1) ] i, j represents the ith row and jth column of the IRC matrix on the 1 st subcarrier, [ Wf (NFFT-1) ] i, j represents the ith row and jth column of the IRC matrix on the NFFT-1 th subcarrier. The IFFT indicates that the vector composed of the elements selected from each IRC matrix is subjected to inverse fast fourier transform, so as to obtain a time domain IRC circular convolution filter under the premise of selecting the ith row and jth column elements. Through the above process, i × j time domain IRC circular convolution filters can be obtained.
it should be noted that the value range of the parameter i is from 1 to the total number of relay node forwarding antennas, and the value range of the parameter j is from 1 to the total number of relay node receiving antennas. Through the calculation process of the formula (7), the time domain IRC circular convolution filter between each receiving antenna and each forwarding antenna on the relay node can be obtained. For example, taking the number of receiving antennas of the relay node as 4 and the number of forwarding antennas as 2 as an example, 2 × 4 to 8 time-domain IRC circular convolution filters can be obtained, and a specific filter structure can be as shown in fig. 6.
503. And forming a time domain IRC linear convolution filter by the rear first preset value taps and the front second preset value taps in the time domain IRC circular convolution filter.
since the filter obtained in step 502 is an equivalent time domain circular convolution filter, and circular convolution is a correlation operation of cyclic shift, when calculating the initial output sampling point in an OFDM symbol time, it needs to use a point for the end output in the OFDM symbol time, that is, when the filter performs filtering processing on a signal, it needs to receive all the sampling points in the OFDM symbol time before performing circular convolution processing with the time domain circular convolution filter. The above process is equivalent to a delay of waiting for one OFDM symbol time when processing the signal.
in order to solve the problem of waiting time delay, time domain circular convolution operation is changed into time domain linear convolution operation in the step, and the specific process is to intercept a first preset value tap and a second preset value tap in a time domain IRC circular convolution filter, and form the intercepted taps into the time domain IRC linear convolution filter. Wherein, the above process can be shown as the following formula (8):
in the above formula (8), the last d2 taps in the time domain IRC circular convolution filter of the above formula (7) are represented, and the first d1 taps in the time domain IRC circular convolution filter of the above formula (7) are represented. It should be noted that, after the filter taps are truncated to form the time domain IRC linear convolution filter, the signal is processed by the time domain IRC linear convolution filter, which may reduce the interference suppression performance. When the signal is processed by the time domain IRC circular convolution filter, the complexity and delay in processing the signal may be increased due to the large number of taps. In order to compromise interference suppression performance and complexity and time delay when processing signals, according to results obtained by previous simulation, values of d1 and d2 can be between 100 and 300 time domain sampling points, and corresponding time delay is between 3 microseconds and 10 microseconds.
For example, a number of simulation results show that the time-domain IRC circular convolution filter has a shape as shown in fig. 7, with tap energies concentrated almost completely in the first and last taps, and almost no tap energy in the middle. Therefore, the last d2 taps and the first d1 taps in the time domain IRC circular convolution filter can be truncated, and the truncated taps are combined into the time domain IRC linear convolution filter shown in fig. 8.
Because the time domain IRC circular convolution filter needs to wait for one OFDM symbol time when processing a signal, and one OFDM symbol time is usually about 70 microseconds, the time delay generated when processing a signal can be greatly reduced by intercepting the taps to form the time domain IRC linear convolution filter.
504. when the time domain sampling point of the received signal is not the first time domain sampling point of the last preset value of one OFDM symbol, step 505 is executed, and when the time domain sampling point of the received signal is the first time domain sampling point of the last preset value of one OFDM symbol, step 506 is executed.
Since the relay node should be equivalent to frequency domain processing when performing time domain processing on the received signal, that is, the time domain IRC circular convolution filter should be sampled to process the signal, but in this embodiment, in order to avoid the delay caused by waiting for one OFDM symbol, a truncated linear convolution filter is sampled instead of the circular convolution filter. ISI (Inter Symbol Interference) may be introduced due to the processing of the signal by the sampling time domain IRC linear convolution filter, and the ISI of the linear convolution usually occurs in a CP (Cyclic Prefix) portion, a data header portion and a data tail portion of each OFDM Symbol.
the ISI of the tail portion data can be avoided by modified convolution, that is, when the time domain sample point of the received signal is the tail time domain sample point of one OFDM symbol, step 506 can be executed. In addition, when the time domain sample point of the received signal is not the end time domain sample point of one OFDM symbol, step 505 may be executed.
it should be noted that, before receiving a time domain sampling point at the tail of an OFDM symbol, step 506 needs to be executed subsequently, that is, the received time domain sampling point is processed in a circular convolution manner, so that, for convenience of performing the circular convolution subsequently, the time domain sampling point in the same OFDM symbol received before may be buffered.
505. and performing linear convolution processing on time domain sampling points of the received signal.
When the time domain sampling points of the received signals are subjected to linear convolution processing, the signal value of each time domain sampling point received by each receiving antenna can be multiplied by the corresponding filter tap, and all the multiplication results are superposed, so that the processing result after the signals received by each receiving antenna are processed is obtained. And superposing the processing results of each antenna, wherein the finally obtained superposition result is the processing result after the linear convolution processing is carried out on the received signal. Wherein the above process can be expressed by the following formula (9):
In the above equation (9), j represents the final processing result, j represents the several receiving antennas, N1 represents the total number of receiving antennas of the relay node, m is a variable set by the summation operation, is the (N-m) th tap in the time domain IRC linear convolution filter calculated in equation (8), and represents the m-th time domain sampling point in the signal received by the jth receiving antenna.
in addition, refer to fig. 9 or fig. 10. In either FIG. 9 or FIG. 10, the vertical boxes represent time-domain IRC linear convolution filters, with a length of d1+ d 2. The horizontal box is the signal to be processed, which can be divided into a plurality of OFDM symbols, each OFDM symbol including one CP and one Data. When the time-domain sampling points of the signal to be processed are CP portion or 0 to NFFT-d2-1 in Data portion, the signal can be subjected to linear convolution processing by using the above equation (9). The parameter n is the position coordinate to which the vertical line points in the vertical box as shown in fig. 9 or fig. 10.
506. and carrying out circular convolution processing on time domain sampling points of the received signal.
When the time domain sampling point of the received signal is processed by circular convolution, the time domain sampling point can be divided into two parts for processing, namely a part of the time domain IRC linear convolution filter which does not exceed one OFDM symbol and a part of the time domain IRC linear convolution filter which exceeds one OFDM symbol. For the two contents, the signal value of each time domain sampling point received by each receiving antenna can be multiplied by the corresponding filter tap, and all the multiplication results are superposed, so that the superposition result corresponding to the two contents is obtained. And adding the two superposition results to obtain a processing result after the signal received by each receiving antenna is processed. And superposing the processing results of each antenna, wherein the finally obtained superposition result is the processing result after performing circumferential convolution processing on the received signal. Wherein the above process can be expressed by the following formula (10):
n＝N-d,…,N-1
Referring to fig. 9 or fig. 11, in fig. 11, the left vertical box is the portion of the time domain IRC linear convolution filter beyond one OFDM symbol, and the corresponding overlap ranges from 0 to n + d2-NFFT + 1. The right vertical box is the portion of the time domain IRC linear convolution filter that does not exceed one OFDM symbol, with the corresponding overlap-add ranging from n-d1+1 to NFFT-1.
It should be noted that the methods provided in the foregoing steps can be implemented by a receiver baseband signal processing module in the relay node in a software improvement manner, and this embodiment is not particularly limited to this.
the method provided by the embodiment of the invention comprises the steps of calculating an IRC matrix on each subcarrier according to a first channel matrix, selecting elements with the same row and column in the IRC matrix on each subcarrier, carrying out inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter, forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter, and processing a time domain sampling point of a received signal according to the time domain IRC linear convolution filter. When the Ruu is calculated, the calculation is performed according to the second channel matrix in the previous subframe or the Ruu in the previous subframe, and the waiting time for the current subframe to be received is not required to be finished, so that the waiting time delay in signal processing is reduced. Meanwhile, the linear convolution filter is obtained by intercepting the taps in the circular convolution filter, and the signal is processed by the linear convolution filter, so that the number of taps passing through the signal processing is reduced, and the processed signal can be output only by waiting for the time domain sampling points with the first preset value, so that the complexity and the consumed time delay in signal processing are reduced.
In addition, the received signal can be processed by the linear convolution filter, so that the signal interference of adjacent interference cells can be inhibited, and the signal-to-noise ratio of the signal is improved when the signal is forwarded.
an embodiment of the present invention provides a signal processing apparatus, which is configured to execute the signal processing method provided in the embodiment corresponding to fig. 4 or fig. 5. Referring to fig. 12, the apparatus includes:
A calculating module 1201, configured to calculate an IRC matrix on each subcarrier according to a first channel matrix, where the first channel matrix is a channel matrix from a serving cell base station to each subcarrier of the relay node;
A selecting module 1202, configured to select elements in the same row and column in the IRC matrix on each subcarrier, and perform inverse fast fourier transform on a vector formed by the selected elements to obtain a time domain IRC circular convolution filter;
A forming module 1203, configured to form a time domain IRC linear convolution filter by using a last first preset number of taps and a last second preset number of taps in the time domain IRC circular convolution filter;
a processing module 1204, configured to process time-domain sample points of the received signal according to the time-domain IRC linear convolution filter.
As an alternative embodiment, the calculation module 1201 includes:
the first computing unit is used for computing an interference noise correlation matrix Ruu;
the second calculation unit is used for multiplying the first channel matrix and the conjugate transpose matrix of the first channel matrix to obtain a first product;
A third calculation unit, configured to add the first product to Ruu, and perform inverse operation on a result obtained by the addition;
and the fourth calculation unit is used for multiplying the result obtained by the inverse operation by the conjugate transpose matrix of the first channel matrix, and taking the second product obtained by the multiplication as the IRC matrix.
as an optional embodiment, the first calculating unit is configured to calculate a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, where the second channel matrix is a channel matrix from the interfering cell base station to the relay node; adding all the third products to obtain a first calculation result after addition; multiplying the noise power by the identity matrix to obtain a second calculation result; and adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
As an optional embodiment, when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, the first calculating unit is configured to multiply the noise power by the identity matrix when the interfering cell base station is currently in the first subframe, and take an obtained result as Ruu of the current subframe; if the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
As an optional embodiment, the processing module is configured to perform linear convolution processing on the time domain sampling points of the received signal when the time domain sampling points of the received signal are not the time domain sampling points of the first preset value after one OFDM symbol; and when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
According to the device provided by the embodiment of the invention, the IRC matrix on each subcarrier is calculated according to the first channel matrix, the elements of the same row and column in the IRC matrix on each subcarrier are selected, the vector formed by the selected elements is subjected to inverse fast Fourier transform to obtain a time domain IRC circumferential convolution filter, a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter form a time domain IRC linear convolution filter, and the time domain sampling point of a received signal is processed according to the time domain IRC linear convolution filter. The taps in the circular convolution filter are intercepted to obtain the linear convolution filter, and the signal is processed through the linear convolution filter, so that the taps passing through the signal processing are reduced, the processed signal can be output only by waiting for the time domain sampling points with the first preset value, and the complexity and the consumed time delay in the signal processing are reduced.
The embodiment of the invention provides a relay node. As shown in fig. 13, the relay node includes a transmitter 1301, a receiver 1302, a memory 1303, and a processor 1304 connected to the transmitter 1301, the receiver 1302, and the memory 1303, respectively. Wherein, a group of program codes is stored in the memory 1303, and the processor 1304 is configured to call the program codes stored in the memory 1303, and is configured to perform the following operations:
Calculating an IRC matrix on each subcarrier according to a first channel matrix, wherein the first channel matrix is a channel matrix from a serving cell base station to each subcarrier of the relay node;
Selecting elements of the same row and column in an IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter;
Forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circular convolution filter;
And processing time domain sampling points of the received signals according to the time domain IRC linear convolution filter.
as an alternative embodiment, the calculating an interference suppression combining IRC matrix on each subcarrier according to the first channel matrix includes:
Calculating an interference noise correlation matrix Ruu;
Multiplying the first channel matrix and a conjugate transpose matrix of the first channel matrix to obtain a first product;
Adding the first product and the Ruu, and performing inverse operation on a result obtained by the addition;
and multiplying the result obtained by the inverse operation by a conjugate transpose matrix of the first channel matrix, and taking a second product obtained by the multiplication as an IRC matrix.
as an alternative embodiment, the calculating of the interference noise correlation matrix Ruu includes:
calculating a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, where the second channel matrix is a channel matrix from the interfering cell base station to the relay node;
Adding all the third products to obtain a first calculation result after addition;
multiplying the noise power by the identity matrix to obtain a second calculation result;
And adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
as an optional embodiment, when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, the calculating the interference noise correlation matrix Ruu includes:
If the current subframe is positioned in the first subframe, multiplying the noise power by the unit matrix, and taking the obtained result as Ruu of the current subframe;
If the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
as an alternative embodiment, the processing the time-domain sample points of the received signal according to the time-domain IRC linear convolution filter includes:
When the time domain sampling point of the received signal is not the first preset value time domain sampling point after one OFDM symbol, performing linear convolution processing on the time domain sampling point of the received signal;
and when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
the relay node provided by the embodiment of the invention calculates the IRC matrix on each subcarrier according to the first channel matrix, selects elements with the same row and column in the IRC matrix on each subcarrier, performs inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter, forms a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter, and processes a time domain sampling point of a received signal according to the time domain IRC linear convolution filter. The taps in the circular convolution filter are intercepted to obtain the linear convolution filter, and the signal is processed through the linear convolution filter, so that the taps passing through the signal processing are reduced, the processed signal can be output only by waiting for the time domain sampling points with the first preset value, and the complexity and the consumed time delay in the signal processing are reduced.
it should be noted that: in the signal processing apparatus provided in the foregoing embodiment, when processing a signal, only the division of the functional modules is illustrated, and in practical applications, the above function distribution may be completed by different functional modules according to needs, that is, the internal structure of the apparatus is divided into different functional modules to complete all or part of the above described functions. In addition, the signal processing apparatus and the signal processing method provided by the above embodiments belong to the same concept, and specific implementation processes thereof are described in the method embodiments and are not described herein again.
it will be understood by those skilled in the art that all or part of the steps for implementing the above embodiments may be implemented by hardware, or may be implemented by a program instructing relevant hardware, where the program may be stored in a computer-readable storage medium, and the above-mentioned storage medium may be a read-only memory, a magnetic disk or an optical disk, etc.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents, improvements and the like that fall within the spirit and principle of the present invention are intended to be included therein.
Claims (8)
1. a method of signal processing, the method comprising:
calculating an interference noise correlation matrix Ruu;
multiplying a first channel matrix by a conjugate transpose matrix of the first channel matrix to obtain a first product, wherein the first channel matrix is a channel matrix from a serving cell base station to each subcarrier of the relay node;
adding the first product and the Ruu, and performing inverse operation on a result obtained by the addition;
Multiplying the result obtained by the inverse operation by a conjugate transpose matrix of the first channel matrix, and taking a second product obtained by the multiplication as an interference suppression combination IRC matrix on each subcarrier;
selecting elements of the same row and column in an IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter;
forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circular convolution filter;
and processing time domain sampling points of the received signals according to the time domain IRC linear convolution filter.
2. The method according to claim 1, wherein said calculating an interference noise correlation matrix Ruu comprises:
calculating a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, where the second channel matrix is a channel matrix from the interfering cell base station to the relay node;
Adding all the third products to obtain a first calculation result after addition;
Multiplying the noise power by the identity matrix to obtain a second calculation result;
And adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
3. The method according to claim 1, wherein when the number of antennas of the interfering cell base station is two and a specified transmission mode is adopted, the calculating the interference noise correlation matrix Ruu includes:
if the current subframe is positioned in the first subframe, multiplying the noise power by the unit matrix, and taking the obtained result as Ruu of the current subframe;
if the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
4. The method of claim 1, wherein processing time-domain samples of the received signal according to the time-domain IRC linear convolution filter comprises:
When the time domain sampling point of the received signal is not the first preset value time domain sampling point after the OFDM symbol, performing linear convolution processing on the time domain sampling point of the received signal;
and when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
5. A signal processing apparatus, characterized in that the apparatus comprises:
a calculating module, configured to calculate an interference noise correlation matrix Ruu, multiply a first channel matrix and a conjugate transpose matrix of the first channel matrix to obtain a first product, where the first channel matrix is a channel matrix from a serving cell base station to each subcarrier of the relay node, add the first product to the Ruu, perform inverse operation on an addition result, multiply a result obtained by the inverse operation and the conjugate transpose matrix of the first channel matrix, and use a second product obtained by the multiplication as an interference suppression combining IRC matrix on each subcarrier;
the selection module is used for selecting elements of the same row and column in the IRC matrix on each subcarrier, and performing inverse fast Fourier transform on a vector formed by the selected elements to obtain a time domain IRC circumferential convolution filter;
The forming module is used for forming a time domain IRC linear convolution filter by a first preset value tap and a second preset value tap in the time domain IRC circumferential convolution filter;
and the processing module is used for processing the time domain sampling points of the received signals according to the time domain IRC linear convolution filter.
6. the apparatus according to claim 5, wherein the first calculating unit is configured to calculate a third product between each second channel matrix and a conjugate transpose matrix of each second channel matrix, where the second channel matrix is a channel matrix from an interfering cell base station to the relay node; adding all the third products to obtain a first calculation result after addition; multiplying the noise power by the identity matrix to obtain a second calculation result; and adding the first calculation result and the second calculation result, and taking the result obtained after the addition as Ruu.
7. the apparatus according to claim 5, wherein when the number of antennas of the interfering cell base station is two and a specific transmission mode is adopted, the first calculating unit is configured to, when the current subframe is a first subframe, multiply the noise power by the identity matrix, and take the obtained result as Ruu of the current subframe; if the current subframe is not in the first subframe, calculating Ruu of the current subframe according to the sequence number of the current subframe and Ruu of a subframe before the current subframe.
8. the apparatus of claim 5, wherein the processing module is configured to perform linear convolution processing on the time domain samples of the received signal when the time domain samples of the received signal are not the first predetermined number of time domain samples of an OFDM symbol; and when the time domain sampling point of the received signal is the first preset value time domain sampling point after one OFDM symbol, performing circular convolution processing on the time domain sampling point of the received signal.
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102447658A (en) * | 2010-10-14 | 2012-05-09 | 中兴通讯股份有限公司 | Method and device for suppressing and merging interference |
| CN102780656A (en) * | 2011-05-11 | 2012-11-14 | 中兴通讯股份有限公司 | Method and device for eliminating multi-symbol subcarrier jamming and performing channel estimation jointly |
| CN103475602A (en) * | 2013-09-16 | 2013-12-25 | 东南大学 | MIMO-OFDM channel estimation method considering same frequency interference |
| CN104243384A (en) * | 2013-06-24 | 2014-12-24 | 北京大学 | Method for restraining inter-subcarrier interference through precoding based on OFDM system |
| CN104716982A (en) * | 2015-03-25 | 2015-06-17 | 北京北斗星通导航技术股份有限公司 | Robust anti-interference processing method and device of spread frequency system |
-
2015
- 2015-06-26 CN CN201510364047.0A patent/CN106330793B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102447658A (en) * | 2010-10-14 | 2012-05-09 | 中兴通讯股份有限公司 | Method and device for suppressing and merging interference |
| CN102780656A (en) * | 2011-05-11 | 2012-11-14 | 中兴通讯股份有限公司 | Method and device for eliminating multi-symbol subcarrier jamming and performing channel estimation jointly |
| CN104243384A (en) * | 2013-06-24 | 2014-12-24 | 北京大学 | Method for restraining inter-subcarrier interference through precoding based on OFDM system |
| CN103475602A (en) * | 2013-09-16 | 2013-12-25 | 东南大学 | MIMO-OFDM channel estimation method considering same frequency interference |
| CN104716982A (en) * | 2015-03-25 | 2015-06-17 | 北京北斗星通导航技术股份有限公司 | Robust anti-interference processing method and device of spread frequency system |
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