CN105577021B - A kind of single SVM methods of twin inverter - Google Patents
A kind of single SVM methods of twin inverter Download PDFInfo
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- CN105577021B CN105577021B CN201610008464.6A CN201610008464A CN105577021B CN 105577021 B CN105577021 B CN 105577021B CN 201610008464 A CN201610008464 A CN 201610008464A CN 105577021 B CN105577021 B CN 105577021B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53873—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with digital control
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/085—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation wherein the PWM mode is adapted on the running conditions of the motor, e.g. the switching frequency
Abstract
The invention discloses a kind of twin inverter based on single SVM methods, the modulator approach is using two inverters as an entirety, control two two-level inverters powered by any ratio isolated DC power supply simultaneously using single SVM modulation algorithms, control algolithm is simplified, raising accelerates the speed of service.Simultaneously, the on-off times of twin inverter list SVM methods of the present invention are only the 1/3 of the double SVM methods of conventional twin inverter, reduce the switching loss of system, improve the operational efficiency of system, therefore present invention can apply to the control field of twin inverter, the control for opening the occasion such as winding electric machine system, double converter grid-connected systems such as powered by twin inverter.
Description
Technical field
The invention belongs to technical field of inverter control, and in particular to a kind of single SVM methods of twin inverter.
Background technology
With the development of modern power electronics technology, inverter is in electric automobile, power-driven ship and development of renewable energy
It is widely used in electricity.But the power rating of single power electronic devices limits, and prevents inverter high-power from meeting
The demand of application.The topological structure connected using twin inverter can obtain the control effect of bigger power and more level, reach
To the purpose of high-power output.When the DC bus-bar voltage ratio of two level twin inverters does not wait, can obtain equivalent to two electricity
The control effect of flat, three level, four level or even more level, more level can reduce current harmonics, reduce switching device stress.
Current this kind of twin inverter control strategy is controlled according to two DC bus powered voltage ratios completely, and algorithm is complicated, and
In practical application, the supply voltage ratio of two dc bus is non-artificial controllable, therefore control lacks flexible.
Document 1 (" Discontinuous Decoupled PWMs for Reduced Current Ripple in a
Dual Two-Level Inverter Fed Open-End Winding Induction Motor Drive,"
K.R.Sekhar et.al,Power Electronics,IEEE Transactions on Power Electronics,
2013) the modulation voltage vector in system is divided into two equal voltage vectors of amplitude, voltage needed for each inverter is sweared
Amount is by independent traditional SVM (space vector modulation) algorithm, to generate the switching pulse signal needed for each inverter, this
When, the switching loss of twin inverter is larger.Document 2 (" Two-quadrant clamping inverter scheme for
three-level open-end winding induction motor drive,"S.Pradabane et.al,Power
Electronics, Drives and Energy Systems (PEDES), 2014) switch working state of twin inverter is entered
In-depth study is gone, it is proposed that the alternating clamper work of two inverters, the half of each free-running system modulation voltage rotating range
Method, largely reduce switching loss, but this modulation algorithm omits in the subregion of modulation voltage vector plane
Aobvious redundancy, while current harmonics is added, and based on the equal condition of work of two DC bus powered voltages.
Therefore, inverter switching frequency can be reduced by needing exploration one kind badly, and and can ensures twin inverter in dc bus electricity
Remain valid the modulator approach of operation in the case of pressing as any ratio.
The content of the invention
For the above-mentioned technical problem present in prior art, the invention provides a kind of single SVM methods of twin inverter,
Can reduce the switching loss of twin inverter, and can ensure twin inverter in the case where DC bus-bar voltage is any ratio after
Continuous effectively operation.
A kind of single SVM methods of twin inverter, comprise the following steps：
(1) DC bus-bar voltage V corresponding to two inverters INV1 and INV2 is gathered respectivelydc1And Vdc2；
(2) modulation voltage for trying to achieve twin inverter according to calculating, the amplitude V of the modulation voltage is extractedsAnd modulation electricity
Pressure and the angle theta of α axles；
(3) according to amplitude Vs, angle theta and DC bus-bar voltage Vdc1And Vdc2, calculate and determine two groups of effective voltages arrows
Measure VxAnd VyAnd its corresponding action time txAnd ty；
(4) according to action time txAnd tyWith device for power switching switch periods TsMagnitude relationship, to effective voltage vector
VxAnd VyIt is allocated to determine the effective voltage vector V needed for inverter INV11xAnd V1yAnd its corresponding action time t1xWith
t1yAnd the effective voltage vector V needed for inverter INV22xAnd V2yAnd its corresponding action time t2xAnd t2y；
(5) according to effective voltage vector V1xAnd V1yAnd its corresponding action time t1xAnd t1yGenerate the three of inverter INV1
Phase switching signal S1a~S1c, according to effective voltage vector V2xAnd V2yAnd its corresponding action time t2xAnd t2yGenerate inverter
INV2 threephase switch signal S2a~S2c；And then utilize threephase switch signal S1a~S1cAnd S2a~S2cAfter drive amplification respectively
Device for power switching in inverter INV1 and INV2 is controlled.
Two groups of effective voltage vector V are determined in described step (3)xAnd VySpecific standards it is as follows：
If θ ∈ [0, π/3), described modulation voltage is located at the first sector, then effective voltage vector Vx=V1(100), effectively
Voltage vector Vy=V2(110)；
If θ ∈ [π/3,2 π/3), described modulation voltage is located at the second sector, then effective voltage vector Vx=V3(010),
Effective voltage vector Vy=V2(110)；
If θ ∈ [2 π/3, π), described modulation voltage is located at the 3rd sector, then effective voltage vector Vx=V3(010), have
Imitate voltage vector Vy=V4(011)；
If θ ∈ [π, 4 π/3), described modulation voltage is located at the 4th sector, then effective voltage vector Vx=V5(001), have
Imitate voltage vector Vy=V4(011)；
If θ ∈ [4 π/3,5 π/3), described modulation voltage is located at the 5th sector, then effective voltage vector Vx=V5(001),
Effective voltage vector Vy=V6(101)；
If θ ∈ [5 π/3,2 π), described modulation voltage is located at the 6th sector, then effective voltage vector Vx=V1(100), have
Imitate voltage vector Vy=V6(101)；
Wherein：V1(100) the threephase switch signal corresponding to is respectively 1,0,0, that is, represents the work(of bridge arm in inverter A phases
The device for power switching conducting of bridge arm under rate switch device conductive, B phases and C phases；V2(110) the threephase switch signal point corresponding to
Not Wei 1,1,0, that is, represent the device for power switching conducting of bridge arm in inverter A phases and B phases, the power switch device of bridge arm under C phases
Part turns on；V3(010) the threephase switch signal corresponding to is respectively 0,1,0, that is, represents the power switch of bridge arm in inverter B phases
The device for power switching conducting of bridge arm under break-over of device, A phases and C phases；V4Threephase switch signal corresponding to (011) is respectively 0,
1st, 1, that is, represent that the device for power switching of bridge arm in inverter B phases and C phases turns on, the device for power switching conducting of bridge arm under A phases；
V5(001) the threephase switch signal corresponding to is respectively 0,0,1, that is, represents that the device for power switching of bridge arm in inverter C phases is led
It is logical, the device for power switching conducting of bridge arm under A phases and B phases；V6(101) the threephase switch signal corresponding to is respectively 1,0,1, i.e.,
Represent that the device for power switching of bridge arm in inverter A phases and C phases turns on, the device for power switching conducting of bridge arm under B phases.
Two groups of effective voltage vector V are calculated by below equation in described step (3)xAnd VyCorresponding action time tx
And ty：
If the numbering N of sector residing for modulation voltage is odd number：
If the numbering N of sector residing for modulation voltage is even number：
Wherein：Vdc=(Vdc1+Vdc2)/2。
To effective voltage vector V in described step (4)xAnd VyThe specific standards being allocated are as follows：
IfAndThen make effective voltage vector V1x=Vx, V1y=0, V2y=-Vy, V2x=-
Vx, corresponding action time t1x=Ts, t1y=0,
IfAndThen make effective voltage vector V1x=Vx, V1y=0, V2y=-Vy, V2x=
0, corresponding action timet1y=0,t2x=0；
IfAndThen make effective voltage vector V1x=Vx, V1y=Vy, V2y=-Vy, V2x=
0, corresponding action timet2y=Ts, t2x=0.
Wherein：-VxExpression and VxThe opposite effective voltage vector of corresponding switching signal state ,-VyExpression and VyIt is corresponding
The opposite effective voltage vector of switching signal state.
Twin inverter modulator approach of the present invention is treated two inverters as an entirety, with a SVM algorithm simultaneously
Two two-level inverters powered by isolated DC power supply are controlled, control algolithm is simplified, accelerates the speed of service.It is same with this
When, the single SVM algorithm of the present invention reduces the on-off times of system to the 1/3 of the double SVM algorithms of conventional twin inverter, improves system
Operational efficiency, in turn ensure that two inverters remain valid operation in the case where DC bus-bar voltage is any ratio.Therefore this
Invention can be applied to the control field of twin inverter, as what twin inverter was powered opens winding electric machine system, double grid-connected systems of converter
The occasions such as system.
Brief description of the drawings
Fig. 1 is out the structural representation of winding permanent magnet synchronous motor system.
Fig. 2 is out the system block diagram of winding permanent magnet synchronous motor system control method.
Fig. 3 (a) is synthesis schematic diagram of the present invention in sector N=1 regions 1. internal modulation voltage.
Fig. 3 (b) is synthesis schematic diagram of the present invention in sector N=1 regions 2. internal modulation voltage.
Fig. 3 (c) is synthesis schematic diagram of the present invention in sector N=1 regions 3. internal modulation voltage.
Fig. 4 is the switching signal figure of an inverter in conventional double SVM modulation.
Fig. 5 (a) be in the present invention single SVM modulation inverter INV1 in the 1. interior switching signal signal of sector N=1 regions
Figure.
Fig. 5 (b) be in the present invention single SVM modulation inverter INV1 in the 2. interior switching signal signal of sector N=1 regions
Figure.
Fig. 5 (c) be in the present invention single SVM modulation inverter INV1 in the 3. interior switching signal signal of sector N=1 regions
Figure.
Fig. 6 (a) be in the present invention single SVM modulation inverter INV2 in the 1. interior switching signal signal of sector N=1 regions
Figure.
Fig. 6 (b) be in the present invention single SVM modulation inverter INV2 in the 2. interior switching signal signal of sector N=1 regions
Figure.
Fig. 6 (c) be in the present invention single SVM modulation inverter INV2 in the 3. interior switching signal signal of sector N=1 regions
Figure.
Fig. 7 (a) is that winding electric machine is opened under control method of the present invention with 3Nm load runnings in 500r/min A phases stator electricity
Flow IaOscillogram.
Fig. 7 (b) is to open winding electric machine with 3Nm load runnings in 500r/min torque T under control method of the present inventioneWaveform
Figure.
Fig. 7 (c) is that winding electric machine band 3Nm load runnings are opened under control method of the present invention in 500r/min system inverters
Bridge arm input pulse INV1-A oscillograms in INV1 A phases.
Fig. 7 (d) is that winding electric machine band 3Nm load runnings are opened under control method of the present invention in 500r/min systems sector
Sector oscillograms.
Fig. 7 (e) is to open winding electric machine with 3Nm load runnings in the A of 500r/min system motors under control method of the present invention
Phase stator current IaFrequency analysis figure.
Fig. 8 (a) is that winding electric machine is opened under control method of the present invention with 3Nm load runnings in 1500r/min A phases stator electricity
Flow IaOscillogram.
Fig. 8 (b) is to open winding electric machine with 3Nm load runnings in 1500r/min torque T under control method of the present inventioneRipple
Shape figure.
Fig. 8 (c) is that winding electric machine band 3Nm load runnings are opened under control method of the present invention in 1500r/min system inverters
Bridge arm input pulse INV1-A oscillograms in INV1 A phases.
Fig. 8 (d) is that winding electric machine band 3Nm load runnings are opened under control method of the present invention in 1500r/min systems sector
Sector oscillograms.
Fig. 8 (e) is to open winding electric machine with 3Nm load runnings in the A of 1500r/min system motors under control method of the present invention
Phase stator current IaFrequency analysis figure.
Embodiment
In order to more specifically describe the present invention, below in conjunction with the accompanying drawings and embodiment is to technical scheme
It is described in detail.
As shown in figure 1, this example electric system by dc source 1, electric capacity of voltage regulation 2, dc source 3, electric capacity of voltage regulation 4,
INV1 inverters 5, open winding permanent magnet synchronous motor 6, INV2 inverters 7, photoelectric coded disk 8, three-phase current sensor 9, INV1
Inverter DC bus-bar voltage sensor 10, INV2 inverter DC bus-bar voltages sensor 11 and controller 12 etc. form.
As shown in Fig. 2 present embodiment is based on a kind of isolated DC voltage fed by two free voltage ratios
Twin inverter list SVM methods are controlled to Fig. 1 electric system, are specifically comprised the following steps：
(1) signal acquisition.
The rotor position angle θ for driving winding permanent magnet synchronous motor 6 is gathered using photoelectric coded disk 8r, rotational speed omega is obtained, is utilized
The threephase stator current signal i of winding permanent magnet synchronous motor 6 is opened in the collection of three-phase current sensor 9a、ib、ic, utilize INV1 inverters
DC bus-bar voltage sensor 10 gathers the DC bus-bar voltage V of INV1 inverters 5dc1, utilize INV2 inverters dc bus electricity
Pressure sensor 11 gathers the DC bus-bar voltage V of INV2 inverters 7dc2。
(2) signal converts.
The three-phase current signal i that step (1) is collecteda、ib、icConverted, obtained in two-phase rotating coordinate system by Park
Stator current dq axis components id, iq, calculation formula is：
(3) the set-point i of d shaft currents is calculatedd *, the set-point i of q shaft currentsq *：
Make d shaft current set-points id *For 0.According to rotor speed ω and given rotating speed ω*Difference Δ ω, obtained through PI controllers
To the set-point i of q shaft currentsq *。
(4) d shaft voltage set-points V is calculatedd *：
D shaft current set-points id *With d shaft current values of feedback idDifference input pi regulator, obtain d shaft voltage calculated values
Vdm *, d shaft voltage calculated values Vdm *With d shaft voltage offsets Vdffd=-ω LqiqIt is added, obtains d shaft voltage set-points Vd *, wherein
LqFor q axle inductances.
(5) q shaft voltage set-points V is calculatedq *：
The given i of q shaft currentsq *With q shaft current values of feedback iqDifference pass through pi regulator, obtain q shaft voltage calculated values
Vqm *, q shaft voltage calculated values Vqm *With q shaft voltage offsets Vqffd=ω (Ldid+ψf) be added, obtain q shaft voltage set-points Vq *；
Wherein LdFor d axle inductances, ψfFor permanent magnet flux linkage.
(6) the amplitude V of modulation voltage is calculatedsWith the angle theta of modulation voltage and α axles：
(7) calculate and determine effective voltage vector VxAnd VyAnd its corresponding action time tx, ty：
7.1 utilize angle theta scope according to determination effective voltage vector VxAnd Vy, as shown in table 1；This embodiment party shown in Fig. 3
The modulation voltage that formula obtains is located at the schematic diagram in sector 1.
Table 1
| θ scopes | Sector N | Vx | Vy |
| [0,π/3) | 1 | V1(100) | V2(110) |
| [π/3,2π/3) | 2 | V3(010) | V2(110) |
| [2π/3,π) | 3 | V3(010) | V4(011) |
| [π,4π/3) | 4 | V5(001) | V4(011) |
| [4π/3,5π/3) | 5 | V5(001) | V6(101) |
| [5π/3,2π) | 6 | V1(100) | V6(101) |
7.2 calculate effective voltage vector V according to following formulax, VyEach self-corresponding time txAnd ty:
If the numbering N of sector residing for modulation voltage is odd number：
If the numbering N of sector residing for modulation voltage is even number：
Wherein：Vdc=(Vdc1+Vdc2)/2。
(8) the first effective voltage vector V needed for INV1 inverters 5 is determined1x, the second effective voltage vector V1yIt is right with its
The action time t answered1x, t1yWith the first effective voltage vector V needed for determination INV2 inverters 72x, the second effective voltage vector
V2yAction time t corresponding with its2x, t2y：
IfAndThen select vector V1x=Vx, V1y=0, V2y=-Vy, V2x=-Vx, selection
Vector action time is t1x=Ts, t1y=0,
IfAndThen select vector V1x=Vx, V1y=0, V2y=-Vy, V2x=0, selection arrow
Amount action time bet1y=0,t2x=0.
IfAndThen select vector V1x=Vx, V1y=Vy, V2y=-Vy, V2x=0, selection arrow
Amount action time bet2y=Ts, t2x=0.
Wherein：If modulation voltage is at the first sector, Vx=V1(100), Vy=V2(110) ,-VxExpression and VxIt is corresponding to open
The opposite effective voltage vector of OFF signal state ,-VyExpression and VyThe opposite effective voltage vector of corresponding switching signal state,
Now ,-Vx=V4(011) ,-Vy=V5(001)。
Remaining interval I NV1 inverters 5 and INV2 inverters 7 in switch periods select zero vector V0(000)。
(9) according to the first effective voltage vector V of INV1 inverters 51x, the second effective voltage vector V1yWith its corresponding work
With time t1x, t1yWith the first effective voltage vector V needed for INV2 inverters 72x, the second effective voltage vector V2yIt is corresponding with it
Action time t2x, t2y, thereby determine that on twin inverter that bridge arm corresponds to ON time corresponding to switching tube, and with given triangular wave
Compare, obtain the threephase switch signal S of INV1 inverters 5 and INV2 inverters 71a~S1cAnd S2a~S2c；Believed using threephase switch
Number S1a~S1cAnd S2a~S2cControl INV1 inverters 5 and INV2 inverters 7 respectively after drive circuit, and then control and open winding
Permagnetic synchronous motor 4.
We are tested present embodiment below, the used parameter for the driving winding permanent magnet synchronous motor such as institute of table 2
Show：
Table 2
Observe Fig. 3 to understand, in sector during N=1, meetAndRelation, corresponding region is 1.；It is full
FootAndRelation, corresponding region is 2.；MeetAndRelation, corresponding area
Domain is 3..From Fig. 4, Fig. 5 and Fig. 6, in a switch periods, twin inverter needs out conventional double SVM modulation algorithms altogether
Pass acts 6*2=12 times, and the twin inverter list SVM modulation algorithms of present embodiment need to switch altogether in a switch periods
Action 4 times, on-off times is reduced to the 1/3 of the double SVM modulation of twin inverter, specifically refer to Fig. 7 (c) and Fig. 8 (c) INV1 are inverse
Become bridge arm pulse output in the A phases of device 5 to understand.
Fig. 7 and Fig. 8 is respectively to open winding permanent magnet synchronous motor bringing onto load under present embodiment control to run on different turn
A phases stator current I when fasta, torque Te, bridge arm input pulse INV1-A, sector Sector and A phase stator current I in A phasesaIt is humorous
The test waveform figure of ripple.Fig. 7 (b) and Fig. 8 (b) are observed as can be seen that output torque is steady under different rotating speeds, (- 0.1,
+ 0.1) fluctuated between Nm, or even fluctuation is smaller during high speed.Fig. 7 (e) and Fig. 8 (e) is observed, the equal very little of both current harmonics, is shown
Motor operation performance is fine under control method of the present invention.
In summary, single SVM algorithm of the invention can be realized double inverse under the conditions of any ratio of two DC bus-bar voltages
Become the high performance control of device, the on-off times of twin inverter are significantly reduced, and improve the operational efficiency of system.
Claims (3)
1. a kind of single SVM methods of twin inverter, comprise the following steps：
(1) DC bus-bar voltage V corresponding to two inverters INV1 and INV2 is gathered respectivelydc1And Vdc2；
(2) modulation voltage for trying to achieve twin inverter according to calculating, the amplitude V of the modulation voltage is extractedsAnd the modulation voltage and α
The angle theta of axle；
(3) according to amplitude Vs, angle theta and DC bus-bar voltage Vdc1And Vdc2, calculate and determine two groups of effective voltage vector VxWith
VyAnd its corresponding action time txAnd ty；
(4) according to action time txAnd tyWith device for power switching switch periods TsMagnitude relationship, to effective voltage vector VxWith
VyIt is allocated to determine the effective voltage vector V needed for inverter INV11xAnd V1yAnd its corresponding action time t1xAnd t1yWith
And the effective voltage vector V needed for inverter INV22xAnd V2yAnd its corresponding action time t2xAnd t2y, specific allocation criterion is such as
Under：
IfAndThen make effective voltage vector V1x=Vx, V1y=0, V2y=-Vy, V2x=-Vx, it is right
The action time t answered1x=Ts, t1y=0,
IfAndThen make effective voltage vector V1x=Vx, V1y=0, V2y=-Vy, V2x=0, it is corresponding
Action timet1y=0,t2x=0；
IfAndThen make effective voltage vector V1x=Vx, V1y=Vy, V2y=-Vy, V2x=0, it is corresponding
Action timet2y=Ts, t2x=0；
Wherein：Vdc=(Vdc1+Vdc2)/2 ,-VxExpression and VxThe opposite effective voltage vector of corresponding switching signal state ,-VyTable
Show and VyThe opposite effective voltage vector of corresponding switching signal state；
(5) according to effective voltage vector V1xAnd V1yAnd its corresponding action time t1xAnd t1yGeneration inverter INV1 three-phase is opened
OFF signal S1a~S1c, according to effective voltage vector V2xAnd V2yAnd its corresponding action time t2xAnd t2yGenerate inverter INV2's
Threephase switch signal S2a~S2c；And then utilize threephase switch signal S1a~S1cAnd S2a~S2cRespectively to inversion after drive amplification
Device for power switching in device INV1 and INV2 is controlled.
2. single SVM methods according to claim 1, it is characterised in that：Two groups of effective voltages are determined in described step (3)
Vector VxAnd VySpecific standards it is as follows：
If θ ∈ [0, π/3), described modulation voltage is located at the first sector, then effective voltage vector Vx=V1(100), effective voltage
Vector Vy=V2(110)；
If θ ∈ [π/3,2 π/3), described modulation voltage is located at the second sector, then effective voltage vector Vx=V3(010), effectively
Voltage vector Vy=V2(110)；
If θ ∈ [2 π/3, π), described modulation voltage is located at the 3rd sector, then effective voltage vector Vx=V3(010) it is, effectively electric
Press vector Vy=V4(011)；
If θ ∈ [π, 4 π/3), described modulation voltage is located at the 4th sector, then effective voltage vector Vx=V5(001) it is, effectively electric
Press vector Vy=V4(011)；
If θ ∈ [4 π/3,5 π/3), described modulation voltage is located at the 5th sector, then effective voltage vector Vx=V5(001), effectively
Voltage vector Vy=V6(101)；
If θ ∈ [5 π/3,2 π), described modulation voltage is located at the 6th sector, then effective voltage vector Vx=V1(100) it is, effectively electric
Press vector Vy=V6(101)；
Wherein：V1(100) the threephase switch signal corresponding to is respectively 1,0,0, that is, represents that the power of bridge arm in inverter A phases is opened
Break-over of device is closed, the device for power switching conducting of bridge arm under B phases and C phases；V2(110) the threephase switch signal corresponding to is respectively
1st, 1,0, that is, represent that the device for power switching of bridge arm in inverter A phases and B phases turns on, the device for power switching of bridge arm is led under C phases
It is logical；V3(010) the threephase switch signal corresponding to is respectively 0,1,0, that is, represents the device for power switching of bridge arm in inverter B phases
Turn on, the device for power switching conducting of bridge arm under A phases and C phases；V4(011) the threephase switch signal corresponding to is respectively 0,1,1,
Represent that the device for power switching of bridge arm in inverter B phases and C phases turns on, the device for power switching conducting of bridge arm under A phases；V5
(001) the threephase switch signal corresponding to is respectively 0,0,1, that is, represents the device for power switching conducting of bridge arm in inverter C phases,
The device for power switching conducting of bridge arm under A phases and B phases；V6(101) the threephase switch signal corresponding to is respectively 1,0,1, i.e. table
Show that the device for power switching of bridge arm in inverter A phases and C phases turns on, the device for power switching conducting of bridge arm under B phases.
3. single SVM methods according to claim 2, it is characterised in that：Calculated in described step (3) by below equation
Two groups of effective voltage vector VxAnd VyCorresponding action time txAnd ty：
If the numbering N of sector residing for modulation voltage is odd number：
<mrow>
<msub>
<mi>t</mi>
<mi>x</mi>
</msub>
<mo>=</mo>
<mfrac>
<mrow>
<msqrt>
<mn>3</mn>
</msqrt>
<msub>
<mi>V</mi>
<mi>s</mi>
</msub>
</mrow>
<msub>
<mi>V</mi>
<mrow>
<mi>d</mi>
<mi>c</mi>
</mrow>
</msub>
</mfrac>
<msub>
<mi>T</mi>
<mi>s</mi>
</msub>
<mi>s</mi>
<mi>i</mi>
<mi>n</mi>
<mrow>
<mo>(</mo>
<mi>N</mi>
<mo>&CenterDot;</mo>
<mfrac>
<mi>&pi;</mi>
<mn>3</mn>
</mfrac>
<mo>-</mo>
<mi>&theta;</mi>
<mo>)</mo>
</mrow>
</mrow>
<mrow>
<msub>
<mi>t</mi>
<mi>y</mi>
</msub>
<mo>=</mo>
<mfrac>
<mrow>
<msqrt>
<mn>3</mn>
</msqrt>
<msub>
<mi>V</mi>
<mi>s</mi>
</msub>
</mrow>
<msub>
<mi>V</mi>
<mrow>
<mi>d</mi>
<mi>c</mi>
</mrow>
</msub>
</mfrac>
<msub>
<mi>T</mi>
<mi>s</mi>
</msub>
<mi>s</mi>
<mi>i</mi>
<mi>n</mi>
<mrow>
<mo>(</mo>
<mi>&theta;</mi>
<mo>-</mo>
<mo>(</mo>
<mrow>
<mi>N</mi>
<mo>-</mo>
<mn>1</mn>
</mrow>
<mo>)</mo>
<mfrac>
<mi>&pi;</mi>
<mn>3</mn>
</mfrac>
<mo>)</mo>
</mrow>
</mrow>
If the numbering N of sector residing for modulation voltage is even number：
<mrow>
<msub>
<mi>t</mi>
<mi>x</mi>
</msub>
<mo>=</mo>
<mfrac>
<mrow>
<msqrt>
<mn>3</mn>
</msqrt>
<msub>
<mi>V</mi>
<mi>s</mi>
</msub>
</mrow>
<msub>
<mi>V</mi>
<mrow>
<mi>d</mi>
<mi>c</mi>
</mrow>
</msub>
</mfrac>
<msub>
<mi>T</mi>
<mi>s</mi>
</msub>
<mi>s</mi>
<mi>i</mi>
<mi>n</mi>
<mrow>
<mo>(</mo>
<mi>&theta;</mi>
<mo>-</mo>
<mo>(</mo>
<mrow>
<mi>N</mi>
<mo>-</mo>
<mn>1</mn>
</mrow>
<mo>)</mo>
<mfrac>
<mi>&pi;</mi>
<mn>3</mn>
</mfrac>
<mo>)</mo>
</mrow>
</mrow>
<mrow>
<msub>
<mi>t</mi>
<mi>y</mi>
</msub>
<mo>=</mo>
<mfrac>
<mrow>
<msqrt>
<mn>3</mn>
</msqrt>
<msub>
<mi>V</mi>
<mi>s</mi>
</msub>
</mrow>
<msub>
<mi>V</mi>
<mrow>
<mi>d</mi>
<mi>c</mi>
</mrow>
</msub>
</mfrac>
<msub>
<mi>T</mi>
<mi>s</mi>
</msub>
<mi>s</mi>
<mi>i</mi>
<mi>n</mi>
<mrow>
<mo>(</mo>
<mi>N</mi>
<mo>&CenterDot;</mo>
<mfrac>
<mi>&pi;</mi>
<mn>3</mn>
</mfrac>
<mo>-</mo>
<mi>&theta;</mi>
<mo>)</mo>
</mrow>
</mrow>
Wherein：Vdc=(Vdc1+Vdc2)/2。
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| CN104320013A (en) * | 2014-11-06 | 2015-01-28 | 东南大学 | Double-inverter common-mode voltage restraining method based on 60-degree coordinate system |
| CN104362923A (en) * | 2014-11-05 | 2015-02-18 | 东南大学 | Decoupling SVPWM (space vector pulse width modulation) based fault tolerance control method for open-winding PMSM (permanent magnet synchronous motor) driving system |
| CN104506070A (en) * | 2015-01-21 | 2015-04-08 | 哈尔滨工业大学 | Method for modulating space vectors of double inverters |
| CN104753419A (en) * | 2015-03-19 | 2015-07-01 | 浙江大学 | Voltage cutting method based control method for open-winding permanent synchronizing motor system |
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| CN104362923A (en) * | 2014-11-05 | 2015-02-18 | 东南大学 | Decoupling SVPWM (space vector pulse width modulation) based fault tolerance control method for open-winding PMSM (permanent magnet synchronous motor) driving system |
| CN104320013A (en) * | 2014-11-06 | 2015-01-28 | 东南大学 | Double-inverter common-mode voltage restraining method based on 60-degree coordinate system |
| CN104506070A (en) * | 2015-01-21 | 2015-04-08 | 哈尔滨工业大学 | Method for modulating space vectors of double inverters |
| CN104753419A (en) * | 2015-03-19 | 2015-07-01 | 浙江大学 | Voltage cutting method based control method for open-winding permanent synchronizing motor system |
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