CN105471395A - Compression control adjusted through power amplifier load - Google Patents

Compression control adjusted through power amplifier load Download PDF

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Publication number
CN105471395A
CN105471395A CN201510634729.9A CN201510634729A CN105471395A CN 105471395 A CN105471395 A CN 105471395A CN 201510634729 A CN201510634729 A CN 201510634729A CN 105471395 A CN105471395 A CN 105471395A
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China
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power amplifier
transistor
voltage
reference signal
matching network
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CN201510634729.9A
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CN105471395B (en
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D·S·里普利
P·J·莱托拉
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Skyworks Solutions Inc
Conexant Systems LLC
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Conexant Systems LLC
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Abstract

Provided is compression control adjusted through power amplifier load. A power amplifier module can comprise a power amplifier. The power amplifier comprises a common-emitter common-base transistor pair. The common-emitter common-base transistor pair comprises a first transistor and a second transistor. The power amplifier module comprises a power amplifier bias controller and a current comparator. The current comparator is configured to compare the first base current of the first transistor the second base current of the second transistor, to obtain a comparison value. The power amplifier module comprises a saturation controller which is configured to provide reference signals to an impedance matching network based the comparison value. The impedance matching network can be configured to change load impedance of a load line which communicates with the power amplifier at least partially based on the reference signal.

Description

By the compression control that power amplifier load adjusts
The cross reference of related application
This application claims the U.S. Provisional Application the 62/097th that the denomination of invention submitted on December 30th, 2014 is " COMPRESSIONCONTROLTHROUGHPOWERAMPLIFIERLOADADJUSTEMENT (compression control adjusted by power amplifier load) ", No. 877, the denomination of invention submitted on December 30th, 2014 is the U.S. Provisional Application the 62/097th of " COMPRESSIONCONTROLTHROUGHAMPLITUDEADJUSTMENTOFARADIOFREQ UENCYINPUTSIGNAL (compression control adjusted by the amplitude of radio-frequency input signals) ", No. 899, the denomination of invention submitted on December 30th, 2014 is the U.S. Provisional Application the 62/097th of " COMPRESSIONCONTROLTHROUGHPOWERAMPLIFIERVOLTAGEADJUSTMENT (compression control adjusted by power amplifier voltage) ", the priority of No. 941, hereby by reference and the disclosure of each is all herein incorporated clearly by it.
Technical field
The application relates generally to the wireless communication system with cascode (cascode, or cascade) power amplifier.
Background technology
Many wireless devices comprise one or more linear power amplifier.Amplify received signal exactly for the ease of power amplifier, expect the compression avoiding signal.When power amplifier compression signal, power amplifier exports may be no longer relevant to its input linear, and the waveform modulated may become distortion.In addition, signal spectrum may change and start deterioration, to make in spread spectrum to the adjacent area of frequency band and to violate system specifications.Other wireless device may be disturbed in spread spectrum to adjacent channel, thus other wireless device be had a negative impact.
Summary of the invention
According to some execution modes, the application relates to a kind of power amplifier module, comprises power amplifier.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier module comprises power amplifier bias controller.Described power amplifier bias controller comprises current comparator, and described current comparator is configured to the first base current of more described the first transistor and the second base current of described transistor seconds, to obtain comparison value.Described power amplifier module comprises saturating control, and being configured to provides reference signal based on described comparison value to impedance matching network.Described impedance matching network is configured to change the load impedance with the load line of described power amplifier telecommunication based on described reference signal at least partly.
In certain embodiments, described the first transistor can be grounded-base transistor, and described transistor seconds can be common-emitter transistor.
In certain embodiments, described load line can carry out telecommunication with antenna, and described load line can electrically between described power amplifier and described antenna.
In certain embodiments, described impedance matching network can be dynamic impedance matching network.
In certain embodiments, the described saturating control load impedance that can also be configured to by changing described load line reduces the compression of described power amplifier.
In certain embodiments, described saturating control can also comprise digital to analog converter and ramp generator.In certain embodiments, described ramp generator can be configured to provide count value to described digital to analog converter, and described digital to analog converter can be configured to generate described reference signal based on described count value at least partly.
In certain embodiments, described saturating control can comprise the pull-down-resistor, voltage I/O pin and the oblique wave clock generator that carry out telecommunication with described power amplifier bias controller.Whether described oblique wave clock generator can be configured to detect described the first transistor based on the voltage across described pull-down-resistor and operate in zone of saturation.Described voltage can at least partly based on described comparison value.In response to detecting that described the first transistor operates in described zone of saturation, described oblique wave clock generator can be configured such that described count value changed by described ramp generator.
In certain embodiments, described digital to analog converter can also be configured to generate described reference signal based on average power pursuit gain at least partly, and described average power pursuit gain is determined based on the target power signal received from base station.
In certain embodiments, described saturating control can also comprise RF front end, is configured to receive default data value from saturated data pins.Described count value initially can correspond to described default data value.In certain embodiments, described default data value can be one of multiple default data value, and can select by based target voltage.In certain embodiments, described target voltage can be determined based on the target power signal received from base station at least partly.
In certain embodiments, described power amplifier module can also comprise: boost converter, is configured to regulate the supply power voltage provided to described power amplifier.In certain embodiments, described saturating control can also be configured to the compression being reduced described power amplifier by the combination of following operation: provide the second reference signal to increase described supply power voltage to described boost converter; And by providing described reference signal to change the load impedance of described load line to described impedance matching network.
According to some execution modes, the application relates to a kind of transceiver, comprises impedance matching network.Described impedance matching network is configured to change based on reference signal the load impedance carrying out the load line of telecommunication with power amplifier and antenna.Described transceiver also comprises power amplifier module, comprises power amplifier, power amplifier bias controller and saturating control.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier bias controller comprises current comparator, and described current comparator is configured to the base current of more described the first transistor and the base current of described transistor seconds, to obtain comparison value.Described saturating control is configured to generate described reference signal based on described comparison value at least partly and provide described reference signal to described impedance matching network.
In certain embodiments, described impedance matching network can be dynamic impedance matching network.
In certain embodiments, described saturating control can also comprise digital to analog converter and ramp generator.In certain embodiments, described ramp generator can be configured to provide count value to described digital to analog converter, and described digital to analog converter can be configured to generate described reference signal based on described count value at least partly.
In certain embodiments, described saturating control can comprise the pull-down-resistor, voltage I/O pin and the oblique wave clock generator that carry out telecommunication with described power amplifier bias controller.Whether described oblique wave clock generator can be configured to detect described the first transistor based on the voltage across described pull-down-resistor and operate in zone of saturation, described voltage is at least partly based on described comparison value, and in response to detecting that described the first transistor operates in described zone of saturation, described oblique wave clock generator is configured such that described count value changed by described ramp generator.
In certain embodiments, described transceiver also comprises: boost converter, is configured to regulate the supply power voltage provided to described power amplifier.In certain embodiments, described saturating control is also configured to the compression being reduced described power amplifier by the combination of following operation: provide the second reference signal to increase described supply power voltage to described boost converter; And by providing described reference signal to change the load impedance of described load line to described impedance matching network.
According to some execution modes, the application relates to a kind of wireless device, comprises antenna, and described antenna is configured at least launch the signal from transceiver, and described signal is at least partly based on the radio-frequency input signals that the power amplifier to described transceiver provides.Described transceiver comprises impedance matching network and power amplifier module.Described impedance matching network is configured to change based on reference signal the load impedance carrying out the load line of telecommunication with described power amplifier and described antenna.Described power amplifier module comprises power amplifier, power amplifier bias controller and saturating control.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier bias controller comprises current comparator, and described current comparator is configured to the base current of more described the first transistor and the base current of described transistor seconds, to obtain comparison value.Described saturating control is configured to generate described reference signal based on described comparison value at least partly and provide described reference signal to described impedance matching network.
According to some execution modes, the application relates to a kind of power amplifier module, comprises power amplifier.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier module comprises power amplifier bias controller.Described power amplifier bias controller comprises current comparator, saturating control and radio frequency (RF) attenuator.Described current comparator is configured to the first base current of more described the first transistor and the second base current of described transistor seconds, to obtain comparison value.Described saturating control is configured to provide reference signal based on described comparison value to described RF attenuator.Described RF attenuator is configured to the amplitude changing the RF input signal provided to described power amplifier at least partly based on described reference signal.
In certain embodiments, described RF attenuator can be digital pad, is configured to the amplitude changing described RF input signal at least partly based on pad value.In certain embodiments, described pad value can be the discrete attenuation value selected from multiple discrete attenuation value.The selection of described discrete attenuation value can at least partly based on described reference signal.
In certain embodiments, described RF attenuator can be analog attenuator, is configured to the amplitude changing described RF input signal at least partly based on pad value.In certain embodiments, described pad value can based on analog voltage, and described analog voltage is changed constantly, until described reference signal indicates described power amplifier not to operate in saturation condition.In certain embodiments, described analog attenuator can determine whether to change described analog voltage by increasing described analog voltage or reducing described analog voltage based on the polarity (polarity) of described analog attenuator at least partly.
In certain embodiments, described the first transistor can be grounded-base transistor, and described transistor seconds can be common-emitter transistor.
In certain embodiments, described power amplifier module also comprises: boost converter, is configured to regulate the supply power voltage provided to described power amplifier.
In certain embodiments, described saturating control can also comprise digital to analog converter and ramp generator.Described ramp generator can be configured to provide count value to described digital to analog converter.Described digital to analog converter can be configured to generate described reference signal based on described count value at least partly.
In certain embodiments, described reference signal can be 8 words, is used to specify the pad value for described RF attenuator.Described RF attenuator can change the amplitude of described RF input signal at least partly based on described pad value.
In certain embodiments, described saturating control can comprise the pull-down-resistor, voltage I/O pin and the oblique wave clock generator that carry out telecommunication with described power amplifier bias controller.Whether described oblique wave clock generator can be configured to detect described the first transistor based on the voltage across described pull-down-resistor and operate in zone of saturation.Described voltage can at least partly based on described comparison value.In response to detecting that described the first transistor operates in described zone of saturation, described oblique wave clock generator can be configured such that described count value changed by described ramp generator.
According to some execution modes, the application relates to a kind of transceiver, comprises Receiver And Transmitter.Described transmitter comprises power amplifier module.Described power amplifier module comprises power amplifier and power amplifier bias controller.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier bias controller comprises current comparator, saturating control and radio frequency (RF) attenuator.Described current comparator is configured to the base current of more described the first transistor and the base current of described transistor seconds, to obtain comparison value.Described saturating control is configured to provide reference signal based on described comparison value to described RF attenuator.Described RF attenuator is configured to the amplitude changing the RF input signal provided to described power amplifier at least partly based on described reference signal.
In certain embodiments, described RF attenuator can be digital pad, is configured to the amplitude changing described RF input signal at least partly based on pad value.In certain embodiments, described pad value can be the discrete attenuation value selected from multiple discrete attenuation value.The selection of described discrete attenuation value can at least partly based on described reference signal.
In certain embodiments, described RF attenuator can be analog attenuator, is configured to the amplitude changing described RF input signal at least partly based on pad value.In certain embodiments, described pad value can at least partly based on analog voltage, and described analog voltage is changed constantly, until described reference signal indicates described power amplifier not to operate in saturation condition.In certain embodiments, described analog attenuator can determine whether to change described analog voltage by increasing described analog voltage or reducing described analog voltage based on the polarity of described analog attenuator at least partly.
According to some execution modes, the application relates to a kind of wireless device, comprises antenna, and described antenna is configured at least launch the signal from transmitter, and described signal is at least partly based on the radio-frequency input signals that the power amplifier to described transmitter provides.Described transmitter comprises power amplifier module.Described power amplifier module comprises described power amplifier and power amplifier bias controller.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier bias controller comprises current comparator, saturating control and RF attenuator.Described current comparator is configured to the base current of more described the first transistor and the base current of described transistor seconds, to obtain comparison value.Described saturating control is configured to provide reference signal based on described comparison value to described RF attenuator.Described RF attenuator is configured to the amplitude changing described RF input signal at least partly based on described reference signal.
In certain embodiments, described RF attenuator can be digital pad, and be configured to the amplitude changing described RF input signal at least partly based on discrete attenuation value, described discrete attenuation value is selected from multiple discrete attenuation value.The selection of described discrete attenuation value can at least partly based on described reference signal.
In certain embodiments, described RF attenuator can be analog attenuator, is configured to the amplitude changing described RF input signal at least partly based on pad value.Described pad value can at least partly based on analog voltage, and described analog voltage is changed constantly, until described reference signal indicates described power amplifier not to operate in saturation condition.
According to some execution modes, the application relates to a kind of power amplifier module, comprises power amplifier.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier module comprises power amplifier bias controller.Described power amplifier bias controller comprises current comparator, and described current comparator is configured to the first base current of more described the first transistor and the second base current of described transistor seconds, to obtain comparison value.Described power amplifier module comprises saturating control, and being configured to provides reference signal based on described comparison value to electric pressure converter.Described electric pressure converter is configured to change based on described reference signal the supply power voltage provided to described power amplifier at least partly.
In certain embodiments, described the first transistor can be grounded-base transistor, and described transistor seconds can be common-emitter transistor.In certain embodiments, described the first transistor can be common gate transistor, and described transistor seconds can be common source transistor.
In certain embodiments, described electric pressure converter can indicate described the first transistor to operate in zone of saturation in response to described reference signal increases described supply power voltage.
In certain embodiments, described electric pressure converter can comprise switch-mode boost converter.
In certain embodiments, described saturating control can also be configured to provide described reference signal based on the second comparison value corresponding with the second power amplifier to described electric pressure converter.In certain embodiments, described electric pressure converter can also be configured to change based on described reference signal the supply power voltage provided to described second power amplifier at least partly.
In certain embodiments, described saturating control can also comprise digital to analog converter and ramp generator.Described ramp generator can be configured to provide count value to described digital to analog converter.Described digital to analog converter can be configured to generate described reference signal based on described count value at least partly.
In certain embodiments, described saturating control can comprise the pull-down-resistor, voltage I/O pin and the oblique wave clock generator that carry out telecommunication with described power amplifier bias controller.Whether described oblique wave clock generator can be configured to detect described the first transistor based on the voltage across described pull-down-resistor and operate in zone of saturation.Described voltage can at least partly based on described comparison value.Described oblique wave clock generator can be configured to, in response to detecting that described the first transistor operates in zone of saturation, make described ramp generator change described count value.
In certain embodiments, described digital to analog converter can also be configured to generate described reference signal based on average power pursuit gain at least partly.Described average power pursuit gain can be determined based on the target power signal received from base station.
In certain embodiments, described electric pressure converter can be configured to change described supply power voltage by cell voltage being boosted to the voltage level exceeding described cell voltage.In certain embodiments, described supply power voltage can at least partly based on cell voltage.
According to some execution modes, the application relates to a kind of transceiver, comprises receiver, is configured to change based on reference signal at least partly electric pressure converter and the transmitter of the supply power voltage provided to power amplifier.Described transmitter comprises power amplifier module, power amplifier bias controller and saturating control.Described power amplifier module comprises described power amplifier.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier bias controller comprises current comparator, and described current comparator is configured to the first base current of more described the first transistor and the second base current of described transistor seconds, to obtain comparison value.Described saturating control is configured to provide described reference signal based on described comparison value to described electric pressure converter.
In certain embodiments, described electric pressure converter can indicate described the first transistor to operate in zone of saturation in response to described reference signal increases described supply power voltage.
In certain embodiments, described saturating control can also be configured to provide described reference signal based on the second comparison value corresponding with the second power amplifier to described electric pressure converter.In certain embodiments, described electric pressure converter can also be configured to change based on described reference signal the supply power voltage provided to described second power amplifier at least partly.
In certain embodiments, described saturating control can also comprise digital to analog converter and ramp generator.Described ramp generator can be configured to provide count value to described digital to analog converter.Described digital to analog converter can be configured to generate described reference signal based on described count value at least partly.
In certain embodiments, described saturating control can comprise the pull-down-resistor, voltage I/O pin and the oblique wave clock generator that carry out telecommunication with described power amplifier bias controller.Whether described oblique wave clock generator can be configured to detect described the first transistor based on the voltage across described pull-down-resistor and operate in zone of saturation.Described voltage can based on described comparison value.Described oblique wave clock generator can be configured to, in response to detecting that described the first transistor operates in zone of saturation, make described ramp generator change described count value.
In certain embodiments, described digital to analog converter can also be configured to generate described reference signal based on average power pursuit gain at least partly.Described average power pursuit gain can be determined based on the target power signal received from base station.
In certain embodiments, described electric pressure converter comprises switch-mode boost converter.
According to some execution modes, the application relates to a kind of wireless device, and the one or more parts comprised to described wireless device provide battery and the transmitter of cell voltage.Described transmitter comprises power amplifier module, power amplifier bias controller and saturating control.Described power amplifier module comprises power amplifier.Described power amplifier comprises cascode transistor pair.Described cascode transistor is to comprising the first transistor and transistor seconds.Described power amplifier bias controller comprises current comparator, and described current comparator is configured to compare the first base current of grounded-base transistor and the second base current of common-emitter transistor, to obtain comparison value.Described saturating control is configured to provide reference signal based on described comparison value to electric pressure converter.Described electric pressure converter is configured to change based on reference signal the supply power voltage provided to described power amplifier at least partly.Described supply power voltage is at least partly based on described cell voltage.
In certain embodiments, described wireless device can also comprise nonvolatile memory, is configured to store the one or more average power pursuit gains corresponding with one or more target voltage values.Described supply power voltage can at least partly based on the average power pursuit gain selected from one or more average power pursuit gain.Average power pursuit gain can be selected based on the target voltage from one or more target voltage values.
For general introduction object of the present disclosure, some aspect of the present invention, advantage and novel feature are described herein.Should be appreciated that according to any specific embodiment of the present invention, not necessarily will realize all these advantages.Thus, can implement according to the mode of the advantage realized or optimize as here instructed or one group of advantage or realize the present invention, and not need to realize other advantage as instructed or advise here.
Accompanying drawing explanation
Run through accompanying drawing, reuse Reference numeral to indicate the corresponding relation between referenced element.Accompanying drawing is provided, so that the embodiment of subject matter described here to be described, and to be not used in and to limit its scope.
Figure 1A-1D illustrates the simulation curve figure of the example power amplifier using cascode configuration.
Fig. 2 illustrates the first example of a part for the transceiver comprising cascode power amplifier and saturating control.
Fig. 3 illustrates the example of the saturated saturating control that may be used for preventing cascode power amplifier.
Fig. 4 illustrates the example of the wireless device comprising power amplifier module.
Fig. 5 illustrates the second example of a part for the transceiver comprising cascode power amplifier and saturating control.
Fig. 6 illustrates the 3rd example of a part for the transceiver comprising cascode power amplifier and saturating control.
Fig. 7 illustrates the flow chart of the embodiment of saturation detection and compensation deals.
Fig. 8 illustrates the example of the sequential chart for saturation detection and compensation.
Fig. 9 illustrates the curve chart of the base current of grounded-base transistor and the base current of common-emitter transistor compared for the cascode power amplifier of 2:1 voltage standing wave ratio (VSWR).
Figure 10 illustrates the curve chart described for the adjacent channel leakage ratio (ACLR) of the function as load of the 2:1VSWR situation of Fig. 9.
Figure 11 illustrate describe when by Fig. 9 with 10 saturation detection associate with embodiment described here with ACLR time the curve chart of saturated situation do not detected.
Figure 12 illustrate describe when by Fig. 9 with 10 saturation detection associate with embodiment described here with ACLR time the curve chart of saturated situation detected.
Embodiment
If any, the title here provided just to conveniently, and should not affect scope or the implication of claimed invention.
introduction
Many wireless devices comprise one or more linear power amplifier.In some cases, power amplifier accepts comprises modulation waveform or the signal of amplitude modulation content.Amplify received signal exactly before transmission for the ease of power amplifier, expect the compression avoiding signal.When power amplifier enters compression, power amplifier exports may be no longer relevant to its output linearity.Once power amplifier starts compressed signal and device starts to enter saturation mode, so modulated waveform may become distortion, and it may cause information dropout.In addition, signal spectrum may change and start deterioration, to make in spread spectrum to the adjacent area of frequency band and to violate system specifications.Other wireless device may be disturbed in spread spectrum to adjacent channel, thus other wireless device be had a negative impact.Because the less version of the signal that the wireless device with the power amplifier (PA) being in compression is launched appears in the frequency spectrum distributed to another wireless device, so deterioration may occur.This internal modulation (inner-modulation) component may be difficult to filter, this is because it occurs with the less offset relative to tranmitting frequency.Compared with harmonic wave, this skew is usually obvious closer to carrier frequency.
Often, the power applied to PA and power compression point is the function of supply power voltage and load impedance.Thus, when the supply of fixing voltage and fixing load impedance, the saturation power size of PA and the compression property of PA may be determined.If power amplifier operates in the system that wherein load impedance such as changes due to the environment change (such as, the palmistry of user is for the position of antenna) of antenna or antenna, so the compression of PA and saturation point can change.Power compression may cause radio frequency (RF) signal by brachymemma (clip).Thus, the amplitude peak possible loss of signal.Expect to avoid compression although frequent, PA is generally full blast when operating in and not making frequency spectrum deteriorated near compression.Thus, PA often has narrow opereating specification.
In order to solve the problem of power compression, can expect that determining that PA operates in wherein makes in this situation of output spectrum deterioration.Because deterioration signal may be desired signal with lower aprons 30db, so this may be challenging.A solution uses RF detector or receiver.But interpolation RF detector or receiver can increase significant cost, and may need a large amount of electric currents, cause the shorter battery life of wireless device.In addition, add optional feature and cause extra complexity.
Here embodiment can carry out detection power compression by monitoring for Beta (beta) value (being called " Beta ") of one or more transistors of PA here.Beta refers to the ratio between the collector current of transistor and base current.Usually, collector current is more much bigger than base current.Thus, when transistor is not in saturated, Beta is through being everlasting between 100 and 120.But, should be appreciated that, for unsaturated transistor Beta value may to technique and relevant both applying.When Beta reduces, can determine that transistor is in saturated.Often, the reduction of Beta will be more sharply, such as, be relevant to illustrated in Fig. 1 C.When PA is compressed significantly, the Beta of transistor may be reduced to the half of Beta in non-compressed state.
Be that monitoring is used for collector current and the base current of one or more transistor for monitoring a solution of Beta, and by two electric currents divided by acquisition current ratio, this will obtain Beta.Monitoring collector current may cause the deterioration of the available horsepower from power supply or the reduction that make can be used for PA, can reduce available horsepower this is because add for the parts sensing collector electrode.Thus, monitoring current may cause the loss on collector electrode feed (feed), and this voltage that the collector electrode to PA transistor may be caused to present (present) reduces.
The embodiment here presented utilizes cascode transistor structure to reduce monitoring collector current on the impact of available horsepower.Fig. 2 more described in detail below, 5 and 6 presents some examples of the system comprising following PA, and this PA has the cascode configuration that may be used for each embodiment described here.
Figure 1A-1D illustrates the curve chart of emulation of the power amplifier using cascode configuration, which illustrates and can how to use Beta to carry out the saturated of detection power amplifier or its transistor.Fig. 1 C be for cascode transistor and for the Beta of the RF device transistor of PA that designs with cascode configuration to curve Figure 130 of power output.In the case, cascode transistor can refer to the transistor carrying out telecommunication with the antenna of wireless device, but this telecommunication needs not to be direct communication.In addition, in the case, RF device transistor can refer to the transistor received for the RF input signal launched.
Illustrated in the curve Figure 130 in Fig. 1 C, when power output starts compression or gain starts to compress, for each transistor, Beta started to rise gradually before precipitous decline.But, as from curve Figure 130 clearly, before Beta sharply reduces, between two transistors, in power output, have 2 to the difference of 3dB.Thus, when first cascode transistor compresses or enter saturated, there is significant difference in Beta.
Be used in embodiment disclosed herein, can detect saturated by the Beta of the RF device comparing Beta and the PA of cascode transistor.As previously mentioned, among other things, cause very big difference may being there is on Beta between different components due to manufacturing process.Thus, by the relative different between the Beta value of determining two transistors, instead of analyze the Beta value of each transistor independently, the embodiment here presented can have nothing to do with technique.In some cases, the Beta difference of 20% can indicate the saturated of RF device transistor.
Illustrated in the curve Figure 110 in Figure 1A, it is also roughly the point that the gain of PA declines to power output that PA enters saturated power output.In addition, illustrated in the curve Figure 140 in Fig. 1 D, when PA enters saturated, power output keeps constant when electric current increases.But, about Beta, between cascode transistor and the base current of RF device transistor, there is difference.Thus, the base current of each transistor of the PA with cascode configuration may be compared, instead of compare Beta value.Advantageously, in certain embodiments, by comparing base current instead of Beta value, can reduce for determining whether PA is in the complexity of saturated hardware, and cost and power saving can be realized.In addition, the ratio that curve Figure 120 of Figure 1B illustrates the right each base current of the transistor that forms cascode PA may be used for identifying that PA enters saturated point.
Here disclosed embodiment can pass through the ratio of the base current of the pair of transistor of the PA that analysis configure with cascode design, determine that power amplifier is in compression, or the transistor operation of power amplifier is in saturation condition.Whether being in saturated threshold value for right transistor of determining the cascode transistor of power amplifier and/or can apply relevant to technique.Such as, this threshold value can be the difference of 1.2 or 20%.In some embodiments, this threshold value can arrange based on user's setting or operating environment or adjust.
Numerous embodiments may be used for detection power amplifier and whether is in compression, and for making power amplifier leave compression.Be relevant to remaining accompanying drawing here to describe some embodiments.In addition, main phase describes embodiment here about transmitter.But should be appreciated that, some execution modes of system described here can be suitable for being used in receiver.
first example transceiver
Fig. 2 illustrates the first example of a part for the transceiver 200 comprising power amplifier module 202, and this power amplifier module 202 comprises cascode power amplifier 208 and saturating control 240.In some embodiments, transceiver 200 can be transmitter.Usually, transmitter can be relevant to be used in the embodiments described herein.Often need not be relevant to receiver to realize embodiment described here, this is because transceiver is usually designed to the Received signal strength supporting greatest hope, and the compression level that receiver is supported is generally more much bigger than transmitter.But the dynamic range of receiver also may cause larger current consumption.Thus, in certain embodiments, embodiment described here may be used for receiver to reduce dynamic range and to increase power saving.Correspondingly, although be relevant to transmitter to generally describe embodiment described here, in certain embodiments, this transceiver 200 can be receiver.Cascode power amplifier 208 has the power amplifier with the transistor 210 and 212 of cascode configuration electrical connection.Cascode configuration is by a transistor 212 stacked (stack) on another transistor 210, and make when bipolar junction transistor (BJT), the emitter of transistor 212 and the collector electrode of transistor 210 carry out telecommunication.Should be appreciated that, cascode power amplifier 208 can be a part for power amplifier 204.Such as, cascode power amplifier 208 can be the part of the PA204 comprising the pair of transistor be in cascode configuration.
Transistor 210 can refer to RF device transistor or RF transistor, and is configured to receive RF input signal.Transistor 212 can refer to cascode transistor, and be configured to provide reference current, this reference current can be exaggerated biased (bias) controller 230 of device and/or saturating control 240 for determining whether transistor 210 operates in saturation mode.In some embodiments, transistor 210 and 212 is BJT.In this case, transistor 210 can be common-emitter transistor, and transistor 212 can be grounded-base transistor.In other words, transistor 210 can make its emitter and carry out telecommunication publicly, and transistor 212 can make its base stage (such as, via capacitor 214) and carry out telecommunication publicly.Alternatively, transistor 210 and 212 can be field-effect transistor (FET).In this case, transistor 210 can be common source transistor, and transistor 212 can be common gate transistor.
As illustrated in Figure 2, cascode power amplifier 208 can be a part for the power amplifier 204 that can comprise multiple additional device.Such as, power amplifier 204 can comprise: be biased (bias) circuit 206, carry out the capacitor 216 of telecommunication with the base stage of common-emitter transistor 210, carry out the capacitor 214 of telecommunication with the base stage of grounded-base transistor 212 and carry out the inductor 250 of telecommunication with the collector electrode of grounded-base transistor 212.
Capacitor 216 can be configured to prevent DC biased (bias) from leaking in the load in RF input.In addition, capacitor 214 can serve as by-pass capacitor, is configured such that RF energy keeps off the node between (keepoff) biasing circuit 206 and the base stage of grounded-base transistor 212.Inductor 250 can be configured to provide supply power voltage to cascode power amplifier 208.Supply power voltage can be provided to the collector electrode of grounded-base transistor 212.
Biasing circuit 206 can comprise the circuit for providing bias current to cascode power amplifier 208.In certain embodiments, as illustrated in Figure 2, biasing circuit 206 is comprised the part as power amplifier 204.But in some other embodiments, biasing circuit 206 can be separated with power amplifier 204.Biasing circuit 206 can comprise transistor 220, and it can be configured to provide voltage to the base stage of common-emitter transistor 210.Transistor 220 can play buffer effect, and can provide base current to common-emitter transistor 210.This base current can at least partly based on the voltage generated by RF bias block 224 that can apply to common-emitter transistor 210 via transistor 220.The voltage that can be generated by RF bias block 224 can based on current offset (currentbias) block 232.This current offset block 232 that can be included as a part for power amplifier bias controller 230 can be the current source utilizing pair of diodes to be formed.In some cases, following voltage can be utilized to configure one of described diode, described voltage equals the base emitter voltage (Vbe) of common-emitter transistor 210 or is in the threshold value difference of this Vbe.Another diode can have the voltage in the Vbe equaling bias transistor 220 or the threshold value difference being in this Vbe.
In addition, biasing circuit 206 can comprise transistor 218 and cascode bias block 222, and it is similarly configured with transistor 220 and RF bias block 224 and works respectively.In other words, transistor 218 can be configured to provide voltage to the base stage of grounded-base transistor 212.In addition, transistor 218 can play buffer effect, and can provide base current to grounded-base transistor 212.This base current can at least partly based on the voltage generated by cascode bias block 222 that can apply to grounded-base transistor 212 via transistor 218.The voltage that can be generated by cascode bias block 222 can based on current offset block 234.Similar with current offset block 232, this current offset block 234 that can be included as a part for power amplifier bias controller 230 can be the current source utilizing pair of diodes to be formed.In some cases, following voltage can be utilized to configure one of described diode, and described voltage equals the Vbe of grounded-base transistor 212 or is in the threshold value difference of this Vbe.Another diode can have the voltage in the Vbe equaling bias transistor 218 or the threshold value difference being in this Vbe.
Except comprising biasing circuit 206 that can be included in power amplifier 204 under power amplifier 204 and certain situation can be maybe separate payment, power amplifier module 202 can comprise PA offset controller 230.As mentioned above, PA offset controller 230 can comprise a pair current offset block 232 and 234, is respectively used to provide bias current to RF bias block 224 and cascode bias block 222.In addition, PA offset controller 230 can comprise current comparator 236, and it can the collector current of comparator transistor 218 and 220.
Utilize the cascode configuration of cascode power amplifier 208, in some embodiments, electric current can flow to the emitter of grounded-base transistor 212 through grounded-base transistor 212 or cascode device from collector electrode.In addition, electric current can flow to the emitter of lower device or common-emitter transistor 210 from collector electrode, this common-emitter transistor 210 can be called as RF transistor.Thus, in some embodiments, for both transistors 210 and 212, the electric current flowing to emitter from collector electrode can be completely the same or substantially identical (such as, within threshold current difference).
Advantageously, in certain embodiments, because collector-emitter current (Ice) is identical for both transistors 210 and 212, so the saturated or compression of grounded-base transistor 212 or cascode transistor can be determined, and without the need to calculating Beta, can saturated or compressed detected be carried out thus, and not add the additional complexity of Beta detection and measuring element.
As discussed previously, Beta equals collector current divided by base current.In addition, transistor 210 and 212 is configured to have identical Beta, or at least each Beta had in threshold value difference each other.Thus, the Beta due to cascode power amplifier transistor 210 and 212 is equal and collector current is equal, so the base current of transistor 210 and 212 also should be equal.Therefore, in some embodiments, can by the base current of comparator transistor 210 and 212 to determine whether the difference between transistor 210 and the base current of 212 exceedes or meet threshold value difference, detects grounded-base transistor 212 and when or whether to enter saturated.
In order to the base current of comparator transistor 210 and 212, the base current of transistor 212 and the base current of transistor 210 can be provided to current comparator 236.The base current of transistor 210 and 212 can be the electric current that biasing circuit 206 provides.Thus, as transistor 218 collector-emitter current (Ice) and drive the electric current I Csd of the base stage of grounded-base transistor 212 to be effective base currents of transistor 212.In addition, drive the base stage of common-emitter transistor 210 and be that the electric current I RF of the Ice of transistor 220 can be used as effective base current of transistor 210.Electric current I Csd is compared and IRF, PA offset controller 230 can determine that whether transistor 212 is saturated by using current comparator 236.
When PA204 is not in compression, electric current I Csd and IRF by equal, or have and is no more than threshold value difference.When PA is driven into compression, ICsd will increase relative to IRF usually.In this case, current comparator 236 can detect the relative changes on electric current, and provides signal to saturating control 240, and this signal designation PA204 or more specifically cascode PA208 are in compression.Usually, when cascode PA208 enters compression, signal spectrum deterioration, this causes the deterioration of systematic function.Advantageously, in certain embodiments, by using ICsd and IRF electric current to detect compression, compressed detected can be simplified, this is because element or device for measuring and compare Beta can be omitted from transceiver 200 and/or PAM202.
In order to determine whether transistor 212 operates in saturation condition, expect to compare electric current I Csd and the electric current corresponding with being not in saturated transistor.Thus, in certain embodiments, expect transistor 210 to maintain in unsaturated state, to be used as the benchmark determining that whether transistor 212 is saturated.Usually, the voltage that the voltage applied to transistor 210 can apply to the base stage to grounded-base transistor 212 is relevant.In some embodiments, the voltage of the voltage ratio emitter applied to the base stage of grounded-base transistor 212 is high 1.2 volts.Should be appreciated that, this voltage difference of 1.2 volts is relevant to technique, and may change in other embodiments.But suppose the technique causing 1.2 volts of differences between the base stage of grounded-base transistor 212 and transmitter, the voltage that so can apply than the base stage to grounded-base transistor 212 across the voltage of common-emitter transistor 210 is low 1.2 volts.Thus, suppose that biasing circuit 206 applies sufficient biased (bias) at the base stage place of transistor 212, function that the node at base stage place is not inputted as the RF received or change due to noise, so can suppose that the voltage across common-emitter transistor 210 can not be saturated, or at least can not detect grounded-base transistor 212 saturated before saturated.Therefore, by selecting the voltage applied at the base stage place of transistor 212 also by selecting capacitor 214, transistor 210 can be prevented saturated.In certain embodiments, transistor 210 can be saturated at the watt level place higher than transistor 212, make it possible to thus by transistor 212 saturated before transistor 212 be used as benchmark detect compression.
Once determining power amplifier 204 based on the comparison signal received from current comparator 236 has entered compression (such as at least partly, a transistor of cascode PA208 is in saturated), so saturating control 240 just can make the supply power voltage that change (modify) applies to power amplifier 204.Such as, saturating control 240 can make power amplifier 204 leave compressive state by increasing the supply power voltage applied to power amplifier 204.
In certain embodiments, saturating control 240 can by providing reference signal to increase supply power voltage to the boost converter of such as switch-mode boost converter 242 and so on.Based on this reference signal, switch-mode boost converter 242 can adjust the supply power voltage applied to power amplifier 204.The DC voltage provided arranges the headroom (headroom) on power amplifier 204.Thus, when power amplifier 204 is in compression, switch-mode boost converter 242 triggers to the increase on the DC supply power voltage of PA204 applying, and this can make PA204 leave compressive state and can correct its frequency spectrum.In certain embodiments, boost converter 242 can be step-down controller.But boost converter 242 is not limited thereto, and other voltage or electric current change transducer (modificationconverter) may be used for embodiment here.
Although saturating control 240 to be illustrated as the independent component of PAM202, other embodiment is also possible.Such as, saturating control 240 can be a part for PA offset controller 230, switch-mode boost converter 242, or is separated with PAM202.In addition, in some cases, saturating control 240 can be separated with transceiver 200.Similarly, although switch-mode boost converter 242 is illustrated as the independent component in transceiver 200, other embodiment is also possible.Such as, switch-mode boost converter 242 can integrate with PA offset controller 230.
Be relevant to Fig. 3 and describe saturating control 240 in further detail.In addition, more describe in detail as being relevant to Fig. 5 and 6, in certain embodiments, saturating control can use the compression control process of replacing or add to leave compressive state to make power amplifier 204.
Transceiver 200 can launch signal based on RF input signal via antenna 246.In addition, in certain embodiments, the one or more impedance matchings comprised at block 244, filter and/or switch element can carry out telecommunication between antenna 246 and power amplifier 204.As described in more detail below, in certain embodiments, the load that saturating control 240 can be applied to power amplifier 204 with change by the impedance matching network controlling to comprise at block 244, makes power amplifier 204 leave the state of compression.
In certain embodiments, each device of transceiver 200 and/or circuit can use common technique to realize or realize on same device.But, in other embodiments, different process can be used to realize each several part of transceiver 200.Such as, amplifier biasing controller 230 can be realized on silicon wafer (silicondie), power amplifier 204 can use the different materials of such as GaAs (GaAs) and so on to realize simultaneously.
example saturating control
Fig. 3 illustrates the example of the saturated saturating control 240 that may be used for preventing cascode power amplifier 208.As being previously relevant to described by Fig. 2, saturating control 240 can receive the signal of the comparison based on electric current from cascode power amplifier 208.This signal can receive from current comparator 236.The signal of this reception can receive at saturated feedback (SATFB) pin place.In addition, saturating control 240 can output reference signal, and this reference signal can by switch-mode boost converter 242 for adjusting the voltage provided to cascode power amplifier 208.
Saturating control 240 can comprise radio-frequency front-end (RFFE) kernel 304,8 shadow registers (shadowregister) 306,8 oblique waves (ramp) generator 308,8 figure place weighted-voltage D/A converter (DAC) 310, oblique wave clock generator 312 and oscillator clocks 314.In addition, saturating control 208 can comprise pull-down-resistor 316, determines whether one or more transistor 302 is in compression for promoting.
RFFE kernel 304 can comprise meet from alliance the RFFE kernel of specification.RFFE kernel 304 receives the target voltage values for PA204 via serial data (SData) pin, and this serial data (SData) pin can carry out clock control (clockedin) via serial clock (SClk).Alternatively, RFFE kernel 304 receives the default value representing target voltage values.The default value of target voltage or correspondence can be identified by accessing the average power table stored in memory.In addition, based target watt level select target voltage can be carried out.This target power size can be specified by with the base station that the wireless device comprising transceiver 200 carries out communicating.
Once RFFE kernel 304 receives target voltage via SData pin, then serial data can be converted to the parallel data as 8 words by RFFE kernel 304, and it can be stored in 8 shadow registers.Although be described as 8 words, other data size is also possible.In addition, 8 devices can be other size.Such as, shadow register can be 16 shadow registers, is configured to storage 16 words or two 8 words.
The word stored in 8 shadow registers 306 can be used as the initial of 8 digit counters or default conditions.This 8 digit counter can be safeguarded by 8 ramp generators 308.8 digit counters can be driven by the clock signal received from oblique wave clock generator 312, the signal (such as, SATFB signal) that its clock signal provides based on oscillator clock 314 and current comparator 236 by this oblique wave clock generator 312.Advantageously, 8 shadow registers 306 make saturating control to store data, such as corresponding with target voltage values Counter Value, meanwhile, can receive new data via serial line interface SDATA at RFFE kernel 304 place.Thus, in some cases, saturating control 240 can control transition timing (transitiontiming) between previous object magnitude of voltage and fresh target magnitude of voltage, the time period not having initial count value during preventing transition period.
In certain embodiments, saturating control 240 can sharing between multiple PA, transmitter or transceiver such as and illustrated in multiple transmitter modules 302 of SATFB line telecommunication.Each transmitter module 302 can be similarly configured with the transceiver 200 be relevant to described by Fig. 2.Saturating control 240 can comprise VIO pin, and it can be 1 pin interface receiving digital logic high signal.If the power amplifier of any transmitter module 302 enters saturated, then the signal received across SATFB can drag down, and result in the voltage across resistor 316, makes electric current flow through this resistor, and it is saturated to indicate PA to be in oblique wave clock generator 312.
When oblique wave clock generator 312 receive instruction PA be in saturated signal time, it can make ramp generator 308 increase progressively one by providing to ramp generator 308 clock signal at every turn.In some such situations, ramp generator 308 is used as counter, and its initial value provided based on clock signal and the shadow register 306 from oblique wave clock generator 312 counts.In some cases, the count value increased progressively is used as the word or the data that drive DAC310.Digital count value can be converted to analog signal by DAC310, and this analog signal can be supplied to boost converter 242, to drive or to change the voltage supply provided to saturated PA.Thus, in some cases, DAC310 can export the reference signal provided to boost converter (such as, boost converter 242), and reference signal can be translated to the voltage that can apply to the collector electrode of transistor 212 by this boost converter.The voltage of this applying can be called booster voltage (boostvoltage), and may be used for increasing the voltage range on power amplifier 204, reduce or eliminate compression thus.
Alternatively, or additionally, the reference signal that DAC310 exports may be used for changing the amplitude of RF input signal and/or load that apply to PA, as by be relevant to Fig. 5 and 6 further describe.In some cases, when SATFB drags down, ramp generator 308 starts to increase progressively one at every turn, and this can cause increasing progressively to the supply power voltage of power amplifier.Below, Fig. 8 is relevant to describe the example sequential chart for adjusting supply power voltage.
As mentioned above, when PA204 enters compressive state or have saturated transistor, the initial count value corresponding with boost level (boostlevel) can be increased progressively.Once make PA204 leave compression, so pressure-increasning state can be maintained.But in some cases, boost level is no longer required, such as, this is because wireless device is so mobile that more to change close to base station or voltage standing wave ratio (VSWR) situation.In some such situations, the threshold quantity of the voltage headroom that there is the voltage level exceeding the signal that will launch can be determined.In other words, in some cases, the voltage level of signal can more than threshold level, and this threshold level is lower than the enable maximum voltage available level that boosts.In this case, saturating control 240 by providing reset signal to reset the counter for boost value to ramp generator 308, can reduce booster voltage thus.And, in some such situations, the new acquiescence corresponding with fresh target voltage or initial value can be received at RFFE kernel 304 place.
example wireless device
Fig. 4 illustrates the example of the wireless device 400 that can comprise the power amplifier module 202 with power amplifier 204, and this power amplifier 204 comprises the transistor (such as, cascode power amplifier 208) of a pair cascode configuration.Although wireless device 400 illustrates an only power amplifier module (PAM), wireless device 400 may be made to comprise multiple PAM, its each can have or the configuration identical with PAM202 can not be had.Should be appreciated that, wireless device 400 is a non-limiting example of wireless device, and other embodiment of wireless device 400 is also possible.
Power amplifier module 202 can comprise multiple element.These elements such as can comprise power amplifier 204 and PA offset controller 230.Each in these power amplifier module elements can be implemented on identical circuit chip (die).Alternatively, at least some of each element of power amplifier module 202 can be implemented on different elements circuit chip.Advantageously, by realizing each element on different circuit chip, different semiconductor technologies may be used for the different circuit elements of power amplifier module 202.Such as, PA204 can use GaAs (GaAs) technology to realize; And PA offset controller 230 can use silicon (Si) to realize.
As illustrated, PA204 can comprise biasing circuit 206, and PA offset controller 230 can comprise saturating control 240.Alternatively, one or more in biasing circuit 206 and saturating control 240 can be the individual components comprised at PAM202.In addition, comprise single PA204 although be depicted as by PAM202, in certain embodiments, PAM202 also can comprise multiple PA204.In addition, PAM202 can comprise the switching circuit described by block 244 being such as relevant to Fig. 2, and it may be used for selecting signal among multiple PA.Such as, PAM202 can promote the Multiband-operation of wireless device 400.In some cases, the pattern of PAM202 can be arranged based on the signal set by controller and/or model selection by power amplifier controller (not shown).
In certain embodiments, PA offset controller 230 can arrange operating point for PA204 by change biasing circuit 206.Such as, PA offset controller 230 can arrange or change the bias current provided to PA204 by biasing circuit 206.
Power amplifier 204 can comprise the power amplifier of any type.But usually, PA204 comprises the PA had as being relevant to the cascode transistor configuration illustrated in Fig. 2.In addition, PA204 can be set to operate with particular point of operation.This operating point can be configured by biasing circuit 206, and this biasing circuit 206 can provide bias current and/or voltage to power amplifier 204.
In some cases, PAM202 can receive RF signal from transceiver 410, and this transceiver 410 can be configured according to known way and operate, and to generate the RF signal that will amplify and launch, and processes the signal received.In some embodiments, comprise the part of PAM202 as transmitter 430, this transmitter 430 can be included in transceiver 410.In some such situations, PAM202 can process the signal that will launch, and without the need to processing the signal received.In other embodiments, PAM202 can process received signal and such as will be transmitted into the signal of base station.
Transceiver can also comprise receiver 432 and switch-mode boost converter 242.Receiver 432 can comprise independent PAM, or shares PAM202 with transmitter 430.Switch-mode boost converter 242 can provide booster voltage (boostvoltage) to PAM202.In some cases, the part of switch-mode boost converter as transmitter 430 and/or PAM202 is comprised.
Transceiver 410 can carry out alternately with baseband subsystems 408, and this baseband subsystems 408 is configured to provide the conversion being suitable for carrying out the data that process and/or voice signal by one or more user interface element and being suitable for being undertaken between the RF signal that processes by transceiver 410.Transceiver 410 can also be electrically connected to power management components 406, and this power management components 406 is configured to manage the power for the operation of wireless device.This power management can also control the operation of baseband subsystems 408 and PAM202.In addition, power management components 406 can provide supply power voltage to switch-mode boost converter 242, this switch-mode boost converter 242 can before providing voltage to PA204 boosted voltage.Be also to be understood that power management components 406 can comprise the power supply of such as battery and so on.Alternatively, or additionally, one or more battery can be the separate part in wireless device 400.
Multiple connections between all parts of wireless device 400 are also possible, and described multiple connection is omitted from Fig. 4, for the purpose of being only used to clearly demonstrate instead of restriction the application.Such as, power management components 406 can be electrically connected to baseband subsystems 408, PAM202, DSP412 or other parts 414.As the second example, baseband subsystems 408 can be connected to user interface processor 416, and it can promote the input and output of speech and/or the data providing to user and receive from user.
Baseband subsystems 408 can also be connected to memory 418, and this memory 418 can be configured to store data and/or instruction, to promote the operation of wireless device 400, and/or provides the storage of information to user.In addition, in certain embodiments, memory 418 can comprise average power tracking (APT) table or other data structure.APT table can identify with can by the target voltage level for PA204 corresponding to the target power size of identification of base stations.Such as, once receive target power size from base station, so wireless device can access APT table, to determine corresponding target voltage level.This target voltage level may be used for arranging the operating point for PA204.
In certain embodiments, call processing device 434 can communicate with base station.This call processing device 434 can explain the order from base station, and can visit APT table based on the order received from base station.In addition, call processing device 434 can instruction PAM202 by providing target voltage to adjust the operating point of PA204 to the RFFE kernel of saturating control 240, this RFFE kernel then such as by making boost converter 242 be elevated to supply voltage as the target voltage level that in APT show identify corresponding with the target power size specified by base station, can adjust the voltage of PA204.Below, the timing example being relevant to Fig. 8 describes the example of adjustment for the voltage level of PA204 in further detail.
Except above-mentioned parts, wireless device can also comprise one or more central processing unit 420.Each central processing unit 420 can comprise one or more processor cores.In addition, wireless device 400 can comprise one or more antenna 422A, 422B.In some cases, one or more antennas of wireless device 400 can be configured to different frequency or carry out launching and/or receiving within the scope of different frequency.In addition, one or more antenna can be configured to work in different aerial networks.Thus, such as, antenna 422A can be configured to transmit and receive signal on 2G network, and antenna 422B can be configured to transmit and receive signal on 3G network.In some cases, but antenna 422A and 422B can be configured to such as on 2.5G network with different frequencies to transmit and receive signal.
Multiple other wireless device configuration can utilize described one or more features here.Such as, wireless device need not multi-band device.In another example, wireless device can comprise the additional antenna of such as diversity antenna and so on and the additional connection features of such as Wi-Fi, bluetooth and GPS and so on.In addition, wireless device 400 can comprise the optional feature of any number, such as analog to digital converter, digital to analog converter, Graphics Processing Unit, solid-state drive etc.And, wireless device 400 can comprise can communicate on one or more wireless network and the device of any type of PA204 and/or PAM202 can be comprised.Such as, wireless device 400 can be the cell phone, panel computer, laptop computer, video game apparatus, smart machine etc. that comprise smart phone or non intelligent phone.
second example transceiver
Fig. 5 illustrates the second example of a part for the transceiver 500 comprising power amplifier module 202, and this power amplifier module 202 comprises cascode power amplifier 208 and saturating control 240.In certain embodiments, transceiver 500 can be transmitter.As illustrated in reusing of Reference numeral, transceiver 500 can comprise multiple elements of transceiver 200.In addition, each element sharing the transceiver 500 of Reference numeral with each element of transceiver 200 can comprise the some or all of embodiments be relevant to described by transceiver 200.Thus, in order to simplify discussion, the description of each element of the transceiver 500 similar to each element of transceiver 200 will no longer repeat.
The transceiver 500 of Fig. 5 according to the mode similar to transceiver 200, by using current comparator 236 to compare ICsd and IRF electric current, can identify whether PA204 is in compression.But, be not change supply power voltage to increase the voltage headroom of PA204 thus to make PA204 leave compression, but saturating control 240 can using the output of current comparator 236, reducing by using RF attenuator 520 the RF input signal provided to PA204.By reducing, to the RF input signal of PA204 supply, to efficiently reduce the output signal from PA204.If output signal is sufficiently reduced, then PA204 can be made to leave squeeze operation state.Reduce RF input signal and can comprise the amplitude reducing RF input signal.
In some cases, undesirably reduce RF input waveform, this is because the signal provided to transceiver 500 is reduced, this may cause the performance of deterioration.Transceiver 200 is used for the improving SNR that wireless device 400 can cause for wireless device 400; But, and other wireless device carried out communicating in the base station identical with wireless device 400 may have deteriorated performance, this is because the signal that wireless device 400 power output is stronger, this may cause the larger distortion of other wireless device.Use transceiver 500 can improve the performance of other wireless device by reducing distortion, but may cause the more low performance of wireless device 400, this is due to the reduction on RF input signal.Thus, in some cases, transceiver 200 may be preferred when wireless device 400 is away from base station, and transceiver 500 may be preferred when wireless device 400 is close to base station.Advantageously, in certain embodiments, can the system of constitutional diagram 2 and Fig. 5.In other words, wireless device 400 can increase supply power voltage based on operating condition and/or reduce RF input signal.And in some cases, base station can provide order to wireless device 400, supply and/or RF input signal to control whether change the voltage provided to PA204.
As illustrated in fig. 5, the part of RF attenuator as PA offset controller 300 for transceiver 500 can be comprised.Alternatively, RF attenuator 502 can be individual component or the part being included as PA204.This RF attenuator 502 can be configured to receive RF input signal, and decays to it before providing this signal to power amplifier 204.Usually, this RF input signal is fixed signal.In addition, general expectation PA204 does not change this signal, to prevent loss of data.Thus, use RF attenuator 502 to make it possible to provide fixing input waveform to PA204, but be provide with lower amplitude, reduce the generation of compression thus.
RF attenuator 502 can be digital pad or analog attenuator.That in some embodiments of digital pad, RF attenuator 502 can comprise multiple discrete voltage levels at RF attenuator 502.When to detect in PA204 saturated for current comparator 236, saturating control 240 can the value of increasing attenuation device, and reduces RF input signal thus.In some cases, the value of increasing attenuation device iteratively can be carried out based on discrete voltage levels, until PA204 no longer operates in compressive state.
That in some embodiments of analog attenuator, analog voltage arranges pad value at RF attenuator 502.When detecting saturated, adjusting this voltage, depending on that the polarity of attenuator is to make this voltage ramp or oblique deascension, decay is increased, until give the power drop of PA204 to be removed from compressive state by PA204.In other words, use RF attenuator 502, saturating control 240 can increase decay with fixing speed, until eliminate compression in PA204.Once current comparator 236 indicates PA204 to be no longer in compression, so pad value can be kept constant.
RF attenuator 502 can comprise the circuit of any type, and this circuit can be decayed RF input signal, and at least part of reference signal based on receiving from saturating control 240 maintains constant impedance simultaneously.In certain embodiments, RF attenuator 502 can comprise Pi network and/or T-network.
3rd example transceiver
Fig. 6 illustrates the 3rd example of a part for the transceiver 600 comprising power amplifier module 202, and this power amplifier module 202 comprises cascode power amplifier 208 and saturating control 240.In certain embodiments, transceiver 600 can be transmitter.As illustrated in reusing of Reference numeral, similar with transceiver 500, transceiver 600 also can comprise multiple elements of transceiver 200.In addition, each element sharing the transceiver 600 of Reference numeral with each element of transceiver 200 can comprise the some or all of embodiments be relevant to described by transceiver 200.Thus, in order to simplify discussion, the description of each element of the transceiver 600 similar to each element of transceiver 200 will no longer repeat.
The transceiver 600 of Fig. 6 according to the mode similar with 500 to transceiver 200, by using current comparator 236 to compare ICsd and IRF electric current, can identify whether PA204 is in compression.But, be not adjustment supply power voltage or decay RF input signal, but transceiver 600 can change the load of the output of PA204.In certain embodiments, block 244 can comprise the impedance matching network that can be controlled by saturating control 240.In such an embodiment, attenuation controller 240 can provide reference signal to the impedance matching network of block 244, to change the impedance of the output of PA204.Such as, saturating control 240 can make to disconnect based on the one or more switches in the impedance matching network of switched capacitor or close, to change the load of the output of PA204.In certain embodiments, by changing the impedance load in the output of PA204, PA204 can be made to leave compression.
As mentioned above, impedance matching network can be connected electrically between PA204 and antenna 246 and/or one or more additional device.Block 244 can utilize various impedance matching networks.The example of each embodiment of the adjustable automatic impedance matching network that can here use is described in the U.S. Provisional Application the 62/057th that the denomination of invention submitted on September 30th, 2014 is " AUTOMATICIMPEDANCEMATCHINGUSINGTRUEPOWERINFORMATION (using the automatic impedance matching of real power information) ", in No. 451, hereby by reference its whole disclosure is herein incorporated.In addition, other adjustable load circuits can be utilized here to change the load of PA204.
In certain embodiments, the load of PA204 and the voltage supply of PA204 can be changed in combination, to be removed from compressive state by PA204.In such an embodiment, saturating control 240 can provide reference signal to the impedance matching network of switch-mode boost converter 242 and block 244.In addition, in certain embodiments, what saturating control 240 can be configured to adjust in voltage supply, the load of PA204 and the decay of RF signal is one or more.Thus, in some embodiments, saturating control 240 and/or the base station compression that the combination of each technology can be used to carry out to prevent PA204.In certain embodiments, compression avoids the selection of technology can change based on the operating environment of wireless device.Such as, very strong and there is the power of more than threshold value at RF input signal, saturating control 240 can be decayed RF input signal, but when the power of RF input signal is lower than threshold value, saturating control can adjust the load of voltage supply and/or the PA204 provided to PA204.As another example, when the number of wireless device in specific geographical area is determined lower than a threshold value in base station, base station can make wireless device change voltage supply, to prevent compression.
example saturation detection and compensation deals
Fig. 7 presents the flow chart of the embodiment of saturation detection and compensation deals 700.Process 700 can be realized by one or more element, described element can detect the power amplifier being in and making to compress in the saturation condition of RF input signal, and one or more operating conditions of system can be changed, be in saturation condition to prevent power amplifier.Such as, process 700 to be realized whole or in part by power amplifier bias controller 230, saturating control 240, switch-mode boost converter 242, RF attenuator 502 and/or impedance matching network.Although the system of any number can realize process 700 whole or in part, in order to simplify discussion, each several part of process 700 is described with reference to particular system.
Process 700 starts with block 702, and such as, in this block 702, the base current (such as, ICsd) of the grounded-base transistor 212 in the cascode power amplifier 208 of power amplifier 204 monitored by current comparator 236.In block 704, the base current (such as, IRF) of the common-emitter transistor 210 in cascode power amplifier 208 monitored by current comparator 236.In block 706, current comparator 236 compares the base current of grounded-base transistor 212 and the base current of common-emitter transistor 210, to obtain cascode PA current ratio.As described earlier, the comparison of the base current of each transistor of cascode PA208 may be used for determining whether the transistor of cascode PA208 is in saturated, indicates PA204 whether to be in compression thus.In addition, as described earlier, in certain embodiments, by comparing base current instead of the Beta of cascode PA208, can PA204 being simplified, saving power and cost for measuring and comparing Beta to determine PA204 whether to be in the element of compression by eliminating.
In Decision Block 708, saturating control 240 determines whether cascode PA current ratio exceedes or meet threshold value.If not, then process 700 and turn back to block 702.If cascode PA current ratio exceedes or meets this ratio, then saturating control 240 in block 710, change or make the DC supply power voltage of at least one in the following change: PA204, the load of the output of the RF input signal that provides to PA204 and/or PA204.As described earlier, a device can be configured to change the load of in the following or output more than one: DC supply power voltage, RF input signal and/or PA.Can change in the embodiment of multiple operating characteristics of PA204 at this device, saturating control 240 can select based on the operating environment of wireless device and/or based on the order from base station the load whether changing supply power voltage, RF input signal and/or PA204.
example sequential chart
Fig. 8 illustrates the example of the sequential chart for saturation detection and compensation.In bottom, to illustrate to the data input stream of RFE kernel 304 from the left side of sequential chart.Each pulse can represent serial data stream.Multiple operation can be there is at each impulse duration, and simplify sequential chart, be shown in the information to PA transmission in RFFE bus with General maps.As indicated in Figure 8, the enable boosting from boost converter 242 of the first order is powered.As a result, sequential chart illustrate boost output voltage start after the first pulse rise.In addition, the boost level can determined from APT table is utilized to programme to boosting RFFE register 1.At PA enabling pulse place, PA204 is activated, and receives the supply power voltage exported based on DAC310.In addition, PA204 starts to receive RF input signal.In addition, sequential chart illustrates PA204 and is not in saturated.
At point 802 place, the event that such as antenna impedance is modified and so on occurs, and causes being adjusted to the load of PA204.As a result, PA204 starts compression when the transistor of PA204 starts saturated.In sequential chart by SATFB signal dragged down illustrate saturated.
In certain embodiments, SATFB is dragged down the increase triggered in boosting RFEE output.Increase progressively ramp generator 308, the reference signal that result in from DAC310 is modified.The supply power voltage that the reference signal of change can make boost converter 242 increase the collector electrode to PA204 to provide.Supply power voltage can continue to increase, and leaves saturated, as put illustrated in 804 until a bit locate PA204 at certain.Once PA204 is no longer saturated, SATFB signal raises, and represents that saturating control 240 can stop increasing progressively collector voltage or the boosting output of PA204.In certain embodiments, by supply power voltage boosting or more than rising to the cell voltage that provides to PAM202.
In example sequential chart, once PA204 leaves saturated, so all items keep constant, until at point 806 place, till receiving the order for adjustment aim power.This order can be in response to the order that receives from base station and receive from call processing device 434.In illustrated example, reduce target power, this can occur when moving closer in base station when wireless device.If wireless device moves away from base station on the contrary, then can increase target power, and sequential chart can illustrated voltage raise on increase instead of reduce.Base station can ask wireless device to change its target power, uses with other of this base station communication to prevent from disturbing.Such as, if base station is configured to the code division multiple access (CDMA) being used as spread spectrum communication standard, then multiple wireless device can use different codes to launch with identical frequency.In order to base station from these wireless device Received signal strength each, can expect to make watt level roughly equal.If wireless device is launched with much higher watt level, then this wireless device may form the obstacle for other wireless device.Thus, expect to maintain constant watt level.
In response to the request for reducing target power, wireless device can APT table in reference to storage 418, to identify the corresponding target voltage for target power, and saturating control can be made correspondingly to adjust boosting, make to reduce power output.In addition, RFFE kernel 304 can receive new initial or default value, and it is stored in shadow register 306.If PA204 starts compression, then oblique wave clock generator 312 is used to increase progressively the new initial value provided to saturating control 240, to adjust the reference signal that saturating control 240 provides, to adjust the supply power voltage provided to PA204.Whenever receiving new APT value, saturating control 240 by providing reset signal to reset to ramp generator 308, and can receive the new default value corresponding with target AP T voltage at RFFE kernel 304 place.
In certain embodiments, the time quantum of non-zero can be taken for subtracting low power transition (transition).After this manner, at voltage-transition time durations, stop modulation.This is illustrated by the flat line in the RF input line of sequential chart.Timing for adjusting voltage can be very little.Such as, the order of magnitude of 25 microseconds can be in for the timing of Voltage Cortrol.Once time window in the past and Voltage Cortrol complete, so recover modulation, as illustrated in the example sequential chart of Fig. 8.If deactivation (deactivate) wireless device or deactivate the radio function (such as, non-transmitting mode) of this device, then can deactivate PA and voltage raises, illustrated in latter two pulse in sequential chart.
simulation result
Fig. 9-12 illustrates the some curve charts corresponding with the emulation utilized performed by the VSWR of 2:1 (or 2 to 1).2:1VSWR value is through being usually used in measured power amplifier.Fig. 9 illustrates the curve chart 900 of the base current of the grounded-base transistor of the cascode power amplifier compared for 2:1VSWR and the base current of common-emitter transistor.Curve chart 900 comprises many lines, its each correspond to the Vcc of 11.5 volts for the lowest part line in curve chart 900 and the different voltage levels between the Vcc of 9 volts for the highest point line in this curve chart.During it, PA considered to be in saturated ratio and can change based on technique and specification.This is specifically emulated, determine saturated occur between current value exist 20% difference or 1.2 ratio time.When these pressure-wires are at 1.2 current ratio line more than 902, the PA of emulation is considered to saturated, and when these pressure-wires are at 1.2 current ratio line less than 902, the PA of emulation is considered to undersaturated.
Figure 10 illustrates the curve chart 1000 described for the adjacent channel leakage ratio (ACLR) of the function as load of the 2:1VSWR situation of Fig. 9.ACLR curve chart 1000 illustrates the frequency spectrum in the channel measuring the frequency spectrum direct neighbor utilized with wireless device, to define in how many transmit signal leakages to the frequency spectrum of another wireless device or to leak in adjacent channel.The distortion occurred when PA204 is saturated can make the spectrum leakage of wireless device in the frequency spectrum of another wireless device.This is specifically emulated, determines saturated occurring in and exist when leaking more than-36dB (illustrated in horizontal line 1002).Here embodiment detects spectrum leakage by detecting PA compression and eliminating this compression and reduces or eliminate this leakage.The information of Fig. 9 can with the information cross-reference of Figure 10, to determine various magnitudes of voltage across emulation PA to detect the validity of the embodiment here of saturated and spectrum leakage.
Figure 11 illustrate describe when by Fig. 9 with 10 saturation detection associate with embodiment described here with ACLR time the curve chart 1100 of saturated situation do not detected.As stated previously, when current ratio is 1.2 or larger, think that PA is in compression, wherein PA has transistor operation in saturation condition.Point on curve chart 1100 is that the saturating control of emulation does not detect saturated measurement point.Transition between the line 1102 that-36dB locates indicates when the PA emulated considered to be in saturated.
Y-axis represents ACLR, and is used for emulate selected release99ofthe3 in horizontal line 1102 representative of-36dB place mark rdthe maximum acceptable adjacent channel leakage of GenerationPartnershipProject (R993GPP) specification (issue 99 (R993GPP) of third generation partner program) specification.R993GPP relates to the evolution of the 3G mobile telephone system based on global system for mobile communications (GSM) specification.R993GPP specification needs to there will not be higher than-36dBc to the leakage in adjacent channel.Each symbol in curve chart 1100 is the measurement data points that the current comparator 236 of PA for emulating does not indicate the ACLR under saturated conditions.Thus, during emulating, measure and compare two base currents of RF device and cascode device.If obtain be relatively be less than 20% or ratio be less than 1.2, then determine PA and be not in saturated.In curve chart 1100, each measurement data points has the ratio being less than 1.2.Measurement data points associates with ACLR.Be used to indicate the distinct symbols of measurement data points corresponding to 9 volts for emulating and the different magnitudes of voltage between 11.5 volts.
As previously mentioned, line 1102 marks the threshold value of maximum acceptable ACLR.As found out in curve chart 1100, great majority instruction PA is not in the line less than 1102 that compression or saturated point are in the accepted ACLR of instruction when not detecting saturated.Figure 12 illustrate describe when by Fig. 9 with 10 saturation detection associate with embodiment described here with ACLR time the curve chart 1200 of saturated situation detected.Line 1202 corresponds to the line 1102 that instruction is used for the threshold value that can accept ACLR.The saturated generation that the saturating control 240 of illustrated instruction emulation detects in curve chart 1200.In other words, current comparator 236 determine current ratio be greater than 20% or be greater than 1.2 point.As illustrated in curve chart 1200, the point of great majority instruction PA compression is in the line more than 1202 of the unacceptable ACLR of instruction when detecting saturated.
Thus, as found out by comparative graph 1100 and 1200, curve chart indicates analogue system and can be used in the embodiments described herein and in most of time, saturated generation detected with the base current comparing cascode PA.Once detect saturated, one or more embodiment described herein so can be applied in, saturated to make PA leave.
term
Unless context clearly separately has requirement, otherwise run through specification and claims, will according to the meaning of adversative the comprising property with exclusiveness or exhaustive, that is, " comprise (comprise) " to explain term according to the meaning of " including but not limited to ", " comprising (comprising) " etc.Term " couples " connection be used in reference between two elements, and this term refers to two or more elements that directly can connect or connect by means of one or more intermediary element.In addition, when used in this application, term " here ", " above ", " below " and the term of similar implication should refer to the application as a whole, instead of any concrete part of the application.When context allows, use the term in the above detailed description of odd number or plural number also can comprise plural number or odd number respectively.Mention the term "or" during list of two or more projects, it is whole that this term is contained in the following explanation of this term: any combination of project in any project in list, all items in list and list.
The above detailed description of the embodiment of the present invention is not intended to be exhaustive, or precise forms disclosed above limiting the invention to.Although describe specific embodiments of the invention above for purposes of illustration and for example of the present invention, as the skilled person will recognize, various equivalent modifications are within the scope of the present invention possible.Such as, although according to presenting process or block to definite sequence, but the embodiment of replacing can perform the process of the step with different order, or adopt the system with the block of different order, and some process or block can deleted, mobile, add, deduct, combine and/or revise.Can according to various different mode realize these process or block in each.Similarly, perform serially although sometimes process or block are depicted as, on the contrary, these process or block also can perform concurrently, or can perform at different time.
The instruction of the present invention provided can be applied to other system here, and need not to be above-mentioned system.Can combine the element of each above-mentioned embodiment and action, to provide further embodiment.
Unless otherwise expressly specified, or as another Rational Solutions in the context that uses, otherwise the conditional statement here used, inter alia such as " can ", " possibility ", " meeting ", " such as " etc., be generally intended to show that some embodiment comprises and other embodiments do not comprise some feature, element and/or state.Thus, it is that one or more embodiment is necessary by any way that such conditional statement is generally not intended to imply that feature, element and/or state are, or implies one or more embodiment necessarily comprises for judging whether comprise the logic that maybe will perform these features, element and/or feature in any specific embodiment when being with or without designer's input or prompting.
Unless otherwise expressly specified, or as another Rational Solutions in the context that uses, otherwise the such as Disjunctive Languages (disjunctivelanguage) of phrase " in X, Y or Z at least one " and so on is generally used for, and to present a project, entry etc. can be X, Y or Z, or its combination in any (such as, X, Y and/or Z).Thus, this Disjunctive Languages is general and be not intended to and should do not imply that some embodiment needs to present at least one of X, at least one each of at least one or the Z of Y.
Unless expressly stated otherwise, otherwise the article of such as "a" or "an" and so on generally should be interpreted as comprising one or more described project.Correspondingly, such as the phrase of " a kind of device, is configured to " and so on is intended to comprise individual or multiple cited device.This one or more cited device also can be described (recitation) illustrated by being jointly configured to perform.Such as, " a kind of processor, be configured to perform describe A, B and C " can comprise being configured to perform and describe the first processor of A, and it is configured to perform the second processor describing B and C and works in combination.
Although described some embodiment of the present invention, only present these embodiments by means of example, and described embodiment is not intended to limit the scope of the application.In fact, novel method described here and system can be implemented according to other forms multiple; In addition, the pro forma various omission of method and system described herein, replacement and change can be made at, and not depart from the spirit of the application.Accompanying drawing and their equivalent are intended to contain this form as fallen in the scope and spirit of the application or amendment.

Claims (20)

1. a power amplifier module, comprising:
Power amplifier, comprises cascode transistor pair, and described cascode transistor is to comprising the first transistor and transistor seconds;
Power amplifier bias controller, comprises current comparator, and described current comparator is configured to the first base current of more described the first transistor and the second base current of described transistor seconds, to obtain comparison value; And
Saturating control, is configured to provide reference signal based on described comparison value to impedance matching network, and described impedance matching network is configured to change the load impedance with the load line of described power amplifier telecommunication based on described reference signal at least partly.
2. power amplifier module according to claim 1, wherein, described the first transistor is grounded-base transistor, and described transistor seconds is common-emitter transistor.
3. power amplifier module according to claim 1, wherein, described load line and antenna carry out telecommunication, and described load line is electrically between described power amplifier and described antenna.
4. power amplifier module according to claim 1, wherein, described impedance matching network is dynamic impedance matching network.
5. power amplifier module according to claim 1, wherein, the described saturating control load impedance be also configured to by changing described load line reduces the compression of described power amplifier.
6. power amplifier module according to claim 1, wherein, described saturating control also comprises digital to analog converter and ramp generator, described ramp generator is configured to provide count value to described digital to analog converter, and described digital to analog converter is configured to generate described reference signal based on described count value at least partly.
7. power amplifier module according to claim 6, wherein, described saturating control comprises the pull-down-resistor carrying out telecommunication with described power amplifier bias controller, voltage I/O pin and oblique wave clock generator, whether described oblique wave clock generator is configured to detect described the first transistor based on the voltage across described pull-down-resistor and operates in zone of saturation, described voltage is at least partly based on described comparison value, and in response to detecting that described the first transistor operates in described zone of saturation, described oblique wave clock generator is configured such that described count value changed by described ramp generator.
8. power amplifier module according to claim 6, wherein, described digital to analog converter is also configured to generate described reference signal based on average power pursuit gain at least partly, and described average power pursuit gain is determined based on the target power signal received from base station.
9. power amplifier module according to claim 6, wherein, described saturating control also comprises RF front end, is configured to receive default data value from saturated data pins, and described count value initially corresponds to described default data value.
10. power amplifier module according to claim 9, wherein, described default data value is one of multiple default data value, and described default data value based target voltage is selected.
11. power amplifier modules according to claim 10, wherein, described target voltage is determined based on the target power signal received from base station at least partly.
12. power amplifier modules according to claim 1, also comprise: boost converter, are configured to regulate the supply power voltage provided to described power amplifier.
13. power amplifier modules according to claim 12, wherein, described saturating control is also configured to the compression being reduced described power amplifier by the combination of following operation: provide the second reference signal to increase described supply power voltage to described boost converter; And by providing described reference signal to change the load impedance of described load line to described impedance matching network.
14. 1 kinds of transceivers, comprising:
Impedance matching network, is configured to change based on reference signal the load impedance carrying out the load line of telecommunication with power amplifier and antenna; And
Power amplifier module, comprise power amplifier, power amplifier bias controller, and saturating control, described power amplifier comprises cascode transistor pair, described cascode transistor is to comprising the first transistor and transistor seconds, described power amplifier bias controller comprises current comparator, described current comparator is configured to the base current of more described the first transistor and the base current of described transistor seconds to obtain comparison value, described saturating control is configured to generate described reference signal based on described comparison value at least partly and provide described reference signal to described impedance matching network.
15. transceivers according to claim 14, wherein, described impedance matching network is dynamic impedance matching network.
16. transceivers according to claim 14, wherein, described saturating control also comprises digital to analog converter and ramp generator, described ramp generator is configured to provide count value to described digital to analog converter, and described digital to analog converter is configured to generate described reference signal based on described count value at least partly.
17. transceivers according to claim 16, wherein, described saturating control comprises the pull-down-resistor carrying out telecommunication with described power amplifier bias controller, voltage I/O pin and oblique wave clock generator, whether described oblique wave clock generator is configured to detect described the first transistor based on the voltage across described pull-down-resistor and operates in zone of saturation, described voltage is at least partly based on described comparison value, and described oblique wave clock generator is configured in response to detecting that described the first transistor operates in described zone of saturation, described ramp generator is made to change described count value.
18. transceivers according to claim 14, also comprise: boost converter, are configured to regulate the supply power voltage provided to described power amplifier.
19. transceivers according to claim 14, wherein, described saturating control is also configured to the compression being reduced described power amplifier by the combination of following operation: provide the second reference signal to increase described supply power voltage to described boost converter; And by providing described reference signal to change the load impedance of described load line to described impedance matching network.
20. 1 kinds of wireless devices, comprising:
Antenna, is configured at least launch the signal from transceiver, and described signal is at least partly based on the radio-frequency input signals that the power amplifier to described transceiver provides; And
Described transceiver, comprise impedance matching network and power amplifier module, described impedance matching network is configured to change based on reference signal the load impedance carrying out the load line of telecommunication with described power amplifier and described antenna, described power amplifier module comprises power amplifier, power amplifier bias controller, and saturating control, described power amplifier comprises cascode transistor pair, described cascode transistor is to comprising the first transistor and transistor seconds, described power amplifier bias controller comprises current comparator, described current comparator is configured to the base current of more described the first transistor and the base current of described transistor seconds to obtain comparison value, described saturating control is configured to generate described reference signal based on described comparison value at least partly and provide described reference signal to described impedance matching network.
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