CN105323048A - Generating method of preamble symbol in physical frame - Google Patents

Abstract

The invention discloses a generating method of a preamble symbol in a physical frame, comprising the following steps: carrying out discrete Fourier inverse transform on a frequency-domain OFDM symbol of a predetermined length to obtain a time-domain OFDM symbol; intercepting a time-domain OFDM symbol of the cyclic prefix length from the time-domain OFDM symbol as a cyclic prefix; generating a modulation signal based on the intercepted time-domain OFDM symbol of the cyclic prefix length; and generating a preamble symbol based on the cyclic prefix, the time-domain OFDM symbol and the modulation signal. By adopting the technical scheme, the problem in the current DVB_T2 standard and other standards that a DVB_T2 time-domain structure has no cyclic prefix and is not applicable to coherent detection and detection of a preamble symbol by using a low-complexity receiving algorithm under a complex frequency-selective fading channel may fail is solved.

Description

Method for generating preamble symbol in physical frame

Technical Field

The invention relates to the technical field of wireless broadcast communication, in particular to a method for generating a preamble symbol in a physical frame.

Background

Generally, in order for a receiving end of an OFDM system to correctly demodulate data transmitted by a transmitting end, the OFDM system must implement accurate and reliable time synchronization between the transmitting end and the receiving end. Meanwhile, since the OFDM system is very sensitive to the carrier frequency offset, the receiving end of the OFDM system needs to provide an accurate and efficient carrier frequency spectrum estimation method to accurately estimate and correct the carrier frequency offset.

At present, a method for implementing time synchronization between a transmitting end and a receiving end in an OFDM system is basically implemented based on preamble symbols. The preamble symbol is a symbol sequence known to both the transmitting end and the receiving end of the OFDM system, and serves as the start of a physical frame (named P1 symbol), and only one P1 symbol or a plurality of P1 symbols occur consecutively in each physical frame, which marks the start of the physical frame. The P1 symbols have the following uses:

1) enabling a receiving end to quickly detect whether a signal transmitted in a channel is an expected received signal;

2) providing basic transmission parameters (such as FFT point number, frame type information and the like) so that a receiving end can perform subsequent receiving processing;

3) detecting initial carrier frequency offset and timing error, and compensating to achieve frequency and timing synchronization;

4) emergency alerts or broadcast system wake-up.

The DVB _ T2 standard provides a P1 symbol design based on a CAB time domain structure, and the functions are well realized. However, there are still some limitations on low complexity reception algorithms. For example, in a long multipath channel with 1024, 542, or 482 symbols, a large deviation occurs in timing coarse synchronization using the CAB structure, which results in an error in estimating the carrier integer multiple frequency offset in the frequency domain. Additionally, DBPSK differential decoding may also fail in complex frequency selective fading channels, such as long multipath. Moreover, since the DVB _ T2 has no cyclic prefix in the time domain structure, if the DVB _ T2 is combined with a frequency domain structure that needs to perform channel estimation, the performance of the frequency domain channel estimation is seriously degraded.

Disclosure of Invention

The invention solves the problems that in the current DVB _ T2 standard and other standards, a DVB _ T2 time domain structure has no cyclic prefix, so that the DVB _ T2 standard and other standards cannot be applied to coherent detection, and the detection of preamble symbols in a complex frequency selective fading channel by a low-complexity receiving algorithm has failure probability.

In order to solve the above problem, an embodiment of the present invention provides a method for generating a preamble symbol in a physical frame, including the following steps: performing inverse discrete Fourier transform on the frequency domain OFDM symbol with the preset length to obtain a time domain OFDM symbol; intercepting a time domain OFDM symbol with a cyclic prefix length from the time domain OFDM symbol as a cyclic prefix; generating a modulation signal based on the intercepted time domain OFDM symbol with the cyclic prefix length; generating a preamble symbol based on the cyclic prefix, the time domain OFDM symbol, and the modulation signal.

Optionally, before the time domain OFDM symbol with the cyclic prefix length is truncated from the time domain OFDM symbol as the cyclic prefix, the method further includes: and selecting different combinations of the cyclic prefix length and the modulation signal length so that the finally formed preamble symbol transmits the signaling information through the different combinations.

Optionally, the selecting different combinations of the cyclic prefix length and the modulation signal length, and transmitting signaling information in the time domain OFDM symbol includes: determining the bit number N of signaling information to be transmitted; selection 2^NDifferent combinations of cyclic prefix length and modulation signal length, so that the finally formed preamble symbol passes through the above 2^NDifferent combinations to transmit signaling information. .

Optionally, before the time domain OFDM symbol with the cyclic prefix length is truncated from the time domain OFDM symbol as the cyclic prefix, the method further includes:

determining a combination of the cyclic prefix length and the modulated signal length;

and selecting different starting positions from the time domain OFDM symbols for intercepting the cyclic prefix length to intercept the time domain OFDM symbols with the modulation signal length to generate a modulation signal, so that the finally formed preamble symbols transmit signaling information through the different starting positions.

Optionally, the signaling information includes an emergency alert or broadcast system identifier EAS _ flag, transmitter flag information TXID, hook information, or other transmission parameters.

Optionally, before performing inverse discrete fourier transform on the frequency domain OFDM symbol with the predetermined length to obtain the time domain OFDM symbol, the method further includes the following steps:

determining an average power ratio of the fixed sequence and the signaling sequence;

respectively generating a fixed sequence and a signaling sequence on a frequency domain according to the average power ratio;

filling a fixed sequence and a signaling sequence onto effective subcarriers, wherein the fixed sequence and the signaling sequence are arranged in a parity staggered manner;

and filling zero sequence subcarriers on two sides of the effective subcarriers respectively to form frequency domain OFDM symbols with preset length.

Optionally, the average power of the fixed sequence and the average power of the signaling sequence are the same or different.

Optionally, the power ratio between the fixed sequence and the signaling sequence is 1: 1 or 3: 2 or 2:1 or 3: 1.

compared with the prior art, the technical scheme of the invention has the following beneficial effects:

according to the method for generating the preamble symbol in the physical frame provided by the embodiment of the invention, the cyclic prefix length is determined according to different channel environments, and the time domain OFDM symbol with the cyclic prefix length is intercepted from the time domain OFDM symbol to be used as the cyclic prefix, so that the problem of the reduction of the frequency domain channel estimation performance is solved. And generating a modulation signal based on the intercepted time domain OFDM symbol with the cyclic prefix length, so that the generated preamble symbol has good decimal frequency offset estimation performance and timing synchronization performance.

Further, different combinations of the cyclic prefix length and the modulation signal length are selected, so that the finally formed preamble symbols transmit the signaling information through the different combinations; or determining a combination of the cyclic prefix length and the modulation signal length, and selecting different starting positions from the time domain OFDM symbols for cutting the cyclic prefix length to cut the time domain OFDM symbols of the modulation signal length to generate modulation signals, so that the finally formed preamble symbols transmit signaling information through the different starting positions.

Furthermore, the structure of the modulation signal using the time domain OFDM symbol and the time domain OFDM symbol (as a preamble symbol) ensures that a distinct peak can be obtained at the receiving end using delay correlation. In addition, in the process of generating the preamble symbol, the modulation signal of the time domain OFDM symbol is designed to avoid that the receiving end is subjected to continuous wave interference or single frequency interference, or that a multipath channel with the same length as the modulation signal occurs, or that a false detection peak occurs when the guard interval length in the received signal is the same as the modulation signal length.

Drawings

Fig. 1 is a flowchart illustrating a method for generating preamble symbols in a physical frame according to an embodiment of the present invention;

fig. 2 is a schematic diagram of a CAB structure of a preamble symbol generated by the method for generating a preamble symbol in a physical frame shown in fig. 1;

fig. 3A is a schematic diagram illustrating a CAB structure for transmitting a preamble symbol of an emergency alert or broadcast system flag EAS _ flag according to the present invention;

fig. 3B is a schematic diagram illustrating a CAB structure of a preamble symbol for transmitting an emergency alert or broadcast system flag EAS _ flag according to another embodiment of the present invention;

fig. 4 is a schematic flow chart of a specific embodiment of generating a frequency domain OFDM symbol in a method for generating preamble symbols in a physical frame according to the present invention.

Detailed Description

The inventor finds that in the current DVB _ T2 standard and other standards, the DVB _ T2 time domain structure has no cyclic prefix, and the preamble symbol has the problem of low complexity receiving algorithm detection failure probability under a frequency selective fading channel.

In view of the above problems, the inventors have studied and provided a method for generating preamble symbols in a physical frame. The cyclic prefix is arranged in the time domain structure, the problem of the performance reduction of frequency domain channel estimation is solved, and all or part of data segments of the cyclic prefix part are utilized to generate modulation signals, so that the generated preamble symbols have good small frequency offset and timing synchronization performance.

Selecting different combinations of the cyclic prefix length and the modulation signal length so that the finally formed preamble symbol transmits signaling information through the different combinations; or determining a combination of the cyclic prefix length and the modulation signal length, and selecting different starting positions from the time domain OFDM symbols for cutting the cyclic prefix length to cut the time domain OFDM symbols of the modulation signal length to generate modulation signals, so that the finally formed preamble symbols transmit signaling information through the different starting positions.

Further, the receiving end can still process the received signal within the range of-500 kHz to 500kHz by ensuring the carrier frequency deviation.

In order to make the aforementioned objects, features and advantages of the present invention comprehensible, embodiments accompanied with figures are described in detail below.

Fig. 1 is a flowchart illustrating a method for generating preamble symbols in a physical frame according to an embodiment of the present invention. Referring to fig. 1, a method for generating preamble symbols in a physical frame includes the steps of:

step S15: performing inverse discrete Fourier transform on the frequency domain OFDM symbol with the preset length to obtain a time domain OFDM symbol;

step S16: intercepting a time domain OFDM symbol with a cyclic prefix length from the time domain OFDM symbol as a cyclic prefix;

step S17: generating a modulation signal based on the intercepted time domain OFDM symbol with the cyclic prefix length;

step S18: generating a preamble symbol based on the cyclic prefix, the time domain OFDM symbol, and the modulation signal.

In this embodiment, as described in step S15, a frequency domain OFDM symbol of a predetermined length is subjected to inverse discrete fourier transform to obtain a time domain OFDM symbol.

The inverse discrete fourier transform described in this step is a common way of converting a frequency domain signal into a time domain signal, and is not described herein again.

P1_X_iObtaining a time domain OFDM symbol after performing inverse discrete Fourier transform:

$P1\_A\left(t\right)=\frac{1}{\sqrt{M}}\underset{i=0}{\overset{1023}{\mathrm{\Σ}}}P1\_X_i{e}^{j2\mathrm{\π}\frac{(i-512)}{1024T}t},$ wherein M is the number of effective non-zero subcarriers.

As stated in step S16, a cyclic prefix length time domain OFDM symbol is truncated from the time domain OFDM symbol as a cyclic prefix.

In this embodiment, the cyclic prefix length is equal to or less than the predetermined length. Taking the predetermined length as 1024 as an example, the cyclic prefix length may be 1024 or less than 1024. Preferably, the cyclic prefix length is 512, and the latter half (length is 512) of the time domain OFDM symbol is usually truncated as the cyclic prefix, so as to solve the problem of performance degradation of frequency domain channel estimation.

The determined cyclic prefix length is determined according to any one or more factors of the multi-path length which the wireless broadcast communication system usually needs to resist, the minimum length of a robust correlation peak value obtained by the system at the lowest receiving threshold, and the number of bits of the time domain structure transmission signaling. If only the signaling needs to be transmitted in the frequency domain structure, and the time domain structure is fixed and no signaling needs to be transmitted, only one or two of the multipath length to be countered and the minimum length of the robust correlation peak obtained by the system at the lowest receiving threshold need to be considered. In general, the longer the length of the cyclic prefix, the better the performance against long multipath, and the longer the length of the cyclic prefix and the length of the modulated signal, the more robust the peak of its delay correlation. Generally, the length of the cyclic prefix and the length of the modulation signal are required to be greater than or equal to the minimum length of the robust correlation peak obtained by the system at the lowest receiving threshold.

And as indicated by step S17, generating a modulated signal based on the truncated time domain OFDM symbol with the cyclic prefix length. In practice, the modulated signal length typically does not exceed the length of the cyclic prefix portion.

Specifically, the method comprises the following steps:

1) setting a frequency offset sequence;

2) and multiplying the time domain OFDM symbol with the cyclic prefix length or a part of the time domain OFDM symbol with the cyclic prefix length by the frequency offset sequence to obtain the modulation signal.

For example, let N_cpFor a determined cyclic prefix length, Len_BIs the modulation signal length. The modulation signal length is determined by the minimum length of the robust correlation peak that the system can obtain at the lowest receive threshold. Typically the modulation signal length is equal to or greater than the minimum length. Let N_ASetting the sampling point serial number of the time domain OFDM symbol as 0,1, … N for the length of the time domain OFDM symbol_AAnd 1, setting N1 as the sampling point sequence number of the time domain OFDM symbol corresponding to the starting point selected to be copied to the modulation signal segment, and setting N2 as the sampling point sequence number of the time domain OFDM symbol corresponding to the end point selected to be copied to the modulation signal segment. Wherein,

N2＝N1+Len_B-1

for convenience of description, the time domain OFDM symbol is divided into 2 parts, the first part is a part of the time domain OFDM symbol (generally, the front part of the time domain OFDM symbol) which is not truncated as a cyclic prefix, and the second part is a part of the time domain OFDM symbol (generally, the rear part of the time domain OFDM symbol) which is truncated as a cyclic prefix. If all the time domain OFDM symbols are intercepted as cyclic prefixes, the length of the first section is 0. N1 must fall within the second segment, i.e., the portion of the time domain OFDM symbol selected for the modulated signal segment does not span beyond the portion of the time domain OFDM symbol truncated as a cyclic prefix.

The modulation signal part and the cyclic prefix part are the same as part of information in the time domain OFDM symbol. The modulated signal part is only modulated with frequency offset or other signals, so that the correlation value between the modulated signal part and the cyclic prefix part and the correlation value between the modulated signal part and the time domain OFDM symbol can be used for timing synchronization and small offset estimation. In practice, the modulated signal length typically does not exceed the cyclic prefix length. If the length of the modulated signal is greater than the length of the cyclic prefix, the excess part will increase the overhead of the system, resulting in a reduction in transmission efficiency, and it can only enhance the robustness of the correlation value between the modulated signal part and the time domain OFDM symbol, and under the same overhead, the length of the excess part should be increased to the length of the cyclic prefix, which will bring more performance benefits.

As shown in fig. 2, a segment a represents a time domain OFDM symbol, a segment C represents a cyclic prefix, and a segment B represents a modulated signal. The frequency offset sequence isWherein f is_SHMay be selected as the frequency domain subcarrier spacing (i.e., 1/N) corresponding to the time domain OFDM symbol_AT), where T is the sampling period, N_AIs the length of the time domain OFDM symbol. In this example, N_AIs 1024, take f_SH1/1024T. In other examples, to sharpen the correlation peak, f_SHCan also be selected to be 1/(Len)_BT). When Len_B＝N_CPWhen f is present_SH＝1/N_CPAnd T. Such as Len_B＝N_CPWhen is 512, f_SH＝1/512T。

In other embodiments, m (t) may also be designed into other sequences, such as an m-sequence or some simplified window sequence.

The modulation signal of the partial time domain OFDM symbol is P1_ b (t), P1_ b (t) is obtained by multiplying the partial time domain OFDM symbol by the frequency offset sequence m (t), i.e., P1_ b (t) is:

$P1\_A(t-(N_{\mathrm{cp}}+N_A-N1)T)e^{j2\mathrm{\π}{f}_{\mathrm{SH}}t},$ n1 is the sampling point number of the time domain OFDM symbol selected to be copied to the start of the modulation signal segment.

A preamble symbol is generated based on the cyclic prefix, the time domain OFDM symbol and the modulation signal as described in step S18.

Specifically, the cyclic prefix is spliced at the front of the time domain OFDM symbol as a guard interval, and the modulated signal is spliced at the rear of the OFDM symbol as a modulated frequency offset sequence to generate a preamble symbol, as shown in fig. 2.

For example, the preamble symbol may be based on employing the time domain expression:

$P1\left(t\right)=\left\{\begin{array}{cc}P1\_A(t+(N_A-N_{\mathrm{cp}})T)& 0\&le;t<N_{\mathrm{cp}}T\\ P1\_A(t-N_{\mathrm{cp}}T)& N_{\mathrm{cp}}T\&le;t<(N_A+N_{\mathrm{cp}})T\\ P1\_A(t-(N_{\mathrm{cp}}+N_A-N1)T)e^{j2\mathrm{\&pi;}{f}_{\mathrm{SH}}t}& (N_A+N_{\mathrm{cp}})T\&le;t<(N_A+N_{\mathrm{cp}}+{\mathrm{Len}}_B)T\\ 0& \mathrm{otherwise}\end{array}\right.$

in a preferred embodiment, the predetermined length N_A＝1024；N_cpIs half of said predetermined length, i.e. when N_AWhen is 1024, N_cp＝512。

When the time domain structure of the preamble symbol is not needed for signaling transmission, only a fixed starting point is taken when generating the modulated signal. Preferably, Len is set_B＝N_cpAnd N1 ═ N_A-N_cpI.e. by

$P1\left(t\right)=\left\{\begin{array}{cc}P1\_A(t+(N_A-N_{\mathrm{cp}})T)& 0\&le;t<N_{\mathrm{cp}}T\\ P1\_A(t-N_{\mathrm{cp}}T)& N_{\mathrm{cp}}T\&le;t<(N_A+N_{\mathrm{cp}})T\\ P1\_A(t-2N_{\mathrm{cp}}T)e^{j2\mathrm{\&pi;}{f}_{\mathrm{SH}}t}& (N_A+N_{\mathrm{cp}})T\&le;t<(N_A+N_{\mathrm{cp}})T\\ 0& \mathrm{otherwise}\end{array}\right.$

When N is present_A＝1024，N_cpWhen equal to 512, Len_B＝512，N1＝512。

Further, in this embodiment, different cyclic prefixes and modulation signals are generated, so that the finally formed preamble symbols are also different, so that when the receiving end demodulates the preamble symbols in the received physical frame, the receiving end can perform delay correlation operation on the preamble symbols, and different delays are set according to the attempt, wherein an obvious correlation peak value can be obtained only by matching the delay value with the design parameters of the preamble symbols, so as to distinguish different preamble symbols, thereby achieving the purpose of transmitting signaling information in the time domain structure of the preamble symbols.

As a specific example, the method further includes, before the step S16, the following steps: and selecting different combinations of the cyclic prefix length and the modulation signal length so that the finally formed preamble symbol transmits the signaling information through the different combinations.

Specifically, the steps include:

1) determining the bit number N of signaling information to be transmitted;

2) selection 2^NDifferent combinations of cyclic prefix length and modulation signal length, so that the finally formed preamble symbol passes through the above 2^NDifferent combinations to transmit signaling information.

In practice, some signaling information (e.g. emergency alert or broadcast system identification EAS _ flag) only needs 1 bit, and some signaling information (e.g. signaling information)Transmitter identification information TXID) requires 4 bits. Thus, different combinations of cyclic prefix length and modulated signal length are determined according to the number of bits (set to N) of the signaling information to be transmitted, the total number of which is 2^N。

The transmitted signaling information is exemplified as an emergency alert or a broadcast system identity EAS _ flag.

For example, 1 bit of the EASflag is transmitted. Let the sampling point numbers of the OFDM symbols with the predetermined length of 1024 be 0,1, …, 1023. Let N_cpFor a determined cyclic prefix length, Len_BIs the modulation signal length. Let N_AIs the length of the time domain OFDM symbol.

If EASflag is equal to 0, take N_cp＝Len_B512; handle N_ACopying sampling points with corresponding serial numbers of 512-1023 of 1024 OFDM symbols to C as cyclic prefix, and copying N_AAnd (3) correspondingly sampling points with the serial numbers of 512-1023 of the 1024 OFDM symbols, modulating the frequency offset sequence, generating B, and placing the B at the rear part of A.

If EASflag is equal to 1, take N_CP＝512+K；Len_B512-K; handle N_AThe sampling point with the corresponding serial number of 512-K to 1023 of the OFDM symbol with 1024 is copied to C as a cyclic prefix, and N is used_AAnd the corresponding sampling point with the serial number of 512+ K-1023 of the 1024 OFDM symbol generates B after modulating the frequency offset sequence, and the B is placed at the rear part of A.

Preferably, it may be desirable to have Nc ═ N_A/2+K、Nb＝N_A2-K; by selecting 2^NN bits of signaling information are transmitted by different K.

Referring to fig. 3A, a CAB structure for transmitting a preamble symbol of an emergency broadcast system identifier EAS _ flag is shown. The value of K is 0 (corresponding to EAS _ flag ═ 0) and 16 (corresponding to EAS _ flag ═ 1).

The time domain expression is:

if EAS _ flag is 1

$P_{\mathrm{PFB}}\left(t\right)=\left\{\begin{array}{cc}P1\_A(t+(512-K)T)& 0\&le;t<(512+K)T\\ P1\_A(t-(512+K)T)& (512+K)T\&le;t<(1536+K)T\\ P1\_A(t-1024T)e^{j2\mathrm{\&pi;}{f}_{\mathrm{SH}}t}& (1536+K)T\&le;t<2048T\\ 0& \mathrm{otherwise}\end{array}\right.$

If EAS _ flag is equal to 0

$P_{\mathrm{PFB}}\left(t\right)=\left\{\begin{array}{cc}P1\_A(t+512T)& 0\&le;t<512T\\ P1\_A(t-512T)& 512T\&le;t<1536T\\ P1\_A(t-1024T)e^{j2\mathrm{\&pi;}{f}_{\mathrm{SH}}t}& 1536T\&le;t<2048T\\ 0& \mathrm{otherwise}\end{array}\right.$

The frequency offset sequence isWherein f is_SHCan be selected as the frequency domain subcarrier interval corresponding to the time domain OFDM symbol, namely 1/N_AT, where T is the sampling period, N_AIs the length of the time domain OFDM symbol, in this example, N_AIs 1024, take f_SH＝1/1024T。

As another specific example, the method further includes, before the step S16, the following steps:

determining a combination of the cyclic prefix length and the modulated signal length;

and selecting different starting positions from the time domain OFDM symbols for intercepting the cyclic prefix length to intercept the time domain OFDM symbols with the modulation signal length to generate a modulation signal, so that the finally formed preamble symbols transmit signaling information through the different starting positions.

The transmitted signaling information is exemplified as an emergency alert or a broadcast system identity EAS _ flag.

For example, the predetermined length is 1024, N_CPIs 512+ K, Len_B512-K, the length of the whole preamble symbol is 2048, wherein the modulation frequency offset value f_SH1/1024T, the emergency alert or broadcast system identity EAS _ flag is signaled by selecting a different starting position N1 for transmission of the 1-bit signaling.

If EAS _ flag is equal to 1, taking N1 as 512-L, i.e. N is equal to_AAnd the corresponding sampling point with the serial number of 512-L to 1023-2L of the OFDM symbol of 1024 generates B after modulating the frequency offset sequence, and the B is placed at the rear part of A.

If EAS _ flag is equal to 0, N1 is equal to 512+ L, i.e. N is equal to_AAnd the corresponding sampling point with the serial number of 512+ L-1023 of the 1024 OFDM symbol generates B after modulating the frequency offset sequence, and the B is placed at the rear part of A.

Referring to fig. 3B, a CAB structure for transmitting a preamble symbol of an emergency alert or broadcast system flag EAS _ flag is shown. Wherein the value of L is 8.

The time domain expression is:

if EAS _ flag is 1

$P_1\left(t\right)=\left\{\begin{array}{cc}P1\_A(t+(512-L)T)& 0\&le;t<(512+L)T\\ P1\_A(t-(512+L)T)& (512+L)T\&le;t<(1536+L)T\\ P1\_A(t-(1024+2L)T)e^{j2\mathrm{\&pi;}{f}_{\mathrm{SH}}t}& (1536+L)T\&le;t<2048T\\ 0& \mathrm{otherwise}\end{array}\right.$

If EAS _ flag is equal to 0

$P_1\left(t\right)=\left\{\begin{array}{cc}P1\_A(t+(512-L)T)& 0\&le;t<(512+L)T\\ P1\_A(t-(512+L)T)& (512+L)T\&le;t<(1536+L)T\\ P1\_A(t-\left(1024\right)T)e^{j2\mathrm{\&pi;}{f}_{\mathrm{SH}}t}& (1536+L)T\&le;t<\left(2048\right)T\\ 0& \mathrm{otherwise}\end{array}\right.$

As another example, the predetermined length is 1024, N_CPIs 512+ 15L, Len_BFor 512, N1 may be 512+ i L, 0 ≦ i<16, 16 different methods can be represented, and 4bit signaling information is transmitted. For example, different transmitters may transmit their corresponding identification TXID by taking a different N1, the same transmitter may also transmit transmission parameters by changing N1 in time. Preferably, L is 16.

As another example, the predetermined length is 1024, N_CPIs 512+ 7L, Len_BFor 512, N1 may be 512+ i L, 0 ≦ i<And 7, transmitting 3-bit signaling information. Preferably, L is 16.

Further, refer to a schematic flow chart of a specific implementation of generating a frequency domain OFDM symbol in a method for generating preamble symbols in a physical frame shown in fig. 4.

Specifically, the method further includes the following steps before the step S15 in the flowchart shown in fig. 1:

step S11: determining an average power ratio of the fixed sequence and the signaling sequence;

step S12: respectively generating a fixed sequence and a signaling sequence on a frequency domain according to the average power ratio;

step S13: filling a fixed sequence and a signaling sequence onto effective subcarriers, wherein the fixed sequence and the signaling sequence are arranged in a parity staggered manner;

step S14: and filling zero sequence subcarriers on two sides of the effective subcarriers respectively to form frequency domain OFDM symbols with preset length.

Specifically, as described in step S11, the average power ratio of the fixed sequence and the signaling sequence is determined. The fixed sequence includes the relevant information that the receiving end can use to do carrier frequency synchronization and timing synchronization, and the signaling sequence includes each basic transmission parameter.

In this embodiment, the fixed sequence and the signaling sequence are both constant modulus sequences, and the modulus of each complex number in the fixed sequence and the signaling sequence is equal. It should be noted that the complex number includes a real number (i.e., the imaginary part of the complex number is zero). Thus, the average power of the signaling sequence and the fixed sequence is the same.

In other embodiments, the average powers of the fixed sequence and the signaling sequence may be the same or different, and may be adjusted according to the actual application requirement, and the power of the fixed sequence is selectively increased to obtain better channel estimation and offset estimation performance, or the power of the signaling sequence is selectively increased to improve the actual signal-to-noise ratio on the signaling carrier to improve the signaling decoding performance. Therefore, the average power ratio of the fixed sequence and the signaling sequence is determined according to the balanced consideration of the whole offset estimation performance, the channel estimation performance, the de-signaling performance and the timing synchronization performance. In this embodiment, the average power ratio between the fixed sequence and the signaling sequence may be 1: 1 or 3: 2 or 2:1 or 3: 1. when the fixed sequence length and the signaling sequence length are the same, the average power ratio is the ratio of the sum of powers.

After the average power ratio is determined, the amplitude ratio of the fixed sequence and the signaling sequence is obtained accordingly. When it is flatWhen the average power ratio is 2:1 and the fixed sequence and the signaling sequence are constant modulus sequences, the amplitude ratio of the corresponding fixed sequence and the corresponding signaling sequence is

As described in step S12, the fixed sequence and the signaling sequence are generated in the frequency domain according to the average power ratio.

In this embodiment, the signaling sequence may be generated in the frequency domain in any one of the following two ways, and the two ways of generating the signaling sequence are described in detail below.

Mode 1:

1.1, determining the length, the number and the amplitude of a signaling sequence;

1.2 determining root values in a CAZAC sequence generation formula based on the length and the number of the signaling sequences; the length of the signaling sequence is smaller than or equal to the root value, and the root value is larger than or equal to twice of the number of the signaling sequences. Preferably, the root value is chosen as the length of the signaling sequence.

For example, the sequence length L and the number of signalings are determined. For example, if N bits are to be transmitted, the number of signaling num is 2^NAnd selecting CAZAC sequence generation formulaThe value of (a). Wherein, the sequence length L is less than or equal to the root value, and the root value is more than or equal to 2 x num. Root values are typically prime numbers.

1.3 selecting different q values to generate a CAZAC sequence, wherein the number of the q values is equal to the number of signaling sequences, and the sum of any two q values is not equal to a root value; and the generated CAZAC sequence needs to undergo cyclic shift, and the number of bits of the cyclic shift is determined by the corresponding root value and q value.

For example, num different q's are selected₀、q₁、……、q_num-1Generating a CAZAC sequence:

s(n)＝exp(jπqn(n+1)/root),n＝0,...root-1。

the sequences after cyclic shift are:

s_k(n)＝[s(k),s(k+1),...,s(L-1),s(0),...,s(k-1)]

where k is the number of cyclically shifted bits.

In this embodiment, q is selected_i(0. ltoreq. i. ltoreq. num-1) must satisfy the following conditions: any 2 q_i、q_j(0. ltoreq. i, j. ltoreq. num-1) satisfies q_i+q_j≠root.

Under the above conditions, a sequence that makes the PAPR of the entire frequency domain OFDM symbol low is preferentially selected. And if L is equal to or greater than 2 × num, root is preferably selected to be L.

1.4 selecting the signaling sequence from all CAZAC sequences according to the determined number of the signaling sequences. Note that, if L is root, truncation is not necessary, and the obtained CAZAC sequence can be used as a signaling sequence.

For example, each of the num sequences is truncated into a continuous partial sequence or a complete sequence with a length of L as a signaling sequence.

For example, if the length L of the signaling sequence is 353 and the number num is 128, the root can be selected as the closest prime 353. The value range of q is 1-352, and the value range of cyclic shift digits of each sequence is 1-353. Among all the selectable signaling sequences, the following 128 groups are preferred, whose q values and cyclic shift bits are respectively shown in the following table:

q value table

Cyclic shift digit table

Based on the known signaling sequence, a preferred fixed sequence is calculated as follows:

$\mathrm{FC}\left(n\right)e^{{\mathrm{j\&omega;}}_n}$

wherein, ω is_nThe values of (A) are arranged in rows from left to right in sequence as shown in the following table:

5.43	2.56	0.71	0.06	2.72	0.77	1.49	6.06	4.82	2.10
										5.62	4.96	4.93	4.84	4.67	5.86	5.74	3.54	2.50	3.75
0.86	1.44	3.83	4.08	5.83	1.47	0.77	1.29	0.16	1.38
										4.38	2.52	3.42	3.46	4.39	0.61	4.02	1.26	2.93	3.84
3.81	6.21	3.80	0.69	5.80	4.28	1.73	3.34	3.08	5.85
										1.39	0.25	1.28	5.14	5.54	2.38	6.20	3.05	4.37	5.41
2.23	0.49	5.12	6.26	3.00	2.60	3.89	5.47	4.83	4.17
										3.36	2.63	3.94	5.13	3.71	5.89	0.94	1.38	1.88	0.13
0.27	4.90	4.89	5.50	3.02	1.94	2.93	6.12	5.47	6.04
										1.14	5.52	2.01	1.08	2.79	0.74	2.30	0.85	0.58	2.25
5.25	0.23	6.01	2.66	2.48	2.79	4.06	1.09	2.48	2.39
										5.39	0.61	6.25	2.62	5.36	3.10	1.56	0.91	0.08	2.52
5.53	3.62	2.90	5.64	3.18	2.36	2.08	6.00	2.69	1.35
										5.39	3.54	2.01	4.88	3.08	0.76	2.13	3.26	2.28	1.32
5.00	3.74	1.82	5.78	2.28	2.44	4.57	1.48	2.48	1.52
										2.70	5.61	3.06	1.07	4.54	4.10	0.09	2.11	0.10	3.18
3.42	2.10	3.50	4.65	2.18	1.77	4.72	5.71	1.48	2.50
										4.89	4.04	6.12	4.28	1.08	2.90	0.24	4.02	1.29	3.61
4.36	6.00	2.45	5.49	1.02	0.85	5.58	2.43	0.83	0.65

1.95	0.79	5.45	1.94	0.31	0.12	3.25	3.75	2.35	0.73
										0.20	6.05	2.98	4.70	0.69	5.97	0.92	2.65	4.17	5.71
1.54	2.84	0.98	1.47	6.18	4.52	4.44	0.44	1.62	6.09
										5.86	2.74	3.27	3.28	0.55	5.46	0.24	5.12	3.09	4.66
4.78	0.39	1.63	1.20	5.26	0.92	5.98	0.78	1.79	0.75
										4.45	1.41	2.56	2.55	1.79	2.54	5.88	1.52	5.04	1.53
5.53	5.93	5.36	5.17	0.99	2.07	3.57	3.67	2.61	1.72
										2.83	0.86	3.16	0.55	5.99	2.06	1.90	0.60	0.05	4.01
6.15	0.10	0.26	2.89	3.12	3.14	0.11	0.11	3.97	5.15
										4.38	2.08	1.27	1.17	0.42	3.47	3.86	2.17	5.07	5.33
2.63	3.20	3.39	3.21	4.58	4.66	2.69	4.67	2.35	2.44
										0.46	4.26	3.63	2.62	3.35	0.84	3.89	4.17	1.77	1.47
2.03	0.88	1.93	0.80	3.94	4.70	6.12	4.27	0.31	4.85
										0.27	0.51	2.70	1.69	2.18	1.95	0.02	1.91	3.13	2.27
5.39	5.45	5.45	1.39	2.85	1.41	0.36	4.34	2.44	1.60
										5.70	2.60	3.41	1.84	5.79	0.69	2.59	1.14	5.28	3.72
5.55	4.92	2.64

the amplitude of the fixed sequence and the signalling sequence is determined in terms of the average power ratio. For example, if the average power ratio of the fixed sequence and the signaling sequence is 1: 1, the modulus values of the fixed sequence and the signaling sequence in the above embodiment are both 1, and the lengths are the same, thereby meeting the power ratio requirement. For another example, in other embodiments, if the average power ratio of the fixed sequence and the signaling sequence is 2:1, if the fixed sequence and the signaling sequence are both constant modulus, assuming that the amplitude of the fixed sequence is 1, the amplitude of the signaling sequence is

Mode 2:

2.1 determining the length, number and amplitude of the signaling sequence;

2.2 determining a plurality of root values in a CAZAC sequence generation formula based on the length and the number of the signaling sequences; the length of the signaling sequence is smaller than or equal to the minimum value of the selected plurality of root values, and the sum of the selected plurality of root values is larger than or equal to twice the number of the signaling sequences. Preferably, the root value is chosen as the length of the signaling sequence.

For example, the sequence length L and the number of signalings are determined. For example, if N bits are to be transmitted, the number of signaling num is 2^NAnd selecting a plurality of K roots of exp (j pi qn (n +1)/root) in the CAZAC sequence generation formula_k(0≤k≤K^-1). Wherein the length L of the signaling sequence is less than or equal to all roots_kMinimum value of, and a number of roots_kIs greater than or equal to 2 x num, i.e.Root in general_kThe values are prime numbers.

2.3 for each root value, selecting different q values to generate a CAZAC sequence, wherein the number of the q values is less than or equal to 1/2 of the corresponding root value, and the sum of any two q values is not equal to the corresponding root value; and the generated CAZAC sequence needs to undergo cyclic shift, and the number of bits of the cyclic shift is determined by the corresponding root value and q value.

For example, for each root_k(K is more than or equal to 0 and less than or equal to K-1), num is selected_kA different q₀、q₁、Generating a CAZAC sequence exp (j π qn (n +1)/root_k),n＝0,...root_k-1. Wherein,

and is $\underset{k=0}{\overset{K-1}{\mathrm{\&Sigma;}}}{\mathrm{num}}_k=\mathrm{num}.$

In this embodiment 2, for each root value, different q values are selected to generate a CAZAC sequence, and the manner in which the generated CAZAC sequence needs to undergo cyclic shift may refer to the description of the above embodiment 1, and will not be described again here.

In this embodiment, q is selected_i(0≤i≤num_k-1) the following conditions must be satisfied: any 2 q_i、q_j(0≤i,j≤num_k-1) satisfies q_i+q_j≠root_k。

Under the above conditions, a sequence that makes the PAPR of the entire frequency domain OFDM symbol low is preferentially selected. And one of the root ═ L may be preferentially selected. So that the autocorrelation value of the sequence generated by the root is zero.

And 2.4 selecting the signaling sequence from each obtained CAZAC sequence according to the determined number of the signaling sequences. It is emphasized that if a root is L, the signaling sequence is determined from the CAZAC sequence generated from the root value selected as the length of the signaling sequence.

For example, each of the num sequences is truncated into a continuous partial sequence or a complete sequence with a length of L as a signaling sequence.

For example, L353 and num 128, for example. Root is preferentially selected to be 353 in mode 1. Then, q is selected to be 1,2, … 128. Satisfy q_i+q_jNot equal to 353, (i is more than or equal to 0, and j is more than or equal to 128-1). Finally, each sequence is truncated to a length of 353.

For another example, L is 350 and num is 256. In mode 2, root1 is selected as 353, root2 as 359, and then for root1 as 353, a total of 128 sequences, q 1,2,3, … 128, are selected, q_i+q_jNot equal to 353. Then 128 sequences of q 100,101,102, … 227 were selected for root2 359, for a total of 256 sequences. Finally each sequence is truncated to a length of 353.

The amplitude of the fixed sequence and the signalling sequence is determined in terms of the average power ratio. For example, if the average power ratio of the fixed sequence and the signaling sequence is 1: 1, the modulus values of the fixed sequence and the signaling sequence in the above embodiment are both 1, and the lengths are the same, thereby meeting the power ratio requirement. For another example, in other embodiments, if the average power ratio between the fixed sequence and the signaling sequence is 2:1, if the fixed sequence and the signaling sequence are both constant modulus, assuming that the amplitude of the fixed sequence is 1, the amplitude of the signaling sequence is

In addition, in other embodiments, if the fixed sequence and the signaling sequence are not constant modulus, the amplitude coefficient calculation is more complicated, but the average power ratio requirement can be realized, and details are not described here.

As shown in step S13, the fixed sequence and the signaling sequence are padded on the active subcarriers and are arranged in a parity staggered manner.

In a preferred embodiment, the length of the fixed sequence is equal to the length of the signaling sequence, and the length is less than 1/2 of the predetermined length. The predetermined length is 1024, but it can be changed according to the system requirement in practical application.

Taking the predetermined length as 1024 as an example, let the length of the fixed sequence be N (that is, the number of the effective subcarriers carrying the fixed sequence be N), and the length of the signaling sequence be M (that is, the number of the effective subcarriers carrying the signaling sequence be M), where M is equal to N in this embodiment. In other embodiments, N may also be slightly larger than M.

The fixed sequence and the signaling sequence are arranged in a parity staggered manner, namely the fixed sequence is filled to the position of even subcarrier (or odd subcarrier), correspondingly, the signaling sequence is filled to the position of odd subcarrier (or even subcarrier), thereby the distribution state of the parity staggered arrangement of the fixed sequence and the signaling sequence is presented on the effective subcarrier of the frequency domain. It should be noted that, when the lengths of the fixed sequence and the signaling sequence are not consistent (for example, M > N), the parity interleaving of the fixed sequence and the signaling sequence may be implemented by means of zero padding sequence subcarriers.

Zero sequence subcarriers are padded on both sides of the effective subcarrier to form frequency domain OFDM symbols of a predetermined length, respectively, as described in step S14.

In a preferred embodiment, this step comprises: and filling zero sequence subcarriers with equal length on two sides of the effective subcarriers respectively to form frequency domain OFDM symbols with preset length.

Following the example of a predetermined length of 1024, the length G of the zero-sequence subcarrier is 1024-M-N, and (1024-M-N)/2 zero-sequence subcarriers are padded on both sides.

Further, in order to ensure that the receiving end can still process the received signal within the carrier frequency deviation range of-500 kHz to 500kHz, the value of (1024-M-N)/2 is usually larger than the critical length value (set to TH), which is determined by the systematic symbol rate and the predetermined length. E.g. a systematic symbol rate of 1024, 7.61M, and a sampling rate of 9.14M, the predetermined length is then 1024 For example, if M is equal to N, 353, G is equal to 318, and 159 zero-sequence subcarriers are padded on each side.

Accordingly, subcarriers (i.e., frequency domain OFDM symbols) P1_ X of a predetermined length (1024) are provided₀,P1_X₁,…,P1_X₁₀₂₃Generated by filling in the following way:

$P1\_X_i=\left\{\begin{array}{cc}0& i=\mathrm{0,1},\&CenterDot;\&CenterDot;\&CenterDot;,G/2-1\\ {\stackrel{\&OverBar;}{\mathrm{FC}}}_{\frac{i-G/2}{2}}& i=G/2,G/2+2,...G/2+2\&times;(N-1)\\ {\stackrel{\&OverBar;}{\mathrm{SC}}}_{\frac{i-G/2-1}{2}}& i=G/2+1,G/2+3,G/2+2\&times;(M-1)+1\\ 0& i=1024-G/2,...1023\end{array}\right.$

wherein the fixed sequence sub-carriersSub-carriers of a signalling sequenceThe parity positions may be interchanged.

Although the present invention has been described with reference to the preferred embodiments, it is not intended to limit the present invention, and those skilled in the art can make variations and modifications of the present invention without departing from the spirit and scope of the present invention by using the methods and technical contents disclosed above.

Claims (29)

1. A method for generating preamble symbols in a physical frame, comprising the steps of:

performing inverse discrete Fourier transform on the frequency domain OFDM symbol with the preset length to obtain a time domain OFDM symbol;

intercepting a time domain OFDM symbol with a cyclic prefix length from the time domain OFDM symbol as a cyclic prefix;

generating a modulation signal based on the intercepted time domain OFDM symbol with the cyclic prefix length;

generating a preamble symbol based on the cyclic prefix, the time domain OFDM symbol, and the modulation signal.

2. A method for generating preamble symbols in a physical frame as claimed in claim 1, wherein the length of the cyclic prefix is determined according to one or more of the multipath length that the wireless broadcast communication system usually needs to contend with, the minimum length of the robust correlation peak that the system can obtain at the lowest receiving threshold, and the number of bits of the transmission signaling required by the time domain structure.

3. The method of generating preamble symbols in a physical frame according to claim 1, wherein the length of the cyclic prefix is equal to or less than the predetermined length.

4. The method as claimed in claim 1, wherein the generating of the modulation signal based on the truncated time domain OFDM symbol with the cyclic prefix length comprises:

setting a frequency offset sequence;

and multiplying the time domain OFDM symbol with the cyclic prefix length or a part of the time domain OFDM symbol with the cyclic prefix length by the frequency offset sequence to obtain the modulation signal.

5. The method of claim 4, wherein the frequency offset value of the frequency offset sequence is determined according to a frequency domain subcarrier spacing corresponding to a time domain OFDM symbol or according to a modulation signal length.

6. The method of generating preamble symbols in a physical frame according to claim 1, wherein the generating preamble symbols based on the cyclic prefix, the time domain OFDM symbols and the modulation signal comprises:

and splicing the cyclic prefix at the front part of the time domain OFDM symbol as a guard interval, and splicing the modulation signal at the rear part of the OFDM symbol as a modulation frequency offset part to generate a preamble symbol.

7. The method of generating preamble symbols in a physical frame according to claim 1, wherein before the time domain OFDM symbol with a cyclic prefix length truncated therefrom as a cyclic prefix, further comprising:

and selecting different combinations of the cyclic prefix length and the modulation signal length so that the finally formed preamble symbol transmits the signaling information through the different combinations.

8. The method as claimed in claim 7, wherein the selecting different combinations of the cyclic prefix length and the modulation signal length to make the finally formed preamble symbol transmit signaling information through the different combinations comprises:

determining the bit number N of signaling information to be transmitted;

selection 2^NDifferent combinations of cyclic prefix length and modulation signal length, so that the finally formed preamble symbol passes through the above 2^NDifferent combinations to transmit signaling information.

9. The method of generating preamble symbols in a physical frame according to claim 1, wherein before the time domain OFDM symbol with a cyclic prefix length truncated therefrom as a cyclic prefix, further comprising:

determining a combination of the cyclic prefix length and the modulated signal length;

and selecting different starting positions from the time domain OFDM symbols for intercepting the cyclic prefix length to intercept the time domain OFDM symbols with the modulation signal length to generate a modulation signal, so that the finally formed preamble symbols transmit signaling information through the different starting positions.

10. The method of generating preamble symbols in a physical frame according to claim 7 or 9, wherein the signaling information includes an emergency alert or broadcast system identifier EAS _ flag, transmitter flag information TXID, hook information or other transmission parameters.

11. The method as claimed in claim 7 or 9, wherein the length of the modulation signal is determined according to a minimum length of a robust correlation peak obtained by the system at a lowest receiving threshold.

12. The method of generating frequency domain OFDM symbols of claim 1, wherein the predetermined length is 1024.

13. The method for generating preamble symbols in a physical frame as claimed in claim 1, wherein before the inverse discrete fourier transform is performed on the frequency domain OFDM symbols with predetermined length to obtain the time domain OFDM symbols, the method further comprises the following steps:

determining an average power ratio of the fixed sequence and the signaling sequence;

respectively generating a fixed sequence and a signaling sequence on a frequency domain according to the average power ratio;

filling a fixed sequence and a signaling sequence onto effective subcarriers, wherein the fixed sequence and the signaling sequence are arranged in a parity staggered manner;

and filling zero sequence subcarriers on two sides of the effective subcarriers respectively to form frequency domain OFDM symbols with preset length.

14. The method for generating frequency domain OFDM symbols of claim 13, wherein generating a signaling sequence in the frequency domain comprises:

determining the length, the number and the amplitude of a signaling sequence;

determining root values in a CAZAC sequence generation formula based on the length and the number of the signaling sequences; the length of the signaling sequence is less than or equal to a root value, and the root value is more than or equal to twice of the number of the signaling sequences;

selecting different q values to generate a CAZAC sequence, wherein the number of the q values is equal to the number of the signaling sequences, and the sum of any two q values is not equal to a root value; the generated CAZAC sequence needs to be subjected to cyclic shift, and the bit number of the cyclic shift is determined by a corresponding root value and a q value;

and selecting a required signaling sequence from all CAZAC sequences according to the determined number of the signaling sequences.

15. The method of generating frequency domain OFDM symbols of claim 14, wherein the length of the signaling sequence is 353, the number of the signaling sequences is 128, the root value is 353;

the values of q are all in the following table:

the number of bits of the cyclic shift is all the values in the following table:

16. the method for generating frequency domain OFDM symbols of claim 13, wherein generating a signaling sequence in the frequency domain comprises:

determining the length, the number and the amplitude of a signaling sequence;

determining a plurality of root values in a CAZAC sequence generation formula based on the length and the number of the signaling sequences; the length of the signaling sequence is smaller than or equal to the minimum value of the selected plurality of root values, and the sum of the selected plurality of root values is larger than or equal to twice the number of the signaling sequence;

selecting different q values to generate a CAZAC sequence aiming at each root value, wherein the number of the q values is less than or equal to 1/2 of the corresponding root value, and the sum of any two q values is not equal to the corresponding root value; the generated CAZAC sequence needs to be subjected to cyclic shift, and the bit number of the cyclic shift is determined by a corresponding root value and a q value;

and selecting a required signaling sequence from each obtained CAZAC sequence according to the determined number of the signaling sequences.

17. The method of generating frequency domain OFDM symbols of claim 16, wherein the number of q values is chosen to be different for each root value, and the sum of the number of q values is equal to the number of signaling sequences.

18. The method of generating frequency domain OFDM symbols of claim 16, wherein a root value of the number of root values is selected as a length of the signaling sequence.

19. The method for generating frequency domain OFDM symbols as claimed in claim 18, wherein said selecting the signaling sequence from each of the resulting CAZAC sequences according to the determined length of the signaling sequence comprises: and determining the signaling sequence according to the CAZAC sequence generated by the root value selected as the length of the signaling sequence.

20. The method of generating frequency domain OFDM symbols of claim 14 or 16, wherein the root value is a prime number.

21. The method of generating frequency domain OFDM symbols of claim 15, wherein the generation of the fixed sequence is calculated based on a generated signaling sequence.

22. The method of generating frequency domain OFDM symbols of claim 21, wherein the fixed sequence is:

$\mathrm{FC}\left(n\right)e^{{\mathrm{j\&omega;}}_n}$

wherein, ω is_nThe values of (A) are arranged in rows from left to right in sequence as shown in the following table:

5.43 2.56 0.71 0.06 2.72 0.77 1.49 6.06 4.82 2.10 5.62 4.96 4.93 4.84 4.67 5.86 5.74 3.54 2.50 3.75 0.86 1.44 3.83 4.08 5.83 1.47 0.77 1.29 0.16 1.38 4.38 2.52 3.42 3.46 4.39 0.61 4.02 1.26 2.93 3.84 3.81 6.21 3.80 0.69 5.80 4.28 1.73 3.34 3.08 5.85 1.39 0.25 1.28 5.14 5.54 2.38 6.20 3.05 4.37 5.41 2.23 0.49 5.12 6.26 3.00 2.60 3.89 5.47 4.83 4.17 3.36 2.63 3.94 5.13 3.71 5.89 0.94 1.38 1.88 0.13 0.27 4.90 4.89 5.50 3.02 1.94 2.93 6.12 5.47 6.04 1.14 5.52 2.01 1.08 2.79 0.74 2.30 0.85 0.58 2.25 5.25 0.23 6.01 2.66 2.48 2.79 4.06 1.09 2.48 2.39 5.39 0.61 6.25 2.62 5.36 3.10 1.56 0.91 0.08 2.52 5.53 3.62 2.90 5.64 3.18 2.36 2.08 6.00 2.69 1.35 5.39 3.54 2.01 4.88 3.08 0.76 2.13 3.26 2.28 1.32 5.00 3.74 1.82 5.78 2.28 2.44 4.57 1.48 2.48 1.52 2.70 5.61 3.06 1.07 4.54 4.10 0.09 2.11 0.10 3.18 3.42 2.10 3.50 4.65 2.18 1.77 4.72 5.71 1.48 2.50 4.89 4.04 6.12 4.28 1.08 2.90 0.24 4.02 1.29 3.61 4.36 6.00 2.45 5.49 1.02 0.85 5.58 2.43 0.83 0.65 1.95 0.79 5.45 1.94 0.31 0.12 3.25 3.75 2.35 0.73 0.20 6.05 2.98 4.70 0.69 5.97 0.92 2.65 4.17 5.71 1.54 2.84 0.98 1.47 6.18 4.52 4.44 0.44 1.62 6.09 5.86 2.74 3.27 3.28 0.55 5.46 0.24 5.12 3.09 4.66 4.78 0.39 1.63 1.20 5.26 0.92 5.98 0.78 1.79 0.75 4.45 1.41 2.56 2.55 1.79 2.54 5.88 1.52 5.04 1.53 5.53 5.93 5.36 5.17 0.99 2.07 3.57 3.67 2.61 1.72 2.83 0.86 3.16 0.55 5.99 2.06 1.90 0.60 0.05 4.01

6.15 0.10 0.26 2.89 3.12 3.14 0.11 0.11 3.97 5.15 4.38 2.08 1.27 1.17 0.42 3.47 3.86 2.17 5.07 5.33 2.63 3.20 3.39 3.21 4.58 4.66 2.69 4.67 2.35 2.44 0.46 4.26 3.63 2.62 3.35 0.84 3.89 4.17 1.77 1.47 2.03 0.88 1.93 0.80 3.94 4.70 6.12 4.27 0.31 4.85 0.27 0.51 2.70 1.69 2.18 1.95 0.02 1.91 3.13 2.27 5.39 5.45 5.45 1.39 2.85 1.41 0.36 4.34 2.44 1.60 5.70 2.60 3.41 1.84 5.79 0.69 2.59 1.14 5.28 3.72 5.55 4.92 2.64

23. the method of generating frequency domain OFDM symbols of claim 13, wherein the length of the fixed sequence is equal to the length of the signaling sequence and is less than 1/2 of the predetermined length.

24. The method of generating frequency domain OFDM symbols as claimed in claim 13, wherein the padding of zero sequence subcarriers on both sides of the effective subcarrier, respectively, to form frequency domain OFDM symbols of a predetermined length comprises: and filling zero sequence subcarriers with equal length on two sides of the effective subcarriers respectively to form frequency domain OFDM symbols with preset length.

25. The method of generating frequency domain OFDM symbols of claim 13, wherein the length of the zero sequence subcarriers padded on each side is greater than a critical length value, the critical length value being determined by the system sampling rate, the symbol rate and a predetermined length.

26. The method of generating frequency domain OFDM symbols of claim 13, wherein the fixed sequence and the signaling sequence are both constant modulus sequences.

27. The method of generating frequency domain OFDM symbols of claim 13, wherein the fixed sequence and the signaling sequence have the same or different average powers.

28. The method of generating frequency domain OFDM symbols of claim 13, wherein the average power ratio of the fixed sequence and the signaling sequence is determined based on balanced consideration of an offset estimation performance, a channel estimation performance, a de-signaling performance and a timing synchronization performance.

29. The method of generating frequency domain OFDM symbols of claim 13, wherein the fixed sequence and the signaling sequence have an average power ratio of 1: 1 or 3: 2 or 2:1 or 3: 1.