CN105186089B - A kind of big frequency ratio microwave dual-frequency power divider of miniaturization - Google Patents
A kind of big frequency ratio microwave dual-frequency power divider of miniaturization Download PDFInfo
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- 230000007547 defect Effects 0.000 description 1
- 238000009795 derivation Methods 0.000 description 1
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Abstract
The invention discloses a kind of big frequency ratio microwave dual-frequency power dividers of miniaturization, belong to multifrequency power splitter field.Including an isolation resistance and two double frequency impedance transformers, wherein, double frequency impedance transformer is made of symmetric form three-section type stepped impedance transmission line, realizes dual-frequency power divider by the way that two double frequency impedance transformers to be connected to parallel form and loaded isolation resistance.Present invention design circuit is simple, and working frequency is controllable, the ratio of two frequencies is larger, and overall dimensions are smaller, and microstrip line can be used, and the planar transmission lines form such as strip line realizes that cost is relatively low.
Description
Technical Field
The invention relates to a miniaturized large-frequency-ratio microwave dual-frequency power divider, and belongs to the field of multi-frequency power dividers.
Background
At present, the microwave dual-frequency power divider generally has the following implementation schemes:
1. dual-frequency power splitters are designed based on transmission lines loaded with reactive or resistive elements. The design scheme of loading reactance makes the circuit structure complicated and brings parasitic effect. For the solution of loading the resistive element, the circuit is relatively simple, but the achievable operating frequency is relatively small.
2. The dual-frequency power divider is designed based on a coupling structure. This design focuses on replacing the conventional quarter-wave transmission line with a coupling structure or implementing a dual-band power divider using a coupling structure at the output port. Although the power divider based on the scheme has a compact circuit structure, the related theoretical derivation is complex, and the power divider is inconvenient for mass application.
3. The power divider is designed based on a dual-frequency impedance transformation network. Because the dual-frequency impedance conversion network has different implementation structures such as T-shaped or pi-shaped or T-shaped or E-shaped structures and improved structures thereof, a designer can select a proper implementation structure according to design targets such as miniaturization, working frequency ratio range, power division bandwidth and the like, and therefore the scheme has better flexibility.
Disclosure of Invention
The purpose of the invention is as follows: in order to overcome the defects in the prior art, the invention provides a miniaturized microwave dual-frequency power divider to solve the problems of small working frequency ratio, large size of the realization structure, narrow bandwidth and the like of the dual-frequency power divider.
The technical scheme is as follows: in order to achieve the purpose, the invention adopts the technical scheme that:
a miniaturized microwave dual-frequency power divider with large frequency ratio comprises an isolation resistor and two dual-frequency impedance converters, wherein each dual-frequency impedance converter is composed of symmetrical three-section stepped impedance transmission lines, and the two dual-frequency impedance converters are connected in parallel and loaded with the isolation resistor, so that the dual-frequency power divider is realized.
Preferably: two frequency points of the double-frequency impedance converter can be equivalent to a K converter.
Preferably: the structural parameters of the K converter structure in the dual-frequency impedance converter are as follows:
wherein, theta1Is the electrical length of the impedance transmission line, r is the transmission line characteristic impedance ratio, ZTIs the impedance value of the K converter, Z1Is the characteristic impedance of the impedance transmission line.
Preferably: transmission line at frequency f1Electrical length of (theta)f1The values of (A) are as follows:
wherein, thetaf2/θf1＝f2/f1＝m，θf1,θf2Respectively, the transmission line being at frequency f1,f2The electrical length of (d).
Preferably: the structural parameter values of the K converter structure in the double-frequency impedance converter are as follows:
where n is an integer, m is a frequency ratio, and θf1For transmission lines at frequency f1The electrical length of (d).
Preferably: the structural size and the frequency ratio of the dual-frequency impedance converter are as follows:
wherein,is the normalized electrical length, theta, of the transmission line1,θ2Being the electrical length of the impedance transmission line, thetaf2/θf1＝f2/f1＝m，θf1,θf2Respectively, the transmission line being at frequency f1,f2The electrical length of (d).
Preferably: the frequency ratio between the dual-frequency impedance converters is 5.2, the characteristic impedance of one transmission line is 90.4 omega, and the corresponding electrical length is 29.0deg @1.0 GHz; the characteristic impedance of the other transmission line is 55.3 omega, and the corresponding electrical length is 29.0deg @1.0 GHz; the characteristic impedance of the outlet end is 50 omega.
Preferably: the frequency ratio between the dual-frequency impedance converters is 6.0, the characteristic impedance of one transmission line is 112 omega, and the corresponding electrical length is 25.7deg @1.0 GHz; the characteristic impedance of the other transmission line is 41 omega, and the corresponding electrical length is 25.7deg @1.0 GHz; the characteristic impedance of the outlet end is 50 omega.
Compared with the prior art, the miniaturized microwave dual-frequency power divider with the large frequency ratio has the following beneficial effects:
(1) because the dual-frequency impedance converter is composed of a symmetrical three-section stepped impedance transmission line, the dual-frequency power divider is realized by connecting the two dual-frequency impedance converters in a parallel mode and loading the isolation resistor, the dual-frequency power divider can be realized, and the working frequency of the dual-frequency impedance converter is higher than that of f2/f1 and reaches more than 5; therefore, the problems of small working frequency ratio, large size of the realization structure, narrow bandwidth and the like of the double-frequency power divider are solved, and the double-frequency power divider can be realized by using planar transmission line forms such as microstrip lines, strip lines and the like, and has low cost.
(2) The overall size of the power divider is small, which is beneficial to the integrated design of the circuit;
(3) the matching at two frequency points is good, and the isolation between output ports is high.
Drawings
Fig. 1 is a structural diagram of a K converter of the wilkinson power divider;
fig. 2 is a block diagram of a stepped dual-frequency K converter;
fig. 3 is a diagram of an implementation structure of a dual-band power divider;
FIG. 4 is a graph of normalized total electrical length for a dual frequency K-converter;
FIG. 5 is a graph of the impedance of a stepped structure that can be achieved;
fig. 6 plots the insertion loss (S21, S31) and return loss (S11) of port 1 for a dual-frequency power divider (frequency ratio of 5.2);
fig. 7 is a graph of return loss (S22) of port 2 of the dual-frequency power divider (frequency ratio of 5.2);
fig. 8 is a graph of the isolation (S32) of a dual-band power divider (frequency ratio of 5.2);
fig. 9 is a graph of the insertion loss (S21, S31) and return loss (S11) of port 1 for a dual-frequency power divider (frequency ratio of 6.0);
fig. 10 is a graph of return loss (S22) for port 2 of the dual frequency power divider (frequency ratio of 6.0);
fig. 11 is a graph of the isolation (S32) of the dual-band power divider (frequency ratio of 6.0).
Detailed Description
The present invention will be further described with reference to the accompanying drawings.
A K converter structure of a wilkinson power divider, as shown in fig. 1. The impedance matching between the input impedance at the input port and the input transmission line is realized through the impedance conversion function of the K converter, so that the reflection loss of power is reduced.
The ABCD matrix is:
wherein Z isTIs the impedance value of the K-transformer, j is the imaginary unit, and a is the transmission matrix of the K-transformer.
Fig. 2 is a block diagram of a dual-frequency K converter. The dual-frequency impedance converter is composed of a symmetrical three-section type stepped impedance transmission line, and can be equivalent to a K converter at two frequency points, namely, the dual-frequency impedance converter can be analyzed through the equivalent relation between the structure of the figure 2 and the original K converter.
The ABCD matrix of the structure of fig. 2 is:
wherein Z is1,θ1Is the characteristic impedance and electrical length, Z, of the two-ended impedance transmission line2,θ2Is the characteristic impedance and electrical length of the intermediate impedance transmission line, j is an imaginary unit, A1A transmission matrix of the structure of fig. 2.
The simplified result is:
wherein A is1,B1,C1,D1Is a matrix element of the transmission matrix.
From the equality of the two matrix parameters, the following equation can be obtained:
to simplify the analysisθ1＝θ2Then there are:
due to the equation (4) at two frequency points f1,f2＝mf1Both are true, then:
wherein, thetaf1,θf2Respectively, the transmission line being at frequency f1,f2Where r is the transmission line characteristic impedance ratio, and thetaf2/θf1＝f2/f1＝m
Theta can be obtained by analyzing the formula (6)f1The value taking condition of (1):
where n is an integer, m is a frequency ratio, and θf1For transmission lines at frequency f1The electrical length of (d).
Considering the problem of design size miniaturization, the values of the parameters in the equation (7) are as follows:
due to the relationship between the structural size and the frequency ratio of the stepped dual-frequency K converter, the measurement can be carried out through the relationship between the total normalized electrical length and the frequency ratio of the K converter structure of a certain branch of the power divider.
The variation curve is shown in fig. 4, from which the advantage of small size of the power divider can be observed.
And the impedance value Z realized by the K converter structure in the power divider1,Z2The frequency-ratio relation can be obtained from the equation (6), and the variation curve thereof is shown in fig. 5.
For two dual-frequency power dividers with working frequencies of 1GHz and 5.2GHz (frequency ratio of 5.2), respectively, the structure is shown in FIG. 3, (P)1，P2，P3，P4) For the port, the structural parameters of the K converter can be obtained by solving the formula (6), then the overall structure is optimized by using ADS software, and the obtained characteristic impedance and electrical length parameters of each transmission line are shown in the following table:
| z0(Ω) | 50 | zr(Ω) | 100 |
| z1(Ω) | 90.4 | θ1(deg@1.0GHz) | 29.0 |
| z2(Ω) | 55.3 | θ2(deg@1.0GHx) | 29.0 |
wherein z is0,zrRespectively, port characteristic impedance and isolation resistance.
As shown in fig. 6-8, the simulated reflection characteristic curves S11 and S22, the transmission characteristic curves S21 and S31, and the isolation curve S32 are characterized. The corresponding S parameters of the two frequency points are as follows:
f1＝1.0GHz,|S11|＝-46.0dB,|S21|＝-3.0dB,|S22|＝-85.8dB,|S32|＝-52.0dB
f2＝5.2GHz,|S11|＝-46.0dB,|S21|＝-3.0dB,|S22|＝-64.5dB,|S32|＝-48.1dB
the bandwidths at 20dB of isolation are:
817.8MHz-1.162GHz,5.051GHz-5.384GHz
for two structures with working frequencies of 1GHz and 6.0GHz (frequency ratio of 6.0) respectively, as shown in fig. 3, the structural parameters of the K converter can be obtained by solving the formula (6), then the overall structure is optimized by ADS software, and the obtained characteristic impedance and electrical length parameters of each transmission line are shown in the following table:
| z0(Ω) | 50 | zr(Ω) | 100 |
| z1(Ω) | 122 | θ1(deg@1.0GHz) | 25.7 |
| z2(Ω) | 41 | θ2(deg@1.0GHz) | 25.7 |
wherein z is0,zrRespectively, port characteristic impedance and isolation resistance.
As shown in fig. 9-11, the simulated reflection characteristic curves S11 and S22, the transmission characteristic curves S21 and S31, and the isolation curve S32 are characterized. The corresponding S parameters of the two frequency points are as follows:
f1＝1.0GHz,|S11|＝-68.4dB,|S21|＝-3.0dB,|S22|＝-75.5dB,|S32|＝-72.3dB
f2＝6.0GHz,|S11|＝48.3dB,|S21|＝-3.0dB,|S22|＝-58.3dB,|S32|＝-50.0dB
the bandwidths at 20dB of isolation are:
850.1MHz-1.162GHz,5.837GHz-6.160GHz
the dual-frequency 3dB power divider can be realized in the form of planar transmission lines such as microstrip lines, strip lines and the like, and has lower cost. The invention adopts the symmetrical three-section stepped impedance transmission line to form the double-frequency impedance converter, and the actual data shows that the whole electrical length of the double-frequency impedance converter is less than 90 degrees at the first working frequency, and the size is relatively small. Because no resonance units such as any branch line and the like are loaded, the actual working bandwidth of the dual-frequency power divider is relatively wide.
The foregoing is only a preferred embodiment of this invention and it should be noted that modifications can be made by those skilled in the art without departing from the principle of the invention and these modifications should also be considered as the protection scope of the invention.
Claims (6)
1. A miniaturized microwave double-frequency power divider with large frequency ratio is characterized in that: the double-frequency impedance converter comprises an isolation resistor and two double-frequency impedance converters, wherein the double-frequency impedance converter is formed by a symmetrical three-section stepped impedance transmission line, and the double-frequency power divider is realized by connecting the two double-frequency impedance converters in a parallel mode and loading the isolation resistor; two frequency points of the double-frequency impedance converter are equivalent to a K converter;
the structural parameters of the K converter in the dual-frequency impedance converter are as follows:
where m is the operating frequency ratio, θ1Is the electrical length of the impedance transmission line, r is the transmission line characteristic impedance ratio, ZTIs the impedance value of the K converter, Z1Is the characteristic impedance of the impedance transmission line.
2. The miniaturized large-frequency-ratio microwave dual-frequency power divider according to claim 1, characterized in that: transmission line at frequency f1Electrical length of (theta)f1The values of (A) are as follows:
wherein, thetaf2/θf1＝f2/f1＝m，θf1,θf2Respectively, the transmission line being at frequency f1,f2The electrical length of (d).
3. The miniaturized large-frequency-ratio microwave dual-frequency power divider according to claim 2, characterized in that: the structural parameter values of the K converter structure in the double-frequency impedance converter are as follows:
wherein, thetaf1For transmission lines at frequency f1The electrical length of (d).
4. The miniaturized large-frequency-ratio microwave dual-frequency power divider according to claim 1, characterized in that: the structural size and the frequency ratio of the dual-frequency impedance converter are as follows:
wherein,is the normalized electrical length, theta, of the transmission line1,θ2Being the electrical length of the impedance transmission line, thetaf2/θf1＝f2/f1＝m，θf1,θf2Respectively, the transmission line being at frequency f1,f2The electrical length of (d).
5. The miniaturized large-frequency-ratio microwave dual-frequency power divider according to claim 1, characterized in that: the frequency ratio between the dual-frequency impedance converters is 5.2, the characteristic impedance of one transmission line is 90.4 omega, and the corresponding electrical length is 29.0deg @1.0 GHz; the characteristic impedance of the other transmission line is 55.3 omega, and the corresponding electrical length is 29.0deg @1.0 GHz; the characteristic impedance of the outlet end is 50 omega.
6. The miniaturized large-frequency-ratio microwave dual-frequency power divider according to claim 1, characterized in that: the frequency ratio between the dual-frequency impedance converters is 6.0, the characteristic impedance of one transmission line is 112 omega, and the corresponding electrical length is 25.7deg @1.0 GHz; the characteristic impedance of the other transmission line is 41 omega, and the corresponding electrical length is 25.7deg @1.0 GHz; the characteristic impedance of the outlet end is 50 omega.
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| CN107611552B (en) * | 2017-09-15 | 2019-10-01 | 重庆邮电大学 | Micro-strip miniaturization based on stepped impedance artificial transmission line etc. divides power splitter |
| CN111294008B (en) * | 2020-02-26 | 2021-10-01 | 吉林大学 | Double-frequency point impedance converter of parallel transmission line with complex number terminal and its establishing method and application |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN202712402U (en) * | 2012-08-29 | 2013-01-30 | 成都创吉科技有限责任公司 | Double-band Wilkinson power divider |
| CN104078736A (en) * | 2013-03-26 | 2014-10-01 | 中国科学院微电子研究所 | Miniaturized broadband power divider circuit |
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| JP2000216606A (en) * | 1998-12-09 | 2000-08-04 | Ricoh Co Ltd | Power distribution and combining device |
| JP2003283219A (en) * | 2002-03-25 | 2003-10-03 | Mitsubishi Electric Corp | High-frequency power distributor-combiner and antenna apparatus using the same |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN202712402U (en) * | 2012-08-29 | 2013-01-30 | 成都创吉科技有限责任公司 | Double-band Wilkinson power divider |
| CN104078736A (en) * | 2013-03-26 | 2014-10-01 | 中国科学院微电子研究所 | Miniaturized broadband power divider circuit |
Non-Patent Citations (1)
| Title |
|---|
| A Tri-band Wilkinson Power Divider using Step- Impedance Resonator;Xin-Huai Wang等;《Electrical Design of Advanced Packaging and Systems Symposium(EDAPS),2011 IEEE》;20111214;全文 * |
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