CN104617849A - Method for controlling maximum output power of hybrid excitation synchronizing motor - Google Patents

Abstract

The invention discloses a method for controlling maximum output power of a hybrid excitation synchronizing motor. The method is that a d axis, a q axis and excitation current are coordinately controlled to fully utilize the input power so as to maximize the output power; a motor running area is determined according to the rotating speed; when the motor runs at a low speed area, the control is performed by an id=0 manner; if the load torque is not greater than the rated torque, magnet increase type control is saved; if the load torque is more than the rated torque, the magnet increase type control can be carried out; when the motor runs at a high speed area, the id is kept to be 0, the magnet is decreased under the control of the maximum input/ output power, and the q axis current and the excitation current if are coordinated to keep the maximum output power; when the excitation current if reaches the rated value, the d axis current and the q axis current are coordinated to keep maximum output power. According to the method, the power utilization of the weak magnetic running area is increased, the speed regulating range is expanded, and therefore, the hybrid excitation synchronizing motor can run at high efficiency within a wide and constant power operation range.

Description

A kind of hybrid exciting synchronous motor peak power output control method

Technical field

The invention belongs to electric drive technology field, relate to a kind of peak power output strategy, particularly relate to a kind of hybrid exciting synchronous motor control method.

Background technology

Hybrid exciting synchronous motor is a kind of wide range speed control motor grown up on the basis of permanent-magnet synchronous and electric excitation synchronous motor, and its main purpose is the problem being difficult to regulate to solve permagnetic synchronous motor air-gap field.Hybrid exciting synchronous motor has two kinds of excitation sources, and one is permanent magnet, and another kind is electric excitation, and the magnetic potential that permanent magnet produces is main magnetic potential, and the magnetic potential that excitation winding produces is auxiliary magnetic potential.This motor combines the advantage of permanent-magnet synchronous and electric excitation synchronous motor, and two kinds of excitation sources interact and produce main flux in motor gas-gap, when electric magnet exciting coil passes into the exciting current of forward, produces forward electromagnetic torque and increases motor torque; Otherwise, when electric magnet exciting coil passes into reverse exciting current, then produce opposing magnetic field and weaken the object that air-gap field reaches weak magnetic speed-up, thus widened the speed adjustable range of motor.

At present, both at home and abroad for hybrid exciting synchronous motor control method and Research on Driving System less, related data neither be a lot.Substantially can be classified as two classes, a class is i _d=0 controls, and another kind of is weak magnetics detect.The advantage of above-mentioned two class control methods is simple and convenient; Shortcoming is that motor is interval in whole service, and efficiency is lower, and range of operation is narrow.

Summary of the invention

Technical problem: the deficiency that the present invention is directed to prior art, on the basis analyzing existing hybrid exciting synchronous motor control method, propose and a kind ofly widened mixed excitation electric machine output-constant operation scope and the efficiency in weak magnetic field operation interval, amount of calculation is less, controls hybrid exciting synchronous motor peak power output control method simply and easily.

Technical scheme: hybrid exciting synchronous motor peak power output control method of the present invention, comprises the following steps:

(1) phase current i is gathered from motor main circuit _a, i _bwith exciting current i _f, initial position detection is carried out to motor, collection signal from motor encoder, sends into controller and process, draw rotating speed n and rotor position angle θ;

(2) the phase current i will gathered _a, i _bthrough following, filtering, biased and A/D conversion, then carry out park transforms, obtain the stator d shaft current i under two-phase rotating coordinate system _dwith q shaft current i _q;

(3) given rotating speed n is used ^*deduct encoder actual measurement rotating speed n, the rotating speed deviation delta n input speed adjuster obtained is obtained torque reference value after proportional integral computing by torque reference value busbar voltage U _dc, stator d shaft voltage u _d, stator q shaft voltage u _q, actual measurement rotating speed n and given rotating speed n ^*input current distributor, judges motor traffic coverage according to rotating speed: when actual speed is greater than rated speed, then hybrid exciting synchronous motor runs on low regime, enter step 4), otherwise hybrid exciting synchronous motor runs on high velocity, enter step 5);

(4) judge whether load torque meets T _l≤ T _n, wherein T _lfor load torque, T _nfor nominal torque;

Work as T _l≤ T _ntime, without the need to increasing magnetic control, i _fref=0, adopt i _d=0 controls, and distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{dref}}=0\\ i_{\mathrm{qref}}=\frac{{2T}_{\mathrm{eref}}}{{3\mathrm{p\ψ}}_m}\\ i_{\mathrm{fref}}=0\end{array}\right.$

Work as T _l> T _ntime, q shaft current reaches rated value, need carry out increasing magnetic control, therefore i _q=i _qN, adopt i _d=0 controls, and distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{dref}}=0\\ i_{\mathrm{fref}}=\frac{{2T}_{\mathrm{eref}}-{3\mathrm{p\ψ}}_m{i}_{\mathrm{qN}}}{3p{M}_f{i}_{\mathrm{qN}}}\\ i_{\mathrm{qref}}=i_{\mathrm{qN}}\end{array}\right.$

Wherein, i _dreffor d shaft current reference value, i _qreffor q shaft current reference value, i _freffor excitation winding current reference value; ψ _mfor permanent magnet flux linkage, p is motor number of pole-pairs; i _qNfor q shaft current rated value, L _d, L _qbe respectively stator winding d axle and q axle inductance, M _ffor the mutual inductance between armature winding and excitation winding, T _ereffor electromagnetic torque reference value;

(5) the 1st stages continue to keep i _dref=0, adopt the weak magnetic of peak power output control method, distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{qref}}=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{\left(M_f{\mathrm{\Δi}}_f\right)}^2}\\ i_{\mathrm{dref}}=0\\ i_{\mathrm{fref}}=-\frac{{\mathrm{\ψ}}_m}{M_f}-{\mathrm{\Δi}}_f\end{array}\right.$

Wherein, ${\mathrm{\Δi}}_f=\frac{1+\sqrt{1+4{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2}}{{2M}_f};$

After exciting current reaches rated value, the 2nd stage continues peak power output method and carries out weak magnetic, and distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{qref}}=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{\left(L_d{\mathrm{\Δi}}_d\right)}^2}\\ i_{\mathrm{fref}}=i_{\mathrm{fN}}\\ i_{\mathrm{dref}}=-\frac{{\mathrm{\ψ}}_{\mathrm{exc}}}{L_d}+{\mathrm{\Δi}}_d\end{array}\right.$

Wherein, ${\mathrm{\Δi}}_d=\frac{{\mathrm{\ρ\ψ}}_{\mathrm{exc}}-\sqrt{{\mathrm{\ρ}}^2{\mathrm{\ψ}}_{\mathrm{exc}}^2+8{(\mathrm{\ρ}-1)}^2{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2}}{4(\mathrm{\ρ}-1)L_d},$ ρ=L _q/ L _d, ψ _exc=ψ _m+ M _fi _fN, i _fNfor exciting current rated value, ρ is convex grey subset, ω _efor angular rate.

(6) with the d shaft current reference value i that distributing switch produces _drefdeduct the d shaft current i in step (2) _dobtain d shaft current deviation delta i _d, with q shaft current i _qrefdeduct the q shaft current i in step (2) _qobtain q shaft current deviation delta i _q; By d shaft current deviation delta i _dinput d shaft current adjuster carries out proportional integral computing, obtains d shaft voltage u _d, by q shaft current deviation delta i _qinput q shaft current adjuster carries out proportional integral computing, obtains q shaft voltage u _q, then to described d shaft voltage u _dwith q shaft voltage u _qafter jointly carrying out rotating orthogonal-static two phase inversion, obtain α shaft voltage u under static two phase coordinate systems _αwith β shaft voltage u _β, by described α shaft voltage u _αwith β shaft voltage u _βinput pulse width modulation module, computing exports 6 road pulse width modulating signals, drives main power inverter;

The exciting current i simultaneously will gathered in step (1) _f, with exciting current reference value i after signal condition and A/D are changed _frefsend into DC excitation pulse width modulation module together, computing exports 4 road pulse width modulating signals to drive exciting power converter;

In a kind of preferred version of the inventive method, step 6) in Pulse width modulation module be space vector pulse width modulation module.

Beneficial effect: the i of existing hybrid exciting synchronous motor _d=0 and the minimum control method of copper loss there is shortcomings, i _dalthough=0 controls simple and convenient, its control efficiency is lower; Although the minimum control of copper loss can reduce the copper loss of motor.But control method is comparatively complicated, the present invention is by step 4) and step 5) peak power output control method, make hybrid exciting synchronous motor no matter operate in high velocity, there is greater efficiency, so the relatively existing control method of the present invention has the following advantages:

(1) the method is by having widened mixed excitation electric machine output-constant operation scope;

(2) relative to the minimum control method of copper loss, this control method amount of calculation is less, controls simple and convenient;

(3) relative to i _d=0 controls, and the method increases the efficiency of mixed excitation electric machine in weak magnetic field operation interval;

Accompanying drawing explanation

Fig. 1 is the logical procedure diagram of the inventive method;

Fig. 2 is the system block diagram of the inventive method;

Fig. 3 is the structured flowchart realizing the inventive method;

Fig. 4 is electric current allocation result block diagram.

Embodiment

Below in conjunction with embodiment and Figure of description, the present invention is further illustrated.

Fig. 3 is the system block diagram realizing hybrid exciting synchronous motor peak power output control method of the present invention, and this control system is made up of AC power, rectifier, electric capacity of voltage regulation, dsp controller, main power inverter, auxiliary power inverter, transducer, hybrid exciting synchronous motor, photoelectric encoder etc.

AC power is powered to whole system, and after rectifier rectification, filtering, voltage stabilizing, give main and auxiliary power inverter, and Hall voltage transducer gathers busbar voltage, sends into controller after conditioning.The output termination hybrid exciting synchronous motor of main and auxiliary power inverter, Hall current instrument transformer gathers phase current and exciting current, send into controller after conditioning, code device signal gathers rotating speed and rotor-position signal, sends into controller and calculate rotor position angle and rotating speed after process.Controller exports 10 road pwm signals and drives main, exciting power converter respectively.

Hybrid exciting synchronous motor peak power output control method of the present invention, shown in Fig. 3, specifically comprises the following steps:

(1) three Hall current sensor gathers phase current i from motor main circuit respectively _a, i _bwith exciting current i _fthe signal collected is sent into controller after the signal conditions such as voltage follow, filtering, biased and overvoltage protection, carry out accurate initial position detection to motor, collection signal from motor encoder, process is sent into controller and is calculated rotating speed n and rotor position angle θ;

(2) the phase current i of controller will be sent into _a, i _bcarry out A/D conversion, to obtain the d shaft current i under two-phase rotating coordinate system through three phase coordinate systems to the park transforms of two-phase rotating coordinate system _dwith q shaft current i _q;

(3) given rotating speed n is used ^*deduct encoder actual measurement rotating speed n, obtain torque reference value T by after the rotating speed deviation delta n input speed adjuster obtained _e ^*, by torque reference value T _e ^*, busbar voltage U _dc, stator d shaft voltage u _d, stator q shaft voltage u _q, actual measurement rotating speed n and given rotating speed n ^*send into distributing switch, judge whether actual speed is less than rated speed, in this way, motor runs on low regime, enters step 4), otherwise, enter step 5), as shown in Figure 1.

(4) under, surface analysis low regime hybrid exciting synchronous motor peak power output control strategy, specific as follows;

According to principle of vector control, in d-q coordinate system, draw the Mathematical Modeling of hybrid exciting synchronous motor.

Flux linkage equations:

$\left[\begin{array}{c}{\mathrm{\ψ}}_d\\ {\mathrm{\ψ}}_q\\ {\mathrm{\ψ}}_f\end{array}\right]=\left[\begin{array}{ccc}{L}_d& 0& M_f\\ 0& L_q& 0\\ 3/2M_f& 0& L_f\end{array}\right]\left[\begin{array}{c}{i}_d\\ i_q\\ i_f\end{array}\right]+\left[\begin{array}{c}{\mathrm{\ψ}}_m\\ 0\\ 0\end{array}\right]---\left(1\right)$

Voltage equation:

$\left\{\begin{array}{c}{u}_d=R_s{i}_d+\frac{{\mathrm{d\ψ}}_d}{\mathrm{dt}}-{\mathrm{\ω}}_e{\mathrm{\ψ}}_q\\ u_q=R_s{i}_q+\frac{{\mathrm{d\ψ}}_q}{\mathrm{dt}}+{\mathrm{\ω}}_e{\mathrm{\ψ}}_d\\ u_f=R_f{i}_f+\frac{{\mathrm{d\ψ}}_f}{\mathrm{dt}}\end{array}\right.---\left(2\right)$

Torque equation:

$T_e=\frac{3}{2}{\mathrm{pi}}_q[{\mathrm{\ψ}}_m+(L_d-L_q)i_d+M_f{i}_f]---\left(3\right)$

Power equation:

$P_e=\frac{3}{2}{\mathrm{p\ω}}_q{i}_q[{\mathrm{\ψ}}_{\mathrm{pm}}+(L_d-L_q)i_d+M_f{i}_f]---\left(4\right)$

Maximum conditions:

$\left\{\begin{array}{c}{({\mathrm{\ψ}}_m+L_d{i}_d+M_f{i}_f)}^2+{\left(L_q{i}_q\right)}^2\≤{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2\\ i_d^2+i_q^2\≤I_s^2\end{array}\right.---\left(5\right)$

Wherein, i _d, i _qbe respectively d axle and q shaft current, I _sfor rated current, i _ffor excitation winding electric current; L _d, L _qbe respectively d axle and q axle inductance, M _ffor the mutual inductance between armature and excitation winding; ω _efor angular rate; ψ _mfor permanent magnet flux linkage, p is motor number of pole-pairs, u _d, u _qbe respectively the voltage of d axle and q axle, u _ffor excitation winding voltage; R _sfor armature winding resistance, R _ffor excitation winding resistance; ψ _d, ψ _q, ψ _fd axle, q axle and excitation winding magnetic linkage respectively; T _efor electromagnetic torque, ω _efor angular rate, u _sfor rated voltage.

Work as T _l≤ T _ntime, without the need to increasing magnetic control, so i _f=0, adopt i _d=0 controls, and convolution (3) can obtain following electric current and distribute:

$\left\{\begin{array}{c}{i}_d=0\\ i_q=\frac{{2T}_e}{{3\mathrm{p\ψ}}_m}\\ i_f=0\end{array}\right.---\left(6\right)$

Work as T _l> T _ntime, q shaft current reaches rated value, need carry out increasing magnetic control, therefore i _q=i _qN, adopt i _d=0 controls, and convolution (3) can obtain following electric current and distribute:

$\left\{\begin{array}{c}{i}_d=0\\ i_f=\frac{{2T}_e-{3\mathrm{p\ψ}}_m{i}_{\mathrm{qN}}}{3p{M}_f{i}_{\mathrm{qN}}}\\ i_q=i_{\mathrm{qN}}\end{array}\right.---\left(7\right)$

Wherein, i _qNfor the rated value of q shaft current;

(5) after mixed excitation electric machine enters high velocity, can be obtained by formula (5):

$i_q=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{({\mathrm{\ψ}}_m+L_d{i}_d+M_f{i}_f)}^2}---\left(8\right)$

First i is kept _d=0, adopt exciting current i _fweak magnetic, bring formula (7) into formula (4) and to exciting current differentiate, then have:

$\begin{array}{c}\frac{{\∂P}_e}{{\∂i}_f}=\frac{3}{2}{\mathrm{p\ω}}_e\frac{1}{L_q}\left[\frac{{-M}_f}{\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{({\mathrm{\ψ}}_m+M_f{i}_f)}^2}}\right]({\mathrm{\ψ}}_m+M_f{i}_f)\\ +\frac{3}{2}{\mathrm{p\ω}}_e{M}_f\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{({\mathrm{\ψ}}_m+M_f{i}_f)}^2}\end{array}---\left(9\right)$

Order $\frac{{\∂P}_e}{{\∂i}_f}=0,$ Can obtain

$M_f^2{i}_f^2+M_f({2\mathrm{\ψ}}_m+1)i_f+{\mathrm{\ψ}}_m^2+{\mathrm{\ψ}}_m-{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2=0---\left(10\right)$

Solve and can obtain i _f

$i_f=-\frac{{\mathrm{\ψ}}_m}{M_f}-{\mathrm{\Δi}}_f---\left(11\right)$

Wherein, bring formula (11) into formula (8), following electric current can be obtained and distribute:

$\left\{\begin{array}{c}{i}_q=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{\left(M_f{\mathrm{\Δi}}_f\right)}^2}\\ i_d=0\\ i_f=-\frac{{\mathrm{\ψ}}_m}{M_f}-{\mathrm{\Δi}}_f\end{array}\right.---\left(12\right)$

When exciting current reaches rated value (i _f=i _fN) time, continue to utilize i _dcontinue weak magnetic, so (8) can be reduced to:

$i_q=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{({\mathrm{\ψ}}_{\mathrm{exc}}+L_d{i}_d)}^2}---\left(13\right)$

Wherein, ψ _exc=ψ _pm+ M _fi _fN, i _fNrated exciting current;

Bring formula (13) into formula (4) and to the differentiate of d shaft current, then have:

$\begin{array}{c}\frac{{\∂P}_e}{{\∂i}_d}=\frac{3}{2}{\mathrm{p\ω}}_e\frac{1}{L_q}\left\{\frac{-L_d({\mathrm{\ψ}}_{\mathrm{exc}}+L_d{i}_d)}{\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{({\mathrm{\ψ}}_{\mathrm{exc}}+M_d{i}_d)}^2}}\right\}[{\mathrm{\ψ}}_{\mathrm{exc}}+(L_d-L_q)i_d]\\ +\frac{3}{2}{\mathrm{p\ω}}_e(L_d-L_q)\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{({\mathrm{\ψ}}_{\mathrm{exc}}+L_d{i}_d)}^2}\end{array}---\left(14\right)$

Order $\frac{{\∂P}_e}{{\∂i}_f}=0,$ Can obtain

$2(\mathrm{\ρ}-1)L_d^2{i}_d^2+{\mathrm{\ψ}}_{\mathrm{exc}}{L}_d(3\mathrm{\ρ}-4)i_d+(\mathrm{\ρ}-2){\mathrm{\ψ}}_{\mathrm{exc}}^2-(\mathrm{\ρ}-1){\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2=0---\left(15\right)$

Wherein, ρ=L _q/ L _d, ρ is convex grey subset;

Solve and can obtain i _d

$i_d=-\frac{{\mathrm{\ψ}}_{\mathrm{exc}}}{L_d}+{\mathrm{\Δi}}_d---\left(16\right)$

Wherein, ${\mathrm{\Δi}}_d=\frac{{\mathrm{\ρ\ψ}}_{\mathrm{exc}}-\sqrt{{\mathrm{\ρ}}^2{\mathrm{\ψ}}_{\mathrm{exc}}^2+8{(\mathrm{\ρ}-1)}^2{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2}}{4(\mathrm{\ρ}-1)L_d},$ Bring formula (16) into formula (13), following electric current can be obtained and distribute:

$\left\{\begin{array}{c}{i}_q=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{\left(L_d{\mathrm{\Δi}}_d\right)}^2}\\ i_f=i_{\mathrm{fN}}\\ i_d=-\frac{{\mathrm{\ψ}}_{\mathrm{exc}}}{L_d}+{\mathrm{\Δi}}_d\end{array}\right.---\left(17\right)$

(6) with the d shaft current reference value i that distributing switch produces _drefdeduct the d shaft current i in step (2) _dobtain d shaft current deviation delta i _d, with q shaft current i _qrefdeduct the q shaft current i in step (2) _qobtain q shaft current deviation delta i _q, by d shaft current deviation delta i _dinput d shaft current adjuster carries out proportional integral computing, obtains d shaft voltage u _d, by q shaft current deviation delta i _qinput q shaft current adjuster carries out proportional integral computing, obtains q shaft voltage u _q, then to described d shaft voltage u _dwith q shaft voltage u _qafter jointly carrying out rotating orthogonal-static two phase inversion, obtain α shaft voltage u under static two phase coordinate systems _αwith β shaft voltage u _β, by described α shaft voltage u _αwith β shaft voltage u _βinput pulse width modulation module, computing exports 6 road pulse width modulating signals, drives main power inverter;

The exciting current i simultaneously will gathered in step (1) _f, with exciting current reference value i after signal condition and A/D are changed _frefsend into DC excitation pulse width modulation module together, computing exports 4 road pulse width modulating signals to drive exciting power converter.

Above-described embodiment is only the preferred embodiment of the present invention; be noted that for those skilled in the art; under the premise without departing from the principles of the invention; some improvement and equivalent replacement can also be made; these improve the claims in the present invention and are equal to the technical scheme after replacing, and all fall into protection scope of the present invention.

Claims (2)

1. a hybrid exciting synchronous motor peak power output control method, is characterized in that, the method comprises the following steps:

(1) phase current i is gathered from motor main circuit _a, i _bwith exciting current i _f, initial position detection is carried out to motor, collection signal from motor encoder, sends into controller and process, draw rotating speed n and rotor position angle θ;

(2) the phase current i will gathered _a, i _bthrough following, filtering, biased and A/D conversion, then carry out park transforms, obtain the stator d shaft current i under two-phase rotating coordinate system _dwith q shaft current i _q;

(3) given rotating speed n is used ^*deduct encoder actual measurement rotating speed n, the rotating speed deviation delta n input speed adjuster obtained is obtained torque reference value after proportional integral computing by torque reference value busbar voltage U _dc, stator d shaft voltage u _d, stator q shaft voltage u _q, actual measurement rotating speed n and given rotating speed n ^*input current distributor, judges motor traffic coverage according to rotating speed: when actual speed is greater than rated speed, then hybrid exciting synchronous motor runs on low regime, enter step 4), otherwise hybrid exciting synchronous motor runs on high velocity, enter step 5);

(4) judge whether load torque meets T _l≤ T _n, wherein T _lfor load torque, T _nfor nominal torque;

Work as T _l≤ T _ntime, without the need to increasing magnetic control, i _fref=0, adopt i _d=0 controls, and distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{dref}}=0\\ i_{\mathrm{qref}}=\frac{2T_{\mathrm{eref}}}{3p{\mathrm{\ψ}}_m}\\ i_{\mathrm{fref}}=0\end{array}\right.$

Work as T _l> T _ntime, q shaft current reaches rated value, need carry out increasing magnetic control, therefore i _q=i _qN, adopt i _d=0 controls, and distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{dref}}=0\\ i_{\mathrm{fref}}=\frac{2T_{\mathrm{eref}}-3p{\mathrm{\ψ}}_m{i}_{\mathrm{qN}}}{3p{M}_f{i}_{\mathrm{qN}}}\\ i_{\mathrm{qref}}=i_{\mathrm{qN}}\end{array}\right.$

Wherein, i _dreffor d shaft current reference value, i _qreffor q shaft current reference value, i _freffor excitation winding current reference value; ψ _mfor permanent magnet flux linkage, p is motor number of pole-pairs; i _qNfor q shaft current rated value, L _d, L _qbe respectively stator winding d axle and q axle inductance, M _ffor the mutual inductance between armature winding and excitation winding, T _ereffor electromagnetic torque reference value;

(5) the 1st stages continue to keep i _dref=0, adopt the weak magnetic of peak power output control method, distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{qref}}=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{\left(M_f\mathrm{\Δ}{i}_f\right)}^2}\\ i_{\mathrm{dref}}=0\\ i_{\mathrm{fref}}=-\frac{{\mathrm{\ψ}}_m}{M_f}-\mathrm{\Δ}{i}_f\end{array}\right.$

Wherein, $\mathrm{\Δ}{i}_f=\frac{1+\sqrt{1+4{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2}}{2M_f};$

After exciting current reaches rated value, the 2nd stage continues peak power output method and carries out weak magnetic, and distributing switch is according to following current sharing scheme output current:

$\left\{\begin{array}{c}{i}_{\mathrm{qref}}=\frac{1}{L_q}\sqrt{{\left(\frac{u_s}{{\mathrm{\ω}}_e}\right)}^2-{\left(L_d\mathrm{\Δ}{i}_d\right)}^2}\\ i_{\mathrm{fref}}=i_{\mathrm{fN}}\\ i_{\mathrm{dref}}=-\frac{{\mathrm{\ψ}}_{\mathrm{exc}}}{L_d}+\mathrm{\Δ}{i}_d\end{array}\right.$

Wherein, $\mathrm{\Δ}{i}_d=\frac{\mathrm{\ρ}{\mathrm{\ψ}}_{\mathrm{exc}}-\sqrt{{\mathrm{\ρ}}^2{\mathrm{\ψ}}_{\mathrm{exc}}^2+8{(\mathrm{\ρ}-1)}^2{\left(\frac{{\mathrm{\μ}}_s}{{\mathrm{\ω}}_e}\right)}^2}}{4(\mathrm{\ρ}-1)L_d},$ ρ=L _q/ L _d, ψ _exc=ψ _m+ M _fi _fN, i _fNfor exciting current rated value, ρ is convex grey subset, ω _efor angular rate;

(6) with the d shaft current reference value i that distributing switch produces _drefdeduct the d shaft current i in described step (2) _dobtain d shaft current deviation delta i _d, with q shaft current i _qrefdeduct the q shaft current i in described step (2) _qobtain q shaft current deviation delta i _q; By d shaft current deviation delta i _dinput d shaft current adjuster carries out proportional integral computing, obtains d shaft voltage u _d, by q shaft current deviation delta i _qinput q shaft current adjuster carries out proportional integral computing, obtains q shaft voltage u _q, then to described d shaft voltage u _dwith q shaft voltage u _qafter jointly carrying out rotating orthogonal-static two phase inversion, obtain α shaft voltage u under static two phase coordinate systems _αwith β shaft voltage u _β, by described α shaft voltage u _αwith β shaft voltage u _βinput pulse width modulation module, computing exports 6 road pulse width modulating signals, drives main power inverter;

The exciting current i simultaneously will gathered in step (1) _f, through following, filtering, biased and A/D change after and exciting current reference value i _frefsend into DC excitation pulse width modulation module together, computing exports 4 road pulse width modulating signals to drive exciting power converter.

2. hybrid exciting synchronous motor peak power output control method according to claim 1, is characterized in that, described step 6) in Pulse width modulation module be space vector pulse width modulation module.