CN104459628A - Quasi-orthogonal frequency division multiplexing multicarrier linear FM radar signal design and processing method - Google Patents

Quasi-orthogonal frequency division multiplexing multicarrier linear FM radar signal design and processing method Download PDF

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CN104459628A
CN104459628A CN201310427994.0A CN201310427994A CN104459628A CN 104459628 A CN104459628 A CN 104459628A CN 201310427994 A CN201310427994 A CN 201310427994A CN 104459628 A CN104459628 A CN 104459628A
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lfm
frequency
speed
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杨瑞娟
李晓柏
程伟
胡登鹏
张尊泉
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/41—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00 using analysis of echo signal for target characterisation; Target signature; Target cross-section

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Radar Systems Or Details Thereof (AREA)

Abstract

The invention relates to a new system quasi-orthogonal frequency division multiplexing multicarrier linear FM (LFM) radar signal and a corresponding echo processing method. The invention designs a multicarrier LFM radar waveform which has quasi-orthogonality and the polarities of adjacent subcarrier frequency modulation rates are opposite. The waveform permits a certain overlapped bandwidth between subcarriers, so as to reduce bandwidth cost. Aimed at problems of moving object speed and distance coupling in signal object echo processing, a combined speed estimation method based on subcarrier rough estimation and a minimum entropy evaluation method is provided, realizing one-time echo wave speed estimation. The operand of the method is little, and the method is easy to realize. The signal design and the processing method are mainly used in system design of new system multicarrier radars with high bandwidth efficiency.

Description

Accurate OFDM multi-carrier linear frequency modulated radar signal design and disposal route
Technical field
The present invention relates to the design of a kind of New System multicarrier linear frequency modulation (LFM) radar waveform and method for processing received signal thereof, it is characterized in that adopting accurate orthogonal frequency division multiplexi to solve contradiction between multicarrier Waveform Design sub-carriers quantity and system spectrum utilization factor.And OFDM multi-carrier LFM radar signal aimed at by pin, proposes echo reception disposal route, and completes single echo wave speed estimation problem.
Background technology
Multicarrier Radar Signal is a kind of new radar signal form occurred in recent years, can be regarded as the frequency-region signal quantized, synthesis large bandwidth obtains High Range Resolution, and subcarrier form is suitable for adopting multi-channel structure to obtain the advantage of Narrow-band processing, has met the trend of modern radar multiband.Multicarrier radar is as a kind of wideband-radar signal of high distance resolution, compared with Step Frequency Radar, launch because radar signal is modulated on multiple orthogonal subcarrier by multi-carrier signal simultaneously, therefore the duration is shorter, insensitive to target travel, be comparatively applicable to the detection of high-speed target.And the information that radar utilizes multiple carrier wave to return detects simultaneously, the ability of target detection effectively can be improved.Multicarrier range radar has the advantages that finding range is large and precision is high, is applied in navigation, observing and controlling and various space precise range measurement system.A kind of suitable waveform is selected to be the matter of utmost importance that a kind of new system radar of research faces, in order to strengthen the detection performance of multi-carrier signal, usual hope arranges more number of sub carrier wave in certain frequency band, if sub-carrier band is overlapped, then inter-sub-carrier interference is serious, certainly will weaken target detection performance.To make the cross correlation value between sub-carrier signal little as far as possible, the band separation between two adjacent sub-carrier signals must increase as far as possible, then system bandwidth spending is greater than ( bfor subcarrier bandwidth, nfor signal number), therefore need the research more much higher carrier design method of the availability of frequency spectrum and corresponding method for processing received signal thereof.
Summary of the invention
The object of the invention is for the lower problem of the availability of frequency spectrum of multicarrier LFM signal, the present invention adopts accurate orthogonal frequency division multiplexi to solve contradiction between multicarrier Waveform Design sub-carriers quantity and system spectrum utilization factor.
Description of contents of the present invention is divided into the following aspects: the design concept of accurate orthogonal frequency division multiplexi; Method for processing received signal (static target echo signal processing and moving target analysis); Secondary velocity based on subcarrier compensates.
1 design concept
Consider the multicarrier LFM signal group of one group of different carrier frequency , its expression formula is
（1）
Wherein, for the carrier frequency of a kth subcarrier, for sub-carrier frequencies interval.At receiving end, to extract signal independently from this group frequency division LFM signal , then signal need ensure frequency domain orthogonality condition, meets the requirement of formula (1).
（2）
Wherein, for signal s i ( t) Fourier transform, for signal s j ( t) conjugation of Fourier transform.Because LFM signal is time limited signal, be obviously difficult to the requirement meeting above formula.If can design one group of LFM signal, the autocorrelation function of each signal has narrow main lobe, can ignore compared to the cross correlation value between autocorrelation sidelobe unlike signal, now can think that this group signal meets the requirement of near orthogonality.If make the cross correlation value between LFM signal little as far as possible, the band separation between two adjacent LFM signals must increase as far as possible, then system bandwidth spending is greater than ( bfor the bandwidth of single LFM signal, nfor signal number).But, if increase interval between LFM signal, then the sub-carrier number in certain bandwidth must be made to reduce.In Practical Project, if the ratio of signal cross-correlation peak value and autocorrelation peak is less than-30dB, then can ignore the impact disturbed between adjacent sub-carrier input.Therefore, hereafter study under certain bandwidth overlay rate, between LFM signal, meet quasi-orthogonal condition.
In limited frequency band, designing the orthogonal LFM signal of standard as much as possible, is the effective ways reducing bandwidth spending.But the band overlapping of two signals is more, and cross correlation value is larger, its inter-sub-carrier interference is more serious.In order to the above-mentioned contradiction of equilibrium, below, the quasi-orthogonal method of LFM signal that we adopt structure carrier frequency adjacent reduces frequency band expense, and research is under certain band overlapping further, and LFM signal meets quasi-orthogonal condition.
If the original frequency of its LFM signal is respectively f 1, f 2, then three LFM signals x, y, zbe expressed as
（3）
Wherein, zwith ythat original frequency is identical, the opposite polarity LFM signal of frequency modulation rate.
When the band overlapping rate ratio of overlapping bands and sub-carrier band width (between the adjacent sub-carrier) is 25%, calculate the LFM signal of opposite polarity frequency modulation rate respectively x, ywith the LFM signal of identical polar frequency modulation rate x, znormalized crosscorrelation maximal value, emulation can obtain two LFM signals of identical polar frequency modulation rate x, zmaximum normalized crosscorrelation value be-21dB, obtain two LFM signals of opposite polarity frequency modulation rate x, ymaximum normalized crosscorrelation value be-31dB, the accurate orthogonality of its signal is better than the former.But xwindowing autocorrelation function secondary lobe be-31dB, this shows the suitable of signal cross-correlation peak value and autocorrelation sidelobe peak value, meet the condition of the accurate orthogonality of multi-carrier signal.
Known to the analysis of adjacent LFM signal group, one group of LFM signal can be designed, make the auto-correlation of each LFM signal have narrow main lobe and low secondary lobe, and the cross correlation value of any two different LFM signals can be ignored.Then one group of accurate orthogonal LFM composite signal in given bandwidth, is provided with nroad radar subcarrier, its frequency modulation rate is negative, then the tune frequency polarity between adjacent sub-carrier is contrary, if bandwidth overlay rate is 25% between its adjacent sub-carrier, then arbitrary neighborhood subcarrier can both keep good orthogonality under certain Doppler shift.Multi-carrier signal can be expressed as
（5）
Wherein, centered by frequency, for subcarrier bandwidth, for frequency modulation rate.
2 static target echo signal processings
Receiving end disposal route, with reference to the principle of Stepped frequency radar imaging, utilizes multicarrier radar time stepping to be converted to frequently the thought of frequency diversity.Its concrete processing procedure is followed successively by frequency modulation removal, subcarrier separation, Frequency mixing processing, FFT bigness scale Distance geometry coherent synthesis process.
Suppose distance receiver rthe echoed signal of place's static target is
（6）
Wherein, for Received signal strength time delay.At receiving end, first deramp processing is done to the multi-carrier signal received, by signal and a transmitting reference signal phase mixing, can obtain baseband signal is
（7）
Then subcarrier separation is carried out to the low pass signal filtering after mixing, then respectively with the frequency difference phase of odd number subcarriers with the frequency difference phase of even number subcarriers mixing also obtains subcarrier baseband signal and is
（8）
Range compress process (namely FFT conversion and IFFT convert) is done respectively to the odd number road of above formula and even number road, can obtain:
（9）
To above formula delivery, obtain a sinc function spectrum peak, as can be seen from the above equation, the position of peak value is
（10）
As can be seen from formula (10), the position of the detection of a target determines then can obtain the position at sinc function spectrum peak the bigness scale distance of target, get target place bigness scale range unit and compensate unnecessary phase place , and the signal of subcarriers all on this range unit is done nthe IFFT of point, its expression formula is
（11）
Can obtain formula (11) delivery:
（12）
This completes the coherent synthesis process of a range unit, as can be seen from above formula (12), when time, occur peak value, therefore, measuring the target range obtained is , pulse combination one distance main lobe width is sinc function type burst pulse.
3 moving target analyses
Hypothetical target distance is r 0linear uniform motion is done to cell site with speed v.Then launch echo time delay can be expressed as
（13）
Then subcarrier be separated after mixing can obtain the iroad radar sub-carrier signal:
（14）
Wherein .Range compress process (namely FFT conversion and IFFT convert) is done respectively to the odd number road of above formula and even number road, and then delivery can obtain:
（15）
From above formula, after Range compress delivery calculates, the amplitude of signal is sincfunction, and there is peak value when meeting following formula:
（16）
Therefore, the bigness scale distance of target can be obtained:
（17）
As can be seen from the above equation, the Doppler frequency of moving target is coupled in range information, must compensate above formula, could accurate measurement target distance.
4 compensate based on the secondary velocity of subcarrier
As can be seen from above formula (16), after FFT delivery calculates, only just understand bigness scale at the doppler cells place at target place and go out burst pulse, suppose the iindividual subcarrier and i+ kafter calculating respectively through Range compress delivery, with place obtains the peak value of two sinc functions, then with can be expressed as respectively:
（18）
（19）
Can be obtained by above formula (18) and (19):
（20）
Can slightly go out target velocity and be in side:
（21）
If kbe worth larger, then the peak value of two subcarriers after Range compress delivery calculates is at a distance of larger, can estimate peak difference more accurately like this .
In order to the speed of further accurately estimating target, minimum Information Entropy is adopted to carry out second compensation to target velocity.For the bigness scale Range Profile obtained after FFT delivery calculates, its envelope distribution divergence can be measured with entropy, and entropy is larger, and the waveform sharpening degree of each picture point is lower, and there will be the phenomenon defocused; Entropy is less, and the waveform sharpening degree of each picture point is higher, as focusing better.Minimum Information Entropy is by by the one-dimensional range profile amplitude normalization after velocity compensation, then constructs entropy, obtains the precision target speed making entropy reach minimum v 0.Hypothetical target is in speed vunder the discrete series of bigness scale Range Profile amplitude be , order , its normalization amplitude is , then entropy can be defined as
（22）
h( a) reflect a( v) concentration degree of each component in sequence, the sharpening degree of target distance image envelope is higher, a( v) insignificant component is more in sequence, h( a) value less, otherwise, h( a) value larger.Specific algorithm is as follows:
Step 1: through Range compress delivery, by iindividual subcarrier and i+ kindividual subcarrier information bigness scale goes out target velocity v.
Step 2: suppose that velocity compensation precision is v 0, then basis vwith v 0can determine hunting zone be [ v- n v 0, v+n v 0], wherein nfor natural number.
Step 3: select different nvalue, obtains bigness scale speed, then compensates unnecessary phase place on each subcarrier of being caused by Doppler shift.
Step 4: each sub-carrier waveforms after compensating is carried out npoint IFFT computing, obtains the entropy function shown in formula (22) h( a).
Step 5: increase gradually nvalue, expands hunting zone, calculates the entropy corresponding to different velocity estimation values, obtain the speed that entropy reaches minimum according to step (3), (4) as speed vaccurate estimating speed.
Accompanying drawing illustrates:
Fig. 1: the LFM signal overlap frequency band of bipolarity contrary frequency modulation rate frequency modulation rate identical with bipolarity
Under the certain band overlapping rate ratio of overlapping bands and sub-carrier band width (between the adjacent sub-carrier), between adjacent sub-carrier, two adjust the contrary LFM signal of frequency polarity x, ythe identical LFM signal of frequency polarity is adjusted with two x, zinstantaneous frequency over time as shown in Figure 1, if , then two signal bands are separated, and band overlapping rate is zero; If , then two LFM signal spectrums partly overlap, and there is interference between signal.
 
Fig. 2: adjust the Normalized Cross Correlation Function that frequency polarity is identical and contrary
Fig. 2 represents when band overlapping rate is 25%, the LFM signal x of opposite polarity frequency modulation rate, the LFM signal x of y and identical polar frequency modulation rate, the normalized crosscorrelation value of z, adopt hamming window to carry out windowing process to the auto-correlation of LFM signal in figure, its maximum autocorrelation sidelobe is 31dB.Can draw, when bandwidth overlay rate is 25%, the maximum normalized crosscorrelation value of two LFM signals of identical polar frequency modulation rate can be obtained for-21dB from Fig. 2, can obtain the maximum normalized crosscorrelation value of two LFM signals of opposite polarity frequency modulation rate for-31dB, the accurate orthogonality of its signal is better than the former.
 
Fig. 3: two groups of contrary LFM signal cross-correlation ratios identical with polarity of polarity
Fig. 3 represents under different band overlapping rates, two groups of LFM signals x, ywith x, zthe ratio of cross-correlation peak value, as can be seen from Figure, along with the increase of bandwidth overlay rate, two LFM signal maximum cross-correlation value increments of identical polar frequency modulation rate are far longer than the maximum cross-correlation value increment of opposite polarity frequency modulation rate, when band overlapping rate reaches 0.85, maximum cross-correlation peak value ratio increases 10 times, and between identical polar frequency modulation rate LFM signal, subcarrier interference is serious.As the above analysis, when frequency division multi-carrier signal designs, if adopt opposite polarity frequency modulation rate between adjacent sub-carrier, then under certain bandwidth overlay rate, good accurate orthogonality will be kept between each subcarrier.
 
Fig. 4: bandwidth overlay rate and cross correlation function graph of a relation
Show that the relation of CRatio and bandwidth overlay rate is illustrated in fig. 4 shown below by Computer Simulation, as seen from the figure to meet CRatio at below-31dB, band overlapping rate must be less than 25%.
 
Fig. 5: the frequency response schematic diagram of accurate orthogonal multiple carrier LFM signal
Then in given bandwidth, the frequency response of one group of accurate orthogonal LFM composite signal as shown in Figure 5, is provided with nroad radar subcarrier, its frequency modulation rate is negative, then the tune frequency polarity between adjacent sub-carrier is contrary, if bandwidth overlay rate is 25% between its adjacent sub-carrier.
 
Fig. 6: radar receives echo signal processing flow process
Concrete processing procedure is followed successively by frequency modulation removal, subcarrier separation, Frequency mixing processing, FFT bigness scale Distance geometry coherent synthesis process.

Claims (2)

1. an accurate OFDM multi-carrier linear frequency modulated radar signal design, its waveform character is: multi-carrier signal adopts the LFM signal of opposite polarity frequency modulation rate on adjacent sub-carrier, and between its adjacent sub-carrier, band overlapping rate is set to 25%.
2. according to claim 1 based on accurate OFDM multi-carrier linear frequency modulated radar signal, for the problem that velocity to moving target is coupled with distance, propose and a kind ofly estimate the associating speed estimation method with minimum Information Entropy quadratic estimate for the first time based on subcarrier, it is characterized in that: utilize the relation between the peak value of bigness scale distance and Doppler shift, obtain the value according to a preliminary estimate of speed, then, on the basis that speed is worth according to a preliminary estimate, minimum Information Entropy is utilized accurately to estimate speed.
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CN105548968A (en) * 2015-12-14 2016-05-04 桂林电子科技大学 Method of suppressing Doppler spread by multiband Chirp in moving target detection (MTD)
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CN111929656A (en) * 2020-09-23 2020-11-13 南京楚航科技有限公司 Entropy value statistics-based noise estimation method for vehicle-mounted millimeter wave radar system
CN113074967A (en) * 2020-01-06 2021-07-06 北京谛声科技有限责任公司 Abnormal sound detection method and device, storage medium and electronic equipment
CN113687344A (en) * 2021-07-20 2021-11-23 西安空间无线电技术研究所 Triangular wave modulation linear frequency modulation continuous wave radar speed measurement method
CN115963468A (en) * 2023-03-16 2023-04-14 艾索信息股份有限公司 Radar target identification method, device and equipment

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Cited By (15)

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Publication number Priority date Publication date Assignee Title
CN104849711A (en) * 2015-04-22 2015-08-19 大连理工大学 Frequency domain-based Doppler compensation method for I-OFDM MIMO radar signal
CN106291559A (en) * 2015-06-08 2017-01-04 罗伯特·博世有限公司 For the method running radar equipment
CN105548968A (en) * 2015-12-14 2016-05-04 桂林电子科技大学 Method of suppressing Doppler spread by multiband Chirp in moving target detection (MTD)
CN105548968B (en) * 2015-12-14 2017-10-20 桂林电子科技大学 A kind of many methods for suppressing doppler spread when moving-target is detected with Chirp
CN107102319A (en) * 2016-02-19 2017-08-29 松下电器产业株式会社 Radar installations
CN110673129A (en) * 2018-07-03 2020-01-10 松下知识产权经营株式会社 Estimation device and estimation method
CN110673129B (en) * 2018-07-03 2024-02-06 松下知识产权经营株式会社 Estimation device and estimation method
CN109188370A (en) * 2018-10-29 2019-01-11 北京遥感设备研究所 A kind of radar equipment LFM pulse signal envelope curve approximating method and system
CN113074967A (en) * 2020-01-06 2021-07-06 北京谛声科技有限责任公司 Abnormal sound detection method and device, storage medium and electronic equipment
CN113074967B (en) * 2020-01-06 2022-12-16 北京谛声科技有限责任公司 Abnormal sound detection method and device, storage medium and electronic equipment
CN111929656A (en) * 2020-09-23 2020-11-13 南京楚航科技有限公司 Entropy value statistics-based noise estimation method for vehicle-mounted millimeter wave radar system
CN113687344A (en) * 2021-07-20 2021-11-23 西安空间无线电技术研究所 Triangular wave modulation linear frequency modulation continuous wave radar speed measurement method
CN113687344B (en) * 2021-07-20 2023-08-11 西安空间无线电技术研究所 Triangular wave modulation linear frequency modulation continuous wave radar speed measuring method
CN115963468A (en) * 2023-03-16 2023-04-14 艾索信息股份有限公司 Radar target identification method, device and equipment
CN115963468B (en) * 2023-03-16 2023-06-06 艾索信息股份有限公司 Radar target identification method, device and equipment

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