CN104393781A - Frequency domain electrical prospecting high voltage transmitter and control method thereof - Google Patents
Frequency domain electrical prospecting high voltage transmitter and control method thereof Download PDFInfo
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- CN104393781A CN104393781A CN201410675852.0A CN201410675852A CN104393781A CN 104393781 A CN104393781 A CN 104393781A CN 201410675852 A CN201410675852 A CN 201410675852A CN 104393781 A CN104393781 A CN 104393781A
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- signal
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
- H02M7/49—Combination of the output voltage waveforms of a plurality of converters
Abstract
The invention relates to a frequency domain electrical prospecting high voltage transmitter and control method thereof. The frequency domain electrical prospecting high voltage transmitter is composed by that a three-phase alternating current generator a is connected with the anode of a ground load via an isolated direct current regulated power supply I and a high voltage inverter bridge; a three-phase alternating current generator c is connected with the cathode of the ground load via an isolated direct current regulated power supply III and the high voltage inverter bridge; a three-phase alternating current generator b is connected with the cathode of the isolated direct current regulated power supply I via the anode of the isolated direct current regulated power supply II; the cathode of the isolated direct current regulated power supply II is connected with the anode of the isolated direct current regulated power supply III; and the high voltage inverter bridge is connected with a main control unit. Compared with the prior art, the frequency domain electrical prospecting high voltage transmitter uses low voltage withstanding small-power devices to achieve the high-voltage large power output; compared with the two-level output of the prior art, the dv/dt is lower; the insulation impulse and electromagnetic interference are reduced; and the frequency domain electrical prospecting high voltage transmitter has the advantages that the number of power devices is small, the control method is simple and convenient, and the problem of capacitor voltage sharing does not exist. Additionally, the wiring complexity is low, the failure rate is low, and the credibility is high, thereby meeting the requirement of field application.
Description
Technical field:
The present invention relates to the electrical prospecting emitter in a kind of geophysical exploration and control method, the frequency domain high-power being particularly useful for launching hard pulse square-wave signal launches occasion.
Background technology:
In geophysical exploration, artificial source's frequency domain electro-prospecting detection instrument is made up of transmitter and receiver two parts.Transmitter is used for launching the periodic bipolar square wave signal with different frequency, as the controlled artificial field source of electrical survey (-ing) to search coverage.Receiver gathers and records corresponding electromagnetic response data, by the Data Analysis Services collected, and the inversion interpretation of final realize target areal geology structure.In above-mentioned electrical prospecting process, improve the output voltage of emitter, the transmitting power of transmitter can be improved, strengthen nagneto-telluric field response signal, improve the signal to noise ratio of receiver collection signal, strengthen resolution and the investigation depth of detection instrument.
Fig. 9 is existing H bridge inverter bridge road schematic diagram, existing artificial field source adopts single-stage DC power supply cascaded H bridge inverter structure to launch ambipolar pulse square wave signal usually, H bridge generally selects high-voltage high-speed power electronic device IGBT as switching device, usually selects the electric pressure of IGBT to be 1200V or 1700V.
In practical application, in order to ensure that power electronic device has safe and reliable working range, IGBT voltage withstand class choose 2 ~ 3 times that are generally DC bus-bar voltage.Nowadays also 3.3kV is had, the high pressure IGBT of 4.5kV, 6.5kV, although the object selecting that the IGBT of higher voltage withstand class can reach high-voltage inverted, but due to the self structure of IGBT and the restriction of technological level, the corresponding high conduction losses of higher withstand voltage IGBT and switching loss.Higher thermal losses also can cause more complicated heat dissipation problem simultaneously, uses larger heat abstractor to increase volume and the weight of instrument and equipment, causes great difficulty to field studies.Meanwhile, the cost that the IGBT of high voltage withstand class is corresponding higher.In addition, due to the restriction of above-mentioned IGBT constant power power electronic device, the prime D.C. regulated power supply difficult design on H bridge inverter bridge road is caused.The object that these reasons cause adopting the transmitter that combines with the inversion of single-stage H bridge of traditional single-stage DC power supply to be difficult to realize high-power exporting.
Current a kind of conventional solution is for selecting low-voltage-grade IGBT series system to improve emitting voltage grade.Application of directly being connected by IGBT needs to carry out dynamic and static state to it and all presses, and the switching speed of IGBT comparatively fast makes equalizer circuit become complicated, and meanwhile, the equalizer circuit of interpolation also will cause loss to rise, and cause decrease in efficiency.
In addition, multi-level inverse conversion technology can realize high-power output by improving self topological structure, and multi-electrical level inverter approaches sine wave by producing Cycle-symmetry stepped square wave, is widely used in electric power system and large-size machine driving.Basic Topological is divided into diode hoop bit-type, electric capacity hoop bit-type and cascade connection type three kinds.Under identical electric pressure, Figure 10 is diode hoop bit-type multi-level inverse conversion bridge road schematic diagram, and hoop position diode and the switching tube number of its needs are more, and cost is high; There is voltage-sharing in DC bus end input bulky capacitor, equalizer circuit and Pressure and Control complexity.Figure 11 is electric capacity hoop bit-type multi-level inverse conversion bridge road schematic diagram, and because it uses electric capacity number many, electric capacity volume is large, poor reliability, and the high and each electric capacity of cost needs all to press, and causes research at present less, lacks Practical significance.Figure 12 is cascading multiple electrical level inverter bridge road schematic diagram, its method adopting modular unit to connect, and each block coupled in series unit comprises transmitting bridge and isolation stabilized voltage power supply.Usual cascaded inverter carries out independent control to gang mould module unit at different levels, causes wiring various, is subject to extraneous factor interference.Particularly when a certain cascade module unit generation driving malfunction (namely drives inefficacy, without drive singal), trouble unit busbar voltage will become the summation of other concatenation unit voltage, and causing trouble unit bridges road front end direct current stabilized voltage power supply is damaged because of output high pressure.Above reason causes cascade connection type emission system stability to decline, and failure rate improves, and indirectly reduces field construction efficiency, adds exploration cost.
In control method, traditional multi-electrical level inverter adopts complicated control method, and object makes sine wave output shape have more low distortion and harmonic wave rate.And in electrical prospecting field, output waveform does not require it is sinusoidal wave, actual needs be fundamental frequency square-wave pulse signal, so the control method of traditional multi-electrical level inverter be not suitable for electrical prospecting.
CN101634719A proposes a kind of inverter for outputting cascade high voltage being applicable to electrical prospecting, this device adopts tandem type modular unit, every one-level is adopted low voltage designs, then multi-level unit series connection, due to the summation that busbar voltage is cascading power source voltage at different levels, therefore achieve the object of high voltage output.But, due in control method, bridge road at different levels adopts synchronized signal to control, output voltage is the bipolar square wave of two level, under identical DC bus-bar voltage condition, than multi-level inverse conversion device, this inverter by producing larger dv/dt, causes serious electromagnetic interference problem and higher insulating requirements in the course of the work.Meanwhile, need to carry out independent control to gang mould module unit at different levels, wiring is various.The most fatal: when a certain cascade module unit generation driving malfunction (namely drives inefficacy, without drive singal), trouble unit busbar voltage will become the summation of other concatenation unit voltage, and causing trouble unit bridges road front end direct current stabilized voltage power supply is damaged because of output high pressure.
Summary of the invention:
Object of the present invention is exactly the deficiency for above-mentioned technology, provides a kind of frequency domain electro-prospecting to explore high pressure emitter.
Another object of the present invention is to provide the control method of a kind of frequency domain electro-prospecting exploration high pressure emitter.
The object of the invention is to be achieved through the following technical solutions:
1, a kind of frequency domain electro-prospecting exploration high pressure emitter, it is characterized in that, be connected with the positive pole of earth load 9 with high-voltage inverted bridge road 7 through isolated DC stabilized voltage power supply I 4 by threephase alternator a1, threephase alternator c3 is connected with the negative pole of earth load 9 with high-voltage inverted bridge road 7 through isolated DC stabilized voltage power supply III 6, threephase alternator b2 is connected with the negative pole of isolated DC stabilized voltage power supply I 4 through the positive pole of isolated DC stabilized voltage power supply II 5, the negative pole of isolated DC stabilized voltage power supply II 5 is connected with isolated DC stabilized voltage power supply III 6 positive pole, high-voltage inverted bridge road 7 connects and composes with main control unit 8.
2, according to frequency domain electro-prospecting exploration high pressure emitter according to claim 1, it is characterized in that, main control unit 8 drives I to be connected through fault detect and transformer isolation respectively by voltage transformer, current transformer and thermistor, reset key is connected with malfunction coefficient through latch, human-computer interaction interface drives II to be connected with delay circuit AND OR NOT gate circuit through microprocessor, optical coupling isolation circuit, OR-NOT circuit, dead crystal drive circuit, transformer isolation driving I, driving parallel port, transformer isolation, and fault detect connects and composes through latch AND OR NOT gate circuit.
3, according to frequency domain electro-prospecting exploration high pressure emitter according to claim 2, it is characterized in that, described transformer isolation drives 1 respectively to VT
11, VT
42, VT
22, VT
31collector and emitter between voltage V
cEcarry out input, work as VT
11, VT
42, VT
22, VT
31in the V of any switching tube
cEwhen exceeding setting protection threshold values, immediately the drive singal of respective switch pipe is set low, control drive singal A and B is all set low; For VT
12, VT
41, VT
21, VT
32, all do not detect the voltage V between collector and emitter
cE, D
rive12and D
rive41only be controlled by drive singal A, D
rive21and D
rive32only be controlled by drive singal B; When there is overvoltage, overcurrent, overheating fault, control drive singal A and B is all set low.
4, according to frequency domain electro-prospecting exploration high pressure emitter according to claim 1, it is characterized in that, high-voltage inverted bridge road 7 is by three electric capacity C
1, C
2and C
3, four diode D
1, D
2, D
3and D
4, eight switching tube VT
11, VT
12, VT
21, VT
22, VT
31, VT
32, VT
41and VT
42form; Electric capacity C
1positive pole hold with HH and be connected, electric capacity C
1negative pole hold with HL and be connected, electric capacity C
2positive pole hold with HL and be connected, electric capacity C
2negative pole hold with LH and be connected, electric capacity C
3positive pole hold with LH and be connected, electric capacity C
2negative pole hold with LL and be connected; VT
11collector electrode hold with HH and be connected, VT
11emitter and VT
12collector electrode connect, VT
12emitter and VT
21collector electrode be connected with output OUTA, VT
21emitter and VT
22collector electrode connect, VT
22emitter hold with LL and be connected, VT
31collector electrode hold with HH and be connected, VT
31emitter and VT
32collector electrode connect, VT
32emitter and VT
41collector electrode be connected with output OUTB, VT
41emitter and VT
42collector electrode connect, VT
42emitter hold with LL and be connected; D
1anode hold with LH and be connected, D
1negative electrode and VT
12collector electrode connect, D
2anode and VT
21emitter connect, D
2negative electrode hold with HL and be connected, D
3anode hold with LH and be connected, D
3negative electrode and VT
32collector electrode connect, D
4anode and VT
41emitter connect, D
4negative electrode and HL hold and connect and compose.
5, implement the claims a control method for the frequency domain electro-prospecting exploration high pressure emitter described in 1, it is characterized in that,
Two-way drive control signal A anti-phase each other and B is exported, by the rising edge time delay Δ t of signal A by main control unit 8
1, obtain signal D
aOUT, D
aOUTdrive singal D is formed after isolation processing
rive11and D
rive42, D
rive11and D
rive42be respectively used to control VT
11and VT
42, by the rising edge of signal A and trailing edge time delay Δ t respectively
2with Δ t
3, obtain signal D
aIN, D
aINdrive singal D is formed after isolation processing
rive12and D
rive41, D
rive12and D
rive41be respectively used to control VT
12and VT
41, by the rising edge time delay Δ t of signal B
1, obtain signal D
bOUT, D
bOUTdrive singal D is formed after isolation processing
rive22and D
rive31, D
rive22and D
rive31be respectively used to control VT
22and VT
31, by the rising edge of signal B and trailing edge time delay Δ t respectively
2with Δ t
3, obtain signal D
bIN, D
bINdrive singal D is formed after isolation processing
rive21and D
rive32, D
rive21and D
rive32be respectively used to control VT
21and VT
32; Δ t
1> Δ t
2> Δ t
3; Switching tube VT in one-period
11, VT
12, VT
21, VT
22, VT
31, VT
32, VT
41and VT
42turn-on sequence is:
A.VT
12, VT
41conducting, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
B.VT
12, VT
41, VT
11, VT
42conducting, VT
21, VT
32, VT
22, VT
31turn off,
C.VT
12, VT
41conducting, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
D.VT
12, VT
41, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
E.VT
21, VT
32conducting, VT
12, VT
41, VT
11, VT
42, VT
22, VT
31turn off,
F.VT
21, VT
32, VT
22, VT
31conducting, VT
12, VT
41, VT
11, VT
42, turn off,
G.VT
21, VT
32conducting, VT
12, VT
41, VT
11, VT
42, VT
22, VT
31turn off,
H.VT
12, VT
41, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off.
Beneficial effect: compared with prior art, the multi-level inverse conversion principle variation of existing sinewave output is applied to survey of the earth field and achieves high-voltage square-wave output by (1), completes the object of high-power output with low withstand voltage low-power device.(2) in the high-voltage inverted bridge road half period, output voltage is three level change, has lower dv/dt compared with exporting with existing two level, reduces insulation and impacts and electromagnetic interference.(3) under the prerequisite of identical input direct-current busbar voltage, there is power device number low, the easy feature of control method.(4) high voltage direct current side bus electric capacity adopts independently D.C. regulated power supply to power, and there is not capacitor voltage equalizing problem.(5) main control unit is connected with high-voltage inverted bridge road aviation plug through single shielded type cable by aviation plug, has wiring complexity low, the advantage of failure rate is low, uses under being adapted at field complex environment.(6) take the drived control method and the multiple protection method that are applicable to inversion topological structure, there is higher reliability, meet field studies demand.(7) geophysical exploration methods such as controlled-source audiomagnetotellurics method, frequency-domain IP method and complex resistivity method can be applied to.
Accompanying drawing illustrates:
Fig. 1 frequency domain electro-prospecting exploration high pressure emitter structured flowchart
High-voltage inverted bridge road 7, diode hoop position structure chart in Fig. 2 Fig. 1
The structured flowchart of main control unit 8 in Fig. 3 Fig. 1
Fig. 4 drive control signal and bridge road output waveform sequential chart
The circuit turn-on state diagram of high-voltage inverted bridge road, Fig. 5 diode hoop position
The conducting state figure that should avoid during the conducting of Fig. 6 high-voltage inverted bridge road
The conducting state figure that should avoid when the high-voltage inverted bridge road of Fig. 7 turns off
Circuit turn-on state diagram during Fig. 8 cascade connection type inverter bridge road driving malfunction
Equal electric pressure tradition H bridge inverter bridge road schematic diagram in Fig. 9 prior art
Equal electric pressure diode hoop bit-type inverter bridge road schematic diagram in Figure 10 prior art
Equal electric pressure electric capacity hoop bit-type inverter bridge road schematic diagram in Figure 11 prior art
Equal electric pressure cascade connection type inverter bridge road schematic diagram in Figure 12 prior art
Embodiment:
Below in conjunction with drawings and Examples as further detailed description:
Figure 1 shows that frequency domain electro-prospecting exploration high pressure emitter, be connected with isolated DC stabilized voltage power supply I 4 by threephase alternator a1, threephase alternator b2 is connected with isolated DC stabilized voltage power supply II 5, threephase alternator c3 is connected with isolated DC stabilized voltage power supply III 6, isolated DC stabilized voltage power supply I 4 output cathode is held with the HH on high-voltage inverted bridge road 7 and is connected, the HL on isolated DC stabilized voltage power supply I 4 output negative pole and isolated DC stabilized voltage power supply II 5 output cathode and high-voltage inverted bridge road 7 holds and is connected, the LH on isolated DC stabilized voltage power supply II 5 output negative pole and isolated DC stabilized voltage power supply III 6 output cathode and high-voltage inverted bridge road 7 holds and is connected, isolated DC stabilized voltage power supply III 6 output negative pole is held with the LL on high-voltage inverted bridge road 7 and is connected, high-voltage inverted bridge road 7 output OUTA with OUTB is connected with earth load 9, main control unit 8 and high-voltage inverted bridge road 7 connect and compose, main control unit 8 is made up of error protection unit and driving control unit.
Threephase alternator a1, threephase alternator b2 and threephase alternator c3 are used for providing energy to D.C. regulated power supply I 4, D.C. regulated power supply II 5 and D.C. regulated power supply III 6, after the energy that D.C. regulated power supply I 4, D.C. regulated power supply II 5 and D.C. regulated power supply III 6 couples of threephase alternator a1, threephase alternator b2 and threephase alternator c3 provide processes, provide the electric energy of voltage constant to high-voltage inverted bridge road 7.Isolated DC stabilized voltage power supply I 4, D.C. regulated power supply II 5 and D.C. regulated power supply III 6 are connected in series as high-voltage inverted bridge road 7 provides high input voltage.Main control unit 8 is connected with high-voltage inverted bridge road 7 aviation plug through single shielded type cable by aviation plug, exports ambipolar high-voltage square-wave pulse signal for controlling high-voltage inverted bridge road 7 to earth load 9.Earth load 9 is connected and forms at a distance of 1 ~ 3km grounding electrode with the earth by two, and its reactance is resistance sense, and usual equivalent inductance is 1mH ~ 8mH, equivalent resistance 10 ~ 80 Ω.
Being illustrated in figure 2 high-voltage inverted bridge road 7, is by three electric capacity C
1, C
2and C
3, four diode D
1, D
2, D
3and D
4, eight switching tube VT
11, VT
12, VT
21, VT
22, VT
31, VT
32, VT
41and VT
42form; Electric capacity C
1positive pole hold with HH and be connected, electric capacity C
1negative pole hold with HL and be connected, electric capacity C
2positive pole hold with HL and be connected, electric capacity C
2negative pole hold with LH and be connected, electric capacity C
3positive pole hold with LH and be connected, electric capacity C
2negative pole hold with LL and be connected; VT
11collector electrode hold with HH and be connected, VT
11emitter and VT
12collector electrode connect, VT
12emitter and VT
21collector electrode be connected with output OUTA, VT
21emitter and VT
22collector electrode connect, VT
22emitter hold with LL and be connected, VT
31collector electrode hold with HH and be connected, VT
31emitter and VT
32collector electrode connect, VT
32emitter and VT
41collector electrode be connected with output OUTB, VT
41emitter and VT
42collector electrode connect, VT
42emitter hold with LL and be connected; D
1anode hold with LH and be connected, D
1negative electrode and VT
12collector electrode connect, D
2anode and VT
21emitter connect, D
2negative electrode hold with HL and be connected, D
3anode hold with LH and be connected, D
3negative electrode and VT
32collector electrode connect, D
4anode and VT
41emitter connect, D
4negative electrode hold with HL and be connected.
Figure 3 shows that main control unit 8, comprise error protection unit and driving control unit two parts.Error protection unit is by voltage transformer, and current transformer is connected with latch through failure detector circuit with thermistor, and reset key connects and composes through latch and fault display circuit.Voltage transformer for detect high-voltage inverted bridge road 7 input direct-current bus HH and LL between voltage, current transformer is for detecting the electric current of the input direct-current bus HH on high-voltage inverted bridge road 7, thermistor is arranged on the diffusion sheet at IGBT place in high-voltage inverted bridge road 7, for detecting the temperature of fin.Failure detector circuit is used on the one hand detecting in real time the 4 tunnel driving malfunction logical signal D that in voltage analog signal V, the current analog signal I on current transformer and the temperature analog signal T on thermistor on voltage transformer and transformer isolation driving 1,1. driving malfunction output is gone up
error1,2,3,4; Compared with the protection threshold value arranged respectively by these signals on the other hand, when one or several in these signals is higher than the threshold value arranged, failure detector circuit exports corresponding high level overvoltage logical signal V
o, overcurrent logical signal I
o, overheated logical signal T
owith 4 tunnel driving malfunction logical signal D
o1,2,3,4.Latch is used for the overvoltage logical signal V exported by failure detector circuit
o, overcurrent logical signal I
o, overheated logical signal T
owith 4 tunnel driving malfunction logical signal D
o1,2,3,4latch, output overvoltage logical signal V
err, overcurrent logical signal I
err, overheated logical signal T
errwith 4 tunnel driving malfunction logical signal D
err1,2,3,4and lump fault logic signals E
err.Reset key is used for sending R to latch
essignal makes Latch output signal V
err, I
err, T
errwith 4 road D
err1,2,3,4and E
errreset to low level.Fault display circuit is made up of 7 LED light, is respectively used to instruction overvoltage logical signal V
err, overcurrent logical signal I
err, overheated logical signal T
errwith 4 tunnel driving malfunction logical signal D
err1,2,3,4.
Driving control unit is by human-computer interaction interface, connect through microprocessor, optical coupling isolation circuit AND OR NOT gate circuit, OR-NOT circuit exports and is divided into two-way, one tunnel connects dead-zone circuit, another road connects delay circuit, dead-zone circuit drives 1 to be connected with driving parallel port through transformer isolation, and delay circuit drives 2 to connect and compose with driving parallel port through transformer isolation.Error protection unit and the connected mode of driving control unit are connected with the OR-NOT circuit of driving control unit by the latch of error protection unit, and the transformer isolation of driving control unit drives the driving malfunction output of 1 to be 1. connected to form with the failure detector circuit of error protection unit.Human-computer interaction interface is made up of LCDs and button, arranges transmitter tranmitting frequency for artificial.Microprocessor is used for the drive control signal A and the B that the frequency order artificially arranged are converted to two-way respective frequencies.Optical coupling isolation circuit is used for microprocessor and rear class modulate circuit to isolate, and drive control signal A and B is output drive signal after optic coupling element isolation
with
with
be respectively the antilogical of A and B.OR-NOT circuit is used for the lump fault logic signals E exported by latch
errrespectively with drive singal
with
carry out NOR-logic computing, export output drive signal D
aand D
b.Dead-zone circuit is used for arranging drive singal D
aand D
brising edge time delay.Delay circuit is used for arranging drive singal D
aand D
brising edge and trailing edge time delay.Transformer isolation drives 1 to be made up of 4 tunnel transformer isolation drive circuits and 4 tunnel driving malfunction testing circuits, transformer isolation drive circuit is used for drived control logical signal to change into can the drive singal of Direct driver IGBT, and 4 tunnel driving malfunction testing circuits are respectively used to VT
11, VT
42, VT
22, VT
31collector and emitter between voltage V
cEcarry out input, work as VT
11, VT
42, VT
22, VT
31in the V of any switching tube
cEwhen exceeding setting protection threshold values; set low by the drive singal of respective switch pipe immediately, all set low by control drive singal A and B, driving malfunction output is simultaneously by output logic high level; when transformer isolation drive circuit normally works, driving malfunction output output low level.Transformer isolation drives 2 to be only made up of 4 tunnel transformer isolation drive circuits, not containing driving malfunction testing circuit, without driving malfunction output.
The wiring of main control unit 8 internal drive parallel port and transducer is connected with high-voltage inverted bridge road aviation plug through single shielded type cable by aviation plug.
The control method of frequency domain electro-prospecting exploration high pressure emitter, comprising:
Two-way drive control signal A anti-phase each other and B is exported, by the rising edge time delay Δ t of signal A by main control unit 8
1, obtain signal D
aOUT, D
aOUTdrive singal D is formed after isolation processing
rive11and D
rive42, D
rive11and D
rive42be respectively used to control VT
11and VT
42, by the rising edge of signal A and trailing edge time delay Δ t respectively
2with Δ t
3, obtain signal D
aIN, D
aINdrive singal D is formed after isolation processing
rive12and D
rive41, D
rive12and D
rive41be respectively used to control VT
12and VT
41, by the rising edge time delay Δ t of signal B
1, obtain signal D
bOUT, D
bOUTdrive singal D is formed after isolation processing
rive22and D
rive31, D
rive22and D
rive31be respectively used to control VT
22and VT
31, by the rising edge of signal B and trailing edge time delay Δ t respectively
2with Δ t
3, obtain signal D
bIN, D
bINdrive singal D is formed after isolation processing
rive21and D
rive32, D
rive21and D
rive32be respectively used to control VT
21and VT
32; Δ t
1> Δ t
2> Δ t
3; Switching tube VT in one-period
11, VT
12, VT
21, VT
22, VT
31, VT
32, VT
41and VT
42turn-on sequence is:
A.VT
12, VT
41conducting, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
B.VT
12, VT
41, VT
11, VT
42conducting, VT
21, VT
32, VT
22, VT
31turn off,
C.VT
12, VT
41conducting, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
D.VT
12, VT
41, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
E.VT
21, VT
32conducting, VT
12, VT
41, VT
11, VT
42, VT
22, VT
31turn off,
F.VT
21, VT
32, VT
22, VT
31conducting, VT
12, VT
41, VT
11, VT
42, turn off,
G.VT
21, VT
32conducting, VT
12, VT
41, VT
11, VT
42, VT
22, VT
31turn off,
H.VT
12, VT
41, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off.
The control method of frequency domain electro-prospecting exploration high pressure emitter, also comprises:
Respectively to VT
11, VT
42, VT
22, VT
31collector and emitter between voltage V
cEcarry out input, work as VT
11, VT
42, VT
22, VT
31in the V of any switching tube
cEwhen exceeding setting protection threshold values, immediately the drive singal of respective switch pipe is set low, control drive singal A and B is all set low; For VT
12, VT
41, VT
21, VT
32, all do not detect the voltage V between collector and emitter
cE, D
rive12and D
rive41only be controlled by drive singal A, D
rive21and D
rive32only be controlled by drive singal B; When there is overvoltage, overcurrent, overheating fault, control drive singal A and B is all set low.
The control method of frequency domain electro-prospecting exploration high pressure emitter is made a concrete analysis of below in conjunction with Fig. 3.
1) the waveform instruction inputted by the microprocessor recipient machine interactive interface of main control unit 8 inside, microprocessor sends two-way logical signal A and B anti-phase each other, and logical signal A and B exports anti-phase logical signal through optical coupling isolation circuit
with
2) drive by voltage analog signal V, the current analog signal I on current transformer and the temperature analog signal T on thermistor on the failure detector circuit one side real-time detection voltage transformer of main control unit 8 inside and transformer isolation the 4 tunnel driving malfunction logical signal D that in 1,1. driving malfunction output is gone up
error1,2,3,4; Compared with preset fault reference signal respectively by these signals on the other hand, when these signals are higher than fault reference signal, failure detector circuit exports corresponding high level overvoltage logical signal V
o, overcurrent logical signal I
o, overheated logical signal T
owith 4 tunnel driving malfunction logical signal D
o1,2,3,4.The overvoltage logical signal V of high level
o, overcurrent logical signal I
o, overheated logical signal T
owith 4 tunnel driving malfunction logical signal D
o1,2,3,4the fault logic signals V of high level is exported through latches
err, I
err, T
errand D
err1,2,3,4for fault display circuit indication fault, latch exports lump fault logic signals E simultaneously
errthe OR-NOT circuit of supply driving control unit, above-mentioned signal high level is effective, when initial condition and latch reset state, exports lump fault-signal E
errfor low level.
3) optical coupling isolation circuit output logic signal
with
respectively with lump fault logic signals E
errcommon input OR-NOT circuit, obtains output drive signal
wherein "+", "-" represents the "or" in logical operation respectively, NOT operation.Work as E
errduring for high level, D
a, D
bfor low level, it is invalid to drive; Work as E
errduring for low level, D
a, D
bconsistent with drive singal A, B, drive effectively, thus reach the object of error protection.
4) output drive signal D
aand D
brising edge time delay Δ t is produced respectively through dead-zone circuit
1signal D
aOUTand D
bOUT, D
aOUTand D
bOUTfor driving 4, the outside switching tube VT in high-voltage inverted bridge road (7)
11, VT
22, VT
31and VT
42, by D
aOUT1 is driven to export IGBT gate drive signal D through transformer isolation
rive11, D
rive42for driving VT
11and VT
42conducting and shutoff, by D
bOUT1 is driven to export IGBT gate drive signal D through transformer isolation
rive31, D
rive22for driving VT
31and VT
22conducting and shutoff.
5) output drive signal D
aand D
brising edge time delay Δ t is produced respectively through delay circuit
2decline time delay Δ t
3signal D
aIN, D
bINfor driving 4, the inside switching tube VT in high-voltage inverted bridge road 7
12, VT
21, VT
32and VT
41, by D
aIN2 are driven to export IGBT gate drive signal D through transformer isolation
rive12, D
rive41for driving VT
12and VT
41conducting and shutoff, by D
bIN2 are driven to export IGBT gate drive signal D through transformer isolation
rive21, D
rive32for driving VT
21and VT
32conducting and shutoff.
Delay time Δ t
1, Δ t
2with Δ t
3choose by emission maximum frequency f
maxand " the first conducting of internal switch pipe, conducting after external switch pipe; External switch pipe first turns off, and turns off after internal switch pipe " Controlling principle determine.Need: Δ t
1> Δ t
2> Δ t
3>0s, Δ t
1<1/ (2 × f
max).
High-voltage inverted bridge road 7 circuit turn-on state is made a concrete analysis of below in conjunction with the high-voltage inverted bridge road circuit turn-on state diagram of diode hoop position shown in drive control signal shown in Fig. 4 and bridge road output waveform sequential chart and Fig. 5.Symbol VT in following content
xx(D) anti-paralleled diode of IGBT is represented.In actual applications, because earth load induction reactance is large and drive dead band time delay short, high-voltage inverted bridge road 8 is usually operated at output current continuous print pattern.
As shown in Figure 4, t is supposed
0moment is the initial time that powers on, t
0moment drive singal D
afor high level, D
bfor low level, IGBT gate drive signal D
rive11, D
rive42, D
rive22, D
rive31, D
rive12, D
rive41, D
rive21and D
rive32it is all low level.
At t
0~ t
1period, due to IGBT gate drive signal D
rive11, D
rive42, D
rive22, D
rive31, D
rive12, D
rive41, D
rive21and D
rive32, be all low level, therefore high-voltage inverted bridge road 7 is without conducting loop, bridge road output voltage v
ofor 0V;
Signal D
athrough delay circuit rising edge time delay Δ t
2rear arrival t
1moment, now drive singal D
rive12, D
rive41be high level by low transition, IGBT switching tube VT
12and VT
41conducting, rest switch Guan Jun is in off state, therefore without conducting loop, bridge road output voltage v
ofor 0V, at t
1~ t
2period, circuit turn-on state as shown in Figure 5 a;
Signal D
athrough dead-zone circuit rising edge time delay Δ t
1after, arrive t
2moment, now drive singal D
rive11, D
rive42be high level by low transition, IGBT switching tube VT
11and VT
42conducting, now conducting loop is C
1→ VT
11→ VT
12→ load → VT
41→ VT
42→ C
3→ C
2→ C
1, bridge road output voltage v
ofor+3E, at t
2~ t
3period, circuit turn-on state as shown in Figure 5 b;
At t
3moment, signal D
alow level is converted to, now drive singal D by high level
rive11, D
rive42low level is converted to, IGBT switching tube VT by high level
11and VT
42turn off, now conducting loop is C
2→ D
1→ VT
12→ load → VT
41→ D
4→ C
2, bridge road output voltage v
ofor-E, at t
3~ t
4period, circuit turn-on state as shown in Figure 5 c;
Signal D
athrough delay circuit trailing edge time delay Δ t
3rear arrival t
4moment, now drive singal D
rive12, D
rive41low level is converted to, IGBT switching tube VT by high level
12and VT
41turn off, now conducting loop is C
3→ VT
22(D) → VT
21(D) → load → VT
32(D) → VT
31(D) → C
1→ C
2→ C
3, bridge road output voltage v
ofor-3E, at t
4~ t
5period, circuit turn-on state as fig 5d;
Signal D
bthrough delay circuit rising edge time delay Δ t
2rear arrival t
5moment, now drive singal D
rive21, D
rive32be high level by low transition, IGBT switching tube VT
21and VT
32conducting, now conducting loop is C
3→ VT
22(D) → VT
21(D) → load → VT
32(D) → VT
31(D) → C
1→ C
2→ C
3, bridge road output voltage v
ofor-3E, at t
5~ t
6period, circuit turn-on state as shown in Figure 9;
Signal D
bthrough dead-zone circuit rising edge time delay Δ t
1rear arrival t
6moment, now drive singal D
rive22, D
rive31be high level by low transition, IGBT switching tube VT
22and VT
31conducting, now conducting loop is C
3→ VT
22(D) → VT
21(D) → load → VT
32(D) → VT
31(D) → C
1→ C
2→ C
3, bridge road output voltage v
ofor-3E, at t
6~ t
7period, circuit turn-on state as shown in figure 5f;
At t
7in the moment, load inductance afterflow is complete, and load current starts reverse circulated, and now conducting loop is C
1→ VT
31→ VT
32→ load → VT
21→ VT
22→ C
3→ C
2→ C
1, bridge road output voltage v
ofor-3E, at t
7~ t
8period, circuit turn-on state as shown in fig. 5g;
At t
8moment, signal D
blow level is converted to, now drive singal D by high level
rive22, D
rive31low level is converted to, IGBT switching tube VT by high level
22and VT
31turn off, now conducting loop is C
2→ D
3→ VT
32→ load → VT
21→ D
2→ C
2, bridge road output voltage v
ofor+E, at t
8~ t
9period, circuit turn-on state as shown in figure 5h;
Signal D
bthrough delay circuit trailing edge time delay Δ t
3after, at t
9moment, now drive singal D
rive21, D
rive32low level is converted to, IGBT switching tube VT by high level
21and VT
32turn off, now conducting loop is C
1→ C
2→ C
3→ VT
42(D) → VT
41(D) → load → VT
12(D) → VT
11(D) → C
1, bridge road output voltage v
ofor+3E, at t
9~ t
10period, circuit turn-on state as shown in figure 5i;
Signal D
athrough delay circuit rising edge time delay Δ t
2after, at t
10moment, now drive singal D
rive12, D
rive41be high level by low transition, IGBT switching tube VT
12and VT
41conducting, now conducting loop is C
1→ C
2→ C
3→ VT
42(D) → VT
41(D) → load → VT
12(D) → VT
11(D) → C
1, bridge road output voltage v
ofor+3E, at t
10~ t
11period, circuit turn-on state as shown in figure 5j;
Signal D
athrough dead-zone circuit rising edge time delay Δ t
1after, at t
11moment, now drive singal D
rive11, D
rive42be high level by low transition, IGBT switching tube VT
11and VT
42conducting, now conducting loop is C
1→ C
2→ C
3→ VT
42(D) → VT
41(D) → load → VT
12(D) → VT
11(D) → C
1, bridge road output voltage v
ofor+3E, at t
11~ t
12period, circuit turn-on state as shown in figure 5k;
At t
12in the moment, load inductance afterflow is complete, and load current starts reverse circulated, and now conducting loop is C
1→ VT
11→ VT
12→ load → VT
41→ VT
42→ C
3→ C
2→ C
1, bridge road output voltage v
ofor+3E, at t
12~ t
13period, circuit turn-on state is as shown in Fig. 5 l;
From t
13moment plays repetition t
3moment working method, shown in Fig. 5 l, state is consistent with Fig. 5 b, shows that Fig. 5 b ~ Fig. 5 k is circuit turn-on circuit cycle figure when normally working.
In the course of work of above-mentioned bridge road, the current work on earth load 9 under continuous print pattern, high-voltage inverted bridge road 7 output voltage V
o+ 3E →-E →-3E →+E →+3E is changed in one-period, under identical bus input voltage, high-voltage inverted bridge road 7 three level sudden transformation within the half period exports relative to traditional H bridge two level has lower dv/dt, contributes to reducing insulation and impacts and electromagnetic interference.
In the course of work of high-voltage inverted bridge road 7, composition graphs 5 analysis can obtain, the maximum withstand voltage 2E that in high-voltage inverted bridge road 7, each switching tube and power diode bear in one-period, for 2/3 of input direct-current busbar voltage 3E, achieve the object completing High voltage output with the power power electronic device of low voltage withstand class.And traditional H bridge inverter, the voltage that every power switch pipe on bridge road bears is input direct-current busbar voltage 3E, although select the power power electronic device of higher voltage withstand class (as IGBT, MOSFET, diode) that high-voltage inverted object can be reached, but due to the self structure of power power electronic device and the restriction of technological level, the corresponding high conduction losses of higher withstand voltage power power electronic device and switching loss.Higher thermal losses also can cause more complicated heat dissipation problem simultaneously, uses larger heat abstractor to increase volume and the weight of instrument and equipment, causes great difficulty to field studies.Meanwhile, the cost that the power power electronic device of high voltage withstand class is corresponding higher, especially for the power power electronic device high-power emitter structure needing greater number, Cost Problems is particularly serious.So can loss be reduced with the power power electronic device of low voltage withstand class, reduce costs.
The control method adopted can make high-voltage inverted bridge road 7 avoid the conducting state shown in Fig. 6 and Fig. 7.Under operating state shown in Fig. 6 and Fig. 7, the voltage that switching tube bears can reach+3E, and the power power electronic device not reaching use+2E voltage withstand class realizes the object of+3E High voltage output.
The conducting state should avoided when composition graphs 6 analyzes high-voltage inverted bridge road conducting.The switching tube supposing the first conducting of initial time is VT
11and VT
42, then just make VT
12and VT
41conducting.Then switching tube VT
11and VT
42during conducting as shown in Figure 6 a; At VT
12and VT
41in the process of conducting, due to the difference of the individual manufacturing process of switching tube, the ON time of each switching tube and turn-off time is caused to be not quite similar, VT
12and VT
41can not simultaneously conducting, suppose VT
41first conducting, VT
12not yet conducting, as shown in Figure 6 b, now, switching tube VT
12whole busbar voltage 3E will be born in two ends before conducting, cause VT
12damage because of high-voltage breakdown.
Composition graphs 7 analyzes the conducting state should avoided when high-voltage inverted bridge road turns off.Suppose that the switching tube that initial time first turns off is VT
11and VT
42, then just make VT
12and VT
41turn off.Then initial time switching tube VT
11, VT
12, VT
41and VT
42during conducting as shown in Figure 7a; At VT
12and VT
41in the process turned off, due to the difference of the individual manufacturing process of switching tube, VT
12and VT
41can not turn off simultaneously, suppose VT
12first turn off, VT
41not yet turn off, as shown in Figure 7b, now, conducting loop is VT
22(D) → VT
21(D) → load → VT
41→ VT
42→ VT
22(D), switching tube VT
12whole busbar voltage 3E will be born after shut-off in two ends, cause VT
12damage because of high-voltage breakdown.
Therefore, in the control method that this patent proposes, the control method of " the first conducting of internal switch pipe; conducting after external switch pipe " is adopted when conducting, adopting the control method of " internal switch pipe first turns off; turn off after external switch pipe " when turning off, the conducting state shown in Fig. 6 and Fig. 7 can be avoided like this, making the withstand voltage of switching tube all be no more than+2E at any time.Internal switch pipe refers to VT
12, VT
21, VT
32and VT
41, external switch pipe refers to VT
11, VT
22, VT
31and VT
42.
Existing multi-level inverse conversion bridge road is as shown in Figure 10, Figure 11 and Figure 12, Figure 10 is equal electric pressure diode hoop bit-type inverter bridge road schematic diagram in prior art, Figure 11 is equal electric pressure electric capacity hoop bit-type inverter bridge road schematic diagram in prior art, and Figure 12 is equal electric pressure cascade connection type inverter bridge road schematic diagram in prior art.In existing multi-level inverse conversion bridge road, by using more power device to make output produce more level number, coordinating complicated control method, output can be made to approach sine-shaped staircase waveform, there is more low distortion and harmonic wave rate.This use multi-level inverse conversion bridge road exports the method for approaching sine-shaped staircase waveform and is widely used in electric power system and heavy motor drive.And in geophysical exploration, actual needs be fundamental frequency square-wave pulse signal, frequency domain electro-prospecting exploration emitter does not need output waveform to have more level number, only need control transmitter transmit square waves pulse signal.So under the prerequisite of identical input direct-current busbar voltage, the high-voltage inverted bridge road 7 shown in Fig. 2, compared with existing multi-level inverse conversion bridge road, has power device number low, the easy feature of control method.
High-voltage inverted bridge road 7 shown in Fig. 2 is at electric capacity C
1, C
2and C
3the each independently isolated DC stabilized voltage power supply in parallel in two ends, solve the problem of traditional multi-level inverter bridge road capacitor voltage equalizing.
Cascade connection type inverter bridge road shown in Figure 12, the modular method for designing of general employing, namely adopts the method for modular unit series connection, and each serial module structure unit comprises transmitting bridge and isolation stabilized voltage power supply.Cascaded inverter need carry out independently wiring to gang mould module unit at different levels and control, and causes wiring various, is subject to extraneous factor interference.Particularly when a certain cascade module unit generation driving malfunction (namely driving inefficacy, without drive singal), the turn on process of strong damaging will be caused.As shown in Figure 8, suppose the first order modular unit generation driving malfunction on top, other two-rank module unit output voltage summation will be added in malfunctioning module unit output, i.e. fault terminal voltage E
1=E
2+ E
3, causing trouble modular unit bridge road front end direct current stabilized voltage power supply is damaged because of output high pressure.In the present invention, the wiring of main control unit 8 internal drive parallel port and transducer is connected with high-voltage inverted bridge road aviation plug through single shielded type cable by aviation plug, if when there is the fault without drive singal, high-voltage inverted bridge road 7 does not work, and above-mentioned overvoltage fault state can not occur.Therefore it is low to have wiring complexity compared with cascade connection type inverter bridge road, failure rate is low, the advantage used under being adapted at field complex environment.
Claims (5)
1. a frequency domain electro-prospecting exploration high pressure emitter, it is characterized in that, be connected with the positive pole of earth load (9) with high-voltage inverted bridge road (7) through isolated DC stabilized voltage power supply I (4) by threephase alternator a (1), threephase alternator c (3) is connected with the negative pole of earth load (9) with high-voltage inverted bridge road (7) through isolated DC stabilized voltage power supply III (6), threephase alternator b (2) is connected with the negative pole of isolated DC stabilized voltage power supply I (4) through the positive pole of isolated DC stabilized voltage power supply II (5), the negative pole of isolated DC stabilized voltage power supply II (5) is connected with isolated DC stabilized voltage power supply III (6) positive pole, high-voltage inverted bridge road (7) and main control unit (8) connect and compose.
2. according to frequency domain electro-prospecting exploration high pressure emitter according to claim 1, it is characterized in that, main control unit (8) is by voltage transformer, current transformer and thermistor drive I to be connected through fault detect and transformer isolation respectively, reset key is connected with malfunction coefficient through latch, human-computer interaction interface is through microprocessor, optical coupling isolation circuit, OR-NOT circuit, dead crystal drive circuit, transformer isolation drives I, drive parallel port, transformer isolation drives II to be connected with delay circuit AND OR NOT gate circuit, fault detect connects and composes through latch AND OR NOT gate circuit.
3., according to frequency domain electro-prospecting exploration high pressure emitter according to claim 2, it is characterized in that, described transformer isolation drives I respectively to VT
11, VT
42, VT
22, VT
31collector and emitter between voltage V
cEcarry out input, work as VT
11, VT
42, VT
22, VT
31in the V of any switching tube
cEwhen exceeding setting protection threshold values, immediately the drive singal of respective switch pipe is set low, control drive singal A and B is all set low; For VT
12, VT
41, VT
21, VT
32, all do not detect the voltage V between collector and emitter
cE, D
rive12and D
rive41only be controlled by drive singal A, D
rive21and D
rive32only be controlled by drive singal B; When there is overvoltage, overcurrent, overheating fault, control drive singal A and B is all set low.
4., according to frequency domain electro-prospecting exploration high pressure emitter according to claim 1, it is characterized in that, high-voltage inverted bridge road (7) is by three electric capacity C
1, C
2and C
3, four diode D
1, D
2, D
3and D
4, eight switching tube VT
11, VT
12, VT
21, VT
22, VT
31, VT
32, VT
41and VT
42form; Electric capacity C
1positive pole hold with HH and be connected, electric capacity C
1negative pole hold with HL and be connected, electric capacity C
2positive pole hold with HL and be connected, electric capacity C
2negative pole hold with LH and be connected, electric capacity C
3positive pole hold with LH and be connected, electric capacity C
2negative pole hold with LL and be connected; VT
11collector electrode hold with HH and be connected, VT
11emitter and VT
12collector electrode connect, VT
12emitter and VT
21collector electrode be connected with output OUTA, VT
21emitter and VT
22collector electrode connect, VT
22emitter hold with LL and be connected, VT
31collector electrode hold with HH and be connected, VT
31emitter and VT
32collector electrode connect, VT
32emitter and VT
41collector electrode be connected with output OUTB, VT
41emitter and VT
42collector electrode connect, VT
42emitter hold with LL and be connected; D
1anode hold with LH and be connected, D
1negative electrode and VT
12collector electrode connect, D
2anode and VT
21emitter connect, D
2negative electrode hold with HL and be connected, D
3anode hold with LH and be connected, D
3negative electrode and VT
32collector electrode connect, D
4anode and VT
41emitter connect, D
4negative electrode and HL hold and connect and compose.
5. implement the claims a control method for the frequency domain electro-prospecting exploration high pressure emitter described in 1, it is characterized in that,
Two-way drive control signal A anti-phase each other and B is exported, by the rising edge time delay Δ t of signal A by main control unit (8)
1, obtain signal D
aOUT, D
aOUTdrive singal D is formed after isolation processing
rive11and D
rive42, D
rive11and D
rive42be respectively used to control VT
11and VT
42, by the rising edge of signal A and trailing edge time delay Δ t respectively
2with Δ t
3, obtain signal D
aIN, D
aINdrive singal D is formed after isolation processing
rive12and D
rive41, D
rive12and D
rive41be respectively used to control VT
12and VT
41, by the rising edge time delay Δ t of signal B
1, obtain signal D
bOUT, D
bOUTdrive singal D is formed after isolation processing
rive22and D
rive31, D
rive22and D
rive31be respectively used to control VT
22and VT
31, by the rising edge of signal B and trailing edge time delay Δ t respectively
2with Δ t
3, obtain signal D
bIN, D
bINdrive singal D is formed after isolation processing
rive21and D
rive32, D
rive21and D
rive32be respectively used to control VT
21and VT
32; Δ t
1> Δ t
2> Δ t
3; Switching tube VT in one-period
11, VT
12, VT
21, VT
22, VT
31, VT
32, VT
41and VT
42turn-on sequence is:
A.VT
12, VT
41conducting, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
B.VT
12, VT
41, VT
11, VT
42conducting, VT
21, VT
32, VT
22, VT
31turn off,
C.VT
12, VT
41conducting, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
D.VT
12, VT
41, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off,
E.VT
21, VT
32conducting, VT
12, VT
41, VT
11, VT
42, VT
22, VT
31turn off,
F.VT
21, VT
32, VT
22, VT
31conducting, VT
12, VT
41, VT
11, VT
42, turn off,
G.VT
21, VT
32conducting, VT
12, VT
41, VT
11, VT
42, VT
22, VT
31turn off,
H.VT
12, VT
41, VT
11, VT
42, VT
21, VT
32, VT
22, VT
31turn off.
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Cited By (2)
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| CN113447752A (en) * | 2021-09-01 | 2021-09-28 | 广东电网有限责任公司 | Dynamic and static integrated testing device and testing method for half-bridge type power module |
| WO2021208142A1 (en) * | 2020-04-16 | 2021-10-21 | 华为技术有限公司 | Power supply system |
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| CN103346675A (en) * | 2013-07-11 | 2013-10-09 | 北京工业大学 | High-power cascading electromagnetic emitter system with voltage continuously adjustable in wide range |
| CN103701354A (en) * | 2013-12-28 | 2014-04-02 | 吉林大学 | Electrical source transmitter device with self-adaption dummy load and control method |
| KR101425400B1 (en) * | 2013-08-29 | 2014-08-13 | 한국전력공사 | Power converter for high voltage direct current transmission |
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| US7230837B1 (en) * | 2006-03-27 | 2007-06-12 | North Carolina State University | Method and circuit for cascaded pulse width modulation |
| CN102299638A (en) * | 2011-07-29 | 2011-12-28 | 北京工业大学 | Large-power steady transmitting device with continuously adjustable voltage width range |
| CN103346675A (en) * | 2013-07-11 | 2013-10-09 | 北京工业大学 | High-power cascading electromagnetic emitter system with voltage continuously adjustable in wide range |
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| WO2021208142A1 (en) * | 2020-04-16 | 2021-10-21 | 华为技术有限公司 | Power supply system |
| CN113447752A (en) * | 2021-09-01 | 2021-09-28 | 广东电网有限责任公司 | Dynamic and static integrated testing device and testing method for half-bridge type power module |
| CN113447752B (en) * | 2021-09-01 | 2022-03-04 | 广东电网有限责任公司 | Dynamic and static integrated testing device and testing method for half-bridge type power module |
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| CN104393781B (en) | 2017-02-22 |
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