CN104124862A - High-PFC constant current control device without loop compensation and voltage converter - Google Patents
High-PFC constant current control device without loop compensation and voltage converter Download PDFInfo
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Abstract
The invention discloses a high-PFC constant current control device without loop compensation and a voltage converter. The device comprises an automatic gain controller, of which the input end is an AC input voltage sampling signal of a primary side voltage sampling network, and the output end outputs a signal which is the same and of the same frequency with the input voltage but constant in amplitude; a peak current control comparator which has positive and negative input ends and output ends, wherein the negative input end is connected with the output end of the automatic gain controller, and the positive input end is connected with the positive end of a primary side current sensor resistor; a clock signal generator, of which the input end is a DC voltage sampling signal of an auxiliary winding voltage sampling network and the output end outputs a clock signal, the frequency of which is in direct proportion to a DC sampling voltage; and a trigger which is used for receiving the clock signal and a comparison signal output by a peak circuit control comparator and controlling the connection or disconnection of a power switch tube based on the clock signal and the comparison signal. The constant current control device can realize high PFC and output constant-current control without light coupling and loop compensation.
Description
Technical field
The present invention relates to switch power technology field, relate in particular a kind of high PFC constant-current control device without loop compensation, it can be applicable to the buck-boost converter of isolated form inverse excitation type converter, non-isolation and the buck converter of non-isolation simultaneously.
Background technology
The light characteristic of LED is all described as the function of electric current conventionally, rather than the function of voltage, and the minor variations of LED forward voltage can cause larger LED curent change, thereby causes the larger variation of electric current.So, adopt drive of constant voltage source can not guarantee the consistency of LED brightness, and affect reliability, life-span and the light decay of LED.Therefore, LED adopts constant-current source to drive conventionally.
For the purpose of safety, a lot of LED light fixtures all requires LED driver to have isolation features, realizes the electrical isolation of output and electrical network input; In the application of middle low power (being less than 150W), inverse excitation type converter is the isolated converter being most widely used, and the most general feedback system is, by optocoupler, output is sampled FEEDBACK CONTROL at present.But because optocoupler exists problem of aging, therefore can affect the stability of circuit, also weakened the intensity of electrical isolation simultaneously.
On the other hand, the extensive use of power electronics causes severe contamination to public electric wire net, and reactive power comes into one's own day by day.In order to alleviate the extent of injury of electric pollution, the corresponding standard of the numerous and confused formulation of many countries, when power surpasses certain value (>5W), must meet High Power Factor (PF>0.9).Therefore the LED driver of relatively high power need to adopt power factor correction (Power Factor Correction is called for short PFC) technology, reaches high PFC.Wherein, alleged high PFC, refers to that power factor surpasses 0.9 in this application.
At present, the control mode of market is nearly all the loop control mode based on traditional switch power supply, under different frameworks, carry out the variation of some algorithms, but there is a common feature to need exactly loop compensation just can reach system stability, and for different application scenarios, such as different power, different peripheral frameworks, need different loop compensations, this has brought inconvenience to application.As shown in Figure 1, it is the schematic diagram of inverse-excitation type PFC constant-current control device in prior art, the core of this PFC constant-current control device is a constant current pfc controller, and this constant current pfc controller is arranged in the drive circuit of LED load, thereby plays the effect of high PFC and constant current control.
This drive circuit has rectification module, input capacitance Cin, original edge voltage sampling network R1, R2, transformer T, power switch pipe Q1, primary current inductive reactance R0, secondary rectifier diode D1, output capacitance Cout, output LED load L, auxiliary winding limit rectifier diode D2, auxiliary winding voltage sampling network R3, R4; In this constant current pfc controller, be provided with an independent compensation pin, can be used for an external building-out capacitor Ccomp, under different application conditions, the capacitance that need to adjust this building-out capacitor Ccomp reaches the stability of system; Certainly also there are indivedual designs not need loop compensation by control mode cleverly, but reduce because its specific control mode makes its versatility.
Except the difference of loop compensation, also have on the market single-stage and these two kinds of modes of two-stage to reach the constant-current system of high PFC, the design of two-stage control mode is comparatively simple, but efficiency is lower; The design of single-stage control mode is comparatively complicated, but efficiency is higher.
Therefore, studying a kind of general high PFC constant current of the inverse-excitation type single-stage without loop compensation control mode, is not only challenging work technically, has high integration, low cost, high efficiency, the realistic meaning of highly versatile simultaneously.
Summary of the invention
The object of the present invention is to provide a kind of high PFC constant-current control device without loop compensation, the form of its feedback element based on large-signal, removed the small-signal closed circuit of traditional form, and then do not needed, under loop compensation and the debugging of relevant loop stability, can to realize automatic stabilisation.
In order to reach above-mentioned purpose, solution of the present invention is:
A high PFC constant-current control device without loop compensation, wherein, comprising:
Automatic gain controller, input is the AC-input voltage sampled signal of original edge voltage sampling network, output is exported one with the same homophase frequently of input voltage but the signal of constant amplitude;
Peak current is controlled comparator, has positive input terminal, negative input end and output, and this negative input end is connected with the output of automatic gain controller, and positive input terminal is connected with the anode of primary current inductive reactance;
Clock-signal generator, input is the direct voltage sampled signal of auxiliary winding voltage sampling network, output is exported the clock signal that a frequency is directly proportional to direct current sampled voltage;
Trigger, compared with the comparison signal of device output, and comes unlatching or the shutoff of power ratio control switching tube for receive clock signal and peak value circuit control ratio based on clock signal and comparison signal.
Further, this automatic gain controller has the first operational amplifier, fixed resistance, variable resistor, counter and the first comparator, the positive input terminal of this first operational amplifier is connected with original edge voltage sampling network, the negative input end of this first operational amplifier by fixed resistance with power supply be connected, the negative input end of this first operational amplifier is also connected with the output of the first operational amplifier by variable resistor, the negative input end of this first comparator is connected with the output of the first operational amplifier, the positive input terminal of this first comparator is connected with the first normal voltage, the output of this first comparator is connected with the input of counter, the output of this counter is connected to regulate variable-resistance size with variable resistor.
Further, this clock-signal generator has the second operational amplifier, the second comparator, the first metal-oxide-semiconductor, the second metal-oxide-semiconductor, the 3rd metal-oxide-semiconductor, the 4th metal-oxide-semiconductor, the first electric capacity and the 7th resistance, the positive input terminal of this second operational amplifier is connected with auxiliary winding voltage sampling network, the output of this second operational amplifier is connected with the grid of the first metal-oxide-semiconductor, this first metal-oxide-semiconductor is also connected with the 7th resistance with the negative input end of the second operational amplifier, the 7th other one end of resistance with power supply be connected, this second metal-oxide-semiconductor and the 3rd metal-oxide-semiconductor form the mirror current source of 1:1, the output of this second comparator is clock end, the grid of the 4th metal-oxide-semiconductor is connected with the output of the second comparator, source electrode is connected with the positive input terminal of the second comparator, be connected drain electrode and power supply, the drain electrode of the 3rd metal-oxide-semiconductor by the first electric capacity with power supply be connected, the negative input end of this second comparator is connected with the second normal voltage.
Further, described trigger is rest-set flip-flop, has R end, S end and Q end, and this S end is connected with the output of clock-signal generator, the output that R end is controlled comparator with peak current is connected, and Q end is connected with the grid control end of power switch pipe and turn-offs with the unlatching of power ratio control switching tube.
The present invention also provides a kind of voltage changer, and it comprises according to the high PFC constant-current control device described in aforementioned any one, and
Rectification module, for receiving AC-input voltage, and carries out rectification to described AC-input voltage;
Original edge voltage sampling network, for the AC-input voltage of described rectification module institute rectification is sampled, to generate described AC-input voltage sampled signal;
Voltage transformation module, its AC-input voltage for being rectified described in receiving, and be connected in series with power switch pipe and primary current inductive reactance, described voltage transformation module provides output voltage to load under the control of described power switch pipe.
Further, described voltage transformation module is inverse-excitation type conversion module, and it comprises transformer, output diode and output capacitance.Transformer primary side anode is connected with bus VIN, and its negative terminal is connected with the leakage level of power tube; Transformer secondary anode is connected with LED negative terminal and output capacitance negative terminal, and its anode is connected with output diode anode, and output capacitance anode is connected with diode cathode; Transformer secondary side anode is connected with primary side the earth, and its negative terminal is connected with secondary side diode anode.
Further, described voltage transformation module is step-down/up type conversion module, and it comprises transformer, fly-wheel diode, booster diode and output capacitance.Transformer primary side anode is connected with bus VIN and output capacitance negative terminal, and its negative terminal is connected with power tube drain electrode and fly-wheel diode anode, and output capacitance anode is connected with diode cathode; Transformer secondary side anode is connected with the earth, and its negative terminal is connected with booster diode.
Adopt after said structure, the present invention relates to a kind of high PFC constant-current control device without loop compensation, it is by allowing automatic gain controller export one with the same homophase frequently of input voltage but the signal of constant amplitude, so guaranteed can there is same phase between voltage signal and current signal, and then guaranteed High Power Factor; By being set, peak current controls comparator, rest-set flip-flop and clock-signal generator simultaneously, and a clock signal that frequency is directly proportional to direct current sampled voltage of enable clock signal generator output, so can form a constant-current source.
Compared with prior art, advantage of the present invention is: the present invention, without light even summation loop compensation, can realize high PFC and output constant current simultaneously and control, and system stability; Because the present invention adopts single-stage control mode, reduce peripheral component simultaneously, provided cost savings and space, reached the object of miniaturization; In addition, the principle highly versatile of invention, is not only applicable to inverse excitation type converter, also applicable to buck-boost converter and buck converter.
Accompanying drawing explanation
Fig. 1 is the schematic diagram of inverse-excitation type PFC constant-current control device of the prior art;
Fig. 2 is the circuit diagram of the high PFC constant-current control device of the inverse-excitation type of one embodiment of the invention;
Fig. 3 is the circuit diagram of automatic gain controller specific embodiment in Fig. 2;
Fig. 4 is the circuit diagram of clock-signal generator specific embodiment in Fig. 2;
The schematic diagram that Fig. 5 is AC-input voltage, power switch pipe control signal, primary side electric current and the secondary side current waveform described based on control mode of the present invention;
Fig. 6 is the circuit diagram that the present invention is applied to the buck-boost converter of non-isolation.
In figure:
Inverse excitation type converter 100 bridge rectifier modules 1
High PFC constant-current control device 2 automatic gain controllers 21
Counter 211 peak currents are controlled comparator 22
Clock-signal generator 23 rest-set flip-flops 24.
Embodiment
In order further to explain technical scheme of the present invention, below by specific embodiment, the present invention will be described in detail.
As shown in Figure 2, it is to the present invention relates to a kind of high PFC constant-current control device 2 without loop compensation to be applied in the schematic diagram in inverse excitation type converter 100, this inverse excitation type converter 100 comprises bridge rectifier module 1, input capacitance Cin, transformer T, power switch pipe Q1, primary current inductive reactance R0, original edge voltage sampling resistor network R1, R2, secondary rectifier diode D1, output capacitance Cout, output LED load, auxiliary winding limit rectifier diode D2, auxiliary winding voltage sampling network R3, R4, Caux.
The high PFC constant-current control device 2 without loop compensation the present invention relates to, comprises automatic gain controller 21, peak current control comparator 22, clock-signal generator 23 and rest-set flip-flop 24.
The input of this automatic gain controller 21 is the AC-input voltage sampled signal of original edge voltage sampling network, and in the present embodiment, this automatic gain controller 21 is connected with original edge voltage sampling network, and the voltage of its tie point is
, wherein
,
scope be <
v ~
v>; Suppose R1, R2 is set in a suitable ratio, makes Vsine meet following formula:
, wherein
scope be <0.5V ~ 1.56V>.
The output of this automatic gain controller 21 is exported one with the same homophase frequently of input voltage but the signal of constant amplitude, as shown in Figure 3, it is a kind of embodiment of this automatic gain controller 21, this automatic gain controller 21 has the first operational amplifier OP1, fixed resistance R5, variable resistor R6, counter 211 and the first comparator C MP1, the positive input terminal of this first operational amplifier OP1 is connected with original edge voltage sampling network, its input signal is Vsine, the negative input end of this first operational amplifier OP1 by fixed resistance R5 with power supply be connected, the negative input end of this first operational amplifier OP1 is also connected with the output of the first operational amplifier OP1 by variable resistor R6, the negative input end of this first comparator C MP1 is connected with the output of the first operational amplifier OP1, the positive input terminal of this first comparator C MP1 is connected with the first normal voltage Vref1, the output of this first comparator C MP1 is connected with the input of counter 211, the output of this counter 211 is connected to regulate the size of variable resistor R6 with variable resistor R6, the output of this first operational amplifier OP1 is the output of automatic gain controller 21, its output voltage is Vs_out.
" empty short void is disconnected " characteristic from the first operational amplifier:
In the present embodiment, this variable resistor R6 is a N+1 position digital signal d
0d
1d
nthe variable resistor of controlling, works as <d
0d
1d
n>=0 hour, R6=0; Work as <d
0d
1d
n>=<11 ... when 1> is maximum, R6 is maximum.In the starting stage, R6 is zero, and gain (R5+R6)/R6 is minimum, is unit 1.Then by the first comparator C MP1, constantly compare
peak value and
, export a control signal, the operating state of control counter 211, when the output signal of the first comparator C MP1 is while being high, counter 211 constantly increases the result of counting; When low level appears in the output signal of the first comparator C MP1, counter 211 stops counting and keeping count results at that time.Like this, by constantly adjusting <d0d1 ... the value of dN>, and constantly adjust R6, and then constantly adjust gain (R5+R6)/R6, make final
peak value equal
just reach stable, obtain
; So far, the negative input end that peak current is controlled comparator 22 will obtain one and input sinusoidal voltage with homophase frequently, and peak value is constant is
signal.
When power switch pipe Q1 opens, the inductive current by primary side constantly rises, and node voltage constantly raises, when reaching
certain when a bit, peak current is controlled comparator 22 upsets, the R end of rest-set flip-flop 24 transfers ' 1 ', Q end output ' 0 ', switch-off power switching tube Q1 to from ' 0 '.
This peak current is controlled comparator 22 and is had positive input terminal, negative input end and output, and this negative input end is connected with the output of automatic gain controller 21, and positive input terminal is connected with the anode of primary current inductive reactance.
The input of this clock-signal generator 23 is the direct voltage sampled signal of auxiliary winding voltage sampling network, and the output of this clock-signal generator 23 is exported the clock signal that a frequency is directly proportional to direct current sampled voltage, as shown in Figure 4, it is a kind of specific embodiment of this clock-signal generator 23, this clock-signal generator 23 has the second operational amplifier OP2, the second comparator C MP2, the first metal-oxide-semiconductor M1, the second metal-oxide-semiconductor M2, the 3rd metal-oxide-semiconductor M3, the 4th metal-oxide-semiconductor M4, the first capacitor C 1 and the 7th resistance R 7, the positive input terminal of this second operational amplifier OP2 is connected with auxiliary winding voltage sampling network, obtain FB signal, the output of this second operational amplifier OP2 is connected with the grid of the first metal-oxide-semiconductor M1, this first metal-oxide-semiconductor M1 is also connected with the 7th resistance R 7 with the negative input end of the second operational amplifier OP2, the 7th other one end of resistance R 7 with power supply be connected, this the second metal-oxide-semiconductor M2 and the 3rd metal-oxide-semiconductor M3 form the mirror current source of 1:1, the output of this second comparator C MP2 is clock end Clock, the grid of the 4th metal-oxide-semiconductor M4 is connected with the output of the second comparator C MP2, source electrode is connected with the positive input terminal of the second comparator C MP2, be connected drain electrode and power supply, the drain electrode of the 3rd metal-oxide-semiconductor M3 by the first capacitor C 1 with power supply be connected, the negative input end of this second comparator C MP2 is connected with the second normal voltage Vref2.
As shown in Figure 2, FB signal is from the dividing potential drop of auxiliary winding
, wherein
the voltage that secondary winding reflexes to auxiliary winding
, wherein
respectively the coil number of secondary winding and auxiliary winding, because
very little, negligible, so comprehensive 2 formulas above can obtain:
.
Please again consult shown in Fig. 4, this second operational amplifier OP2 is adjusted to the upper end of the 7th resistance R 7 with FB and equates by negative feedback, is so
, then according to basic charge balance formula C*U=I*t, the frequency that can obtain CLK is:
wherein,
.
This clock signal clk is received the S end of rest-set flip-flop 24, and when the high level of this CLK signal arrives, Q end transfers ' 1 ' to, unlatching power tube Q1 from ' 0 '.
This rest-set flip-flop 24 has R end, S end and Q end, this S end is connected with the output of clock-signal generator 23, the output that R end is controlled comparator 22 with peak current is connected, and Q end is connected with the grid control end of power switch pipe and turn-offs with the unlatching of power ratio control switching tube.Be appreciated that rest-set flip-flop 24 also can alternatively be used the trigger of other types, for example JK flip-flop according to the difference of concrete application
For rest-set flip-flop 24, its state conversion is as follows:
S=1, R=0, Q=1, clk cycle is started by rising edge, and power switch pipe Q1 opens;
S=0, R=0, Q=1, CLK transfers low level to by high level, but system still keeps power switch pipe Q1 to open;
S=0, R=1, Q=0, CLK still keeps low level, and comparator 212 outputs transfer high level to by low level, and power switch pipe Q1 closes;
S=0, R=0, Q=0, CLK still keeps low level, and comparator 212 outputs transfer low level again to, and power switch pipe Q1 keeps closing;
S=1, R=0, Q=1, repeats above process circulation.
According to above operation principle, can depict the system works waveform of Fig. 5; In addition, based on above-mentioned statement, can derive the present invention and there is following beneficial effect:
First: primary side current waveform is exactly input current, and it presents sine and covers form, with frequency homophase, with this, reached the requirement of high PFC with inlet highway voltage waveform, wherein the peak current of any point meets the following conditions:
, wherein N represents a civil power cycle
the number of the system duty cycle T inside comprising, n is the natural number between 1 to N.
Second: output current is constant current state:
Input power Pin is equivalent to a complete sinusoidal period
interior input energy:
Wherein
for the equivalent inductance of transformer T primary side,
for system works frequency,
be the current maxima that in a sinusoidal period, primary side flows through, equal
.
By the conservation of energy, can obtain input power and equal power output Pin=Pout;
can obtain:
Bring the expression formula of frequency f into above formula again, can obtain
；
Wherein
,
,
,
,
,
,
,
being the preset parameter of peripheral cell, is a fixed value; Wherein,
,
,
the parameter that internal circuit is controlled,
being preset parameter, is certain value; Obtain similar
,
constant like this reference voltage.
So can see that the expression formula of output current is certain value, reached the effect of constant current, by pushing over of constant current expression formula above, can see that current constant mode of the present invention does not need light occasionally or the compensation of any type of loop stability, thereby have without light even summation loop compensation, can realize the effect that high PFC and output constant current are controlled simultaneously.
The the 3rd: control mode of the present invention is simple and clear, versatility is very strong, is not only applicable to inverse excitation type converter 100, is applicable to too buck-boost converter.Fig. 6 shows and this control device is applied to the circuit diagram of the buck-boost converter of non-isolation according to the embodiment of the present invention.
Specifically please refer to shown in Fig. 6, it also comprises automatic gain controller 21, peak current control comparator 22, clock-signal generator 23 and rest-set flip-flop 24.
Buck-boost converter and inverse excitation type converter have a maximum identical point to be exactly, and primary side inductance energy when input power can be equivalent to power tube unlatching is completely comprehensive, and under the discontinuous condition of inductive current, input power still meets following expression:
By the conservation of energy, can obtain input power and equal power output Pin=Pout;
can obtain:
The expression formula of frequency f becomes simultaneously:
the expression formula of f being brought into Iout can obtain following expression
Wherein
,
,
,
,
,
being the preset parameter of peripheral cell, is a fixed value; Wherein,
,
,
the parameter that internal circuit is controlled,
being preset parameter, is certain value; Obtain similar
,
constant like this reference voltage.So can see that the expression formula of output current is certain value, has reached the effect of constant current.
In sum, the present invention relates to a kind of high PFC constant-current control device 2 without loop compensation, it is by allowing automatic gain controller 21 export one with the same homophase frequently of input voltage but the signal of constant amplitude, so guaranteed can there is same phase between voltage signal and current signal, and then guaranteed High Power Factor; By being set, peak current controls comparator 22, rest-set flip-flop 24 and clock-signal generator 23 simultaneously, and a clock signal that frequency is directly proportional to direct current sampled voltage of enable clock signal generator 23 outputs, so can form a constant-current source.
Compared with prior art, advantage of the present invention is: the present invention, without light even summation loop compensation, can realize high PFC and output constant current simultaneously and control, and system stability; Because the present invention adopts single-stage control mode, reduce peripheral component simultaneously, provided cost savings and space, reached the object of miniaturization; In addition, the principle highly versatile of invention, is not only applicable to inverse excitation type converter, also applicable to buck-boost converter.It will be understood by those skilled in the art that constant-current control device of the present invention can also be applied to the voltage changer of other types, for example buck converter.
Above-described embodiment and graphic and non-limiting product form of the present invention and style, suitable variation or modification that any person of an ordinary skill in the technical field does it, all should be considered as not departing from patent category of the present invention.
Claims (7)
1. without a high PFC constant-current control device for loop compensation, it is characterized in that, comprising:
Automatic gain controller, input is the AC-input voltage sampled signal of original edge voltage sampling network, output is exported one with the same homophase frequently of input voltage but the signal of constant amplitude;
Peak current is controlled comparator, has positive input terminal, negative input end and output, and this negative input end is connected with the output of automatic gain controller, and positive input terminal is connected with the anode of primary current inductive reactance;
Clock-signal generator, input is the direct voltage sampled signal of auxiliary winding voltage sampling network, output is exported the clock signal that a frequency is directly proportional to direct current sampled voltage;
Trigger, compared with the comparison signal of device output, and comes unlatching or the shutoff of power ratio control switching tube for receive clock signal and peak value circuit control ratio based on clock signal and comparison signal.
2. the high PFC constant-current control device without loop compensation as claimed in claim 1, it is characterized in that, this automatic gain controller has the first operational amplifier, fixed resistance, variable resistor, counter and the first comparator, the positive input terminal of this first operational amplifier is connected with original edge voltage sampling network, the negative input end of this first operational amplifier by fixed resistance with power supply be connected, the negative input end of this first operational amplifier is also connected with the output of the first operational amplifier by variable resistor, the negative input end of this first comparator is connected with the output of the first operational amplifier, the positive input terminal of this first comparator is connected with the first normal voltage, the output of this first comparator is connected with the input of counter, the output of this counter is connected to regulate variable-resistance size with variable resistor.
3. the high PFC constant-current control device without loop compensation as claimed in claim 1, it is characterized in that, this clock-signal generator has the second operational amplifier, the second comparator, the first metal-oxide-semiconductor, the second metal-oxide-semiconductor, the 3rd metal-oxide-semiconductor, the 4th metal-oxide-semiconductor, the first electric capacity and the 7th resistance, the positive input terminal of this second operational amplifier is connected with auxiliary winding voltage sampling network, the output of this second operational amplifier is connected with the grid of the first metal-oxide-semiconductor, this first metal-oxide-semiconductor is also connected with the 7th resistance with the negative input end of the second operational amplifier, the 7th other one end of resistance with power supply be connected, this second metal-oxide-semiconductor and the 3rd metal-oxide-semiconductor form the mirror current source of 1:1, the output of this second comparator is clock end, the grid of the 4th metal-oxide-semiconductor is connected with the output of the second comparator, source electrode is connected with the positive input terminal of the second comparator, be connected drain electrode and power supply, the drain electrode of the 3rd metal-oxide-semiconductor by the first electric capacity with power supply be connected, the negative input end of this second comparator is connected with the second normal voltage.
4. the high PFC constant-current control device without loop compensation as claimed in claim 1, it is characterized in that, described trigger is rest-set flip-flop, there is R end, S end and Q end, this S end is connected with the output of clock-signal generator, the output that R end is controlled comparator with peak current is connected, and Q end is connected with the grid control end of power switch pipe and turn-offs with the unlatching of power ratio control switching tube.
5. a voltage changer, comprises according to the high PFC constant-current control device described in any one in claim 1-4, and
Rectification module, for receiving AC-input voltage, and carries out rectification to described AC-input voltage;
Original edge voltage sampling network, for the AC-input voltage of described rectification module institute rectification is sampled, to generate described AC-input voltage sampled signal;
Voltage transformation module, its AC-input voltage for being rectified described in receiving, and be connected in series with power switch pipe and primary current inductive reactance, described voltage transformation module provides output voltage to load under the control of described power switch pipe.
6. voltage changer according to claim 5, is characterized in that, described voltage transformation module is inverse-excitation type conversion module, it comprises transformer, output diode and output capacitance, wherein, transformer primary side anode is connected with bus, and its negative terminal is connected with the leakage level of power tube; Transformer secondary anode is connected with LED negative terminal and output capacitance negative terminal, and its anode is connected with output diode anode, and output capacitance anode is connected with diode cathode; Transformer secondary side anode is connected with primary side the earth, and its negative terminal is connected with secondary side diode anode.
7. voltage changer according to claim 5, it is characterized in that, described voltage transformation module is step-down/up type conversion module, it comprises transformer, fly-wheel diode, booster diode and output capacitance, wherein, transformer primary side anode is connected with bus and output capacitance negative terminal, and its negative terminal is connected with power tube drain electrode and fly-wheel diode anode, and output capacitance anode is connected with diode cathode; Transformer secondary side anode is connected with the earth, and its negative terminal is connected with booster diode.
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| CN107357348A (en) * | 2017-07-19 | 2017-11-17 | 中国科学院上海高等研究院 | A kind of AC signal amplitude accurate control circuit and method |
| CN107608443A (en) * | 2017-10-16 | 2018-01-19 | 中国科学院上海高等研究院 | A kind of AC signal amplitude accurate control circuit and method |
| CN110045174A (en) * | 2019-05-24 | 2019-07-23 | 南京酷科电子科技有限公司 | A kind of current sampling circuit |
| CN110994991A (en) * | 2019-12-17 | 2020-04-10 | 华南理工大学 | Loop-free digital control method for isolated Buck-Boost circuit |
| CN113794368A (en) * | 2021-09-14 | 2021-12-14 | 珠海格力电器股份有限公司 | Flyback switching power supply control device and method and flyback switching power supply |
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| CN107608443B (en) * | 2017-10-16 | 2019-03-12 | 中国科学院上海高等研究院 | A kind of AC signal amplitude accurate control circuit and method |
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| CN110994991A (en) * | 2019-12-17 | 2020-04-10 | 华南理工大学 | Loop-free digital control method for isolated Buck-Boost circuit |
| CN110994991B (en) * | 2019-12-17 | 2021-05-14 | 华南理工大学 | Loop-free digital control method for isolated Buck-Boost circuit |
| CN113794368A (en) * | 2021-09-14 | 2021-12-14 | 珠海格力电器股份有限公司 | Flyback switching power supply control device and method and flyback switching power supply |
| CN113794368B (en) * | 2021-09-14 | 2023-10-27 | 珠海格力电器股份有限公司 | Control device and method of flyback switching power supply and flyback switching power supply |
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