CN104092468B - LDPC linear programming decoding method based on acceleration alternating direction multiplier method - Google Patents
LDPC linear programming decoding method based on acceleration alternating direction multiplier method Download PDFInfo
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Abstract
The invention discloses an LDPC linear programming decoding method based on an acceleration alternating direction multiplier method. The LDPC linear programming decoding method mainly solves the problems that an existing message class transmission algorithm has the error floor and can be easily influenced by a short link. According to the technical scheme, the LDPC linear programming decoding method comprises the steps that first, decoding parameters are initialized; second, iteration updating is carried out on an auxiliary vector, a solution vector and a Lagrangian multiplier vector in the decoding parameters in sequence; third, acceleration processing is carried out to correct the solution vector and the Lagrangian multiplier vector; fourth, according to the corrected solution vector, infinite norms of vectors corresponding to all check nodes are calculated, and the maximum infinite norm is worked out; fifth, whether the decoding process ends or not is judged according to the obtained maximum value and the number of times of iteration; sixth, the solution vector processed through the last time of iteration is output to serve as a decoded code word. The LDPC linear programming decoding method is high in convergence rate and free of the error floor, efficiency of a decoding module in a communication system can be remarkably improved, and the LDPC linear programming decoding method is applicable to the technical field of communication.
Description
Technical field
The invention belongs to communication technical field, particularly to a kind of interpretation method to low-density checksum LDPC code,
Can be used for fiber optic communication, magnetic storage, satellite digital video and audio frequency broadcast world.
Background technology
Low density parity check code LDPC has the characteristics that check matrix is sparse, therefore flexible structure, and decoding complexity is low,
There is the superperformance approaching shannon limit, be widely used in modern communicationses field, such as deep space communication, fiber optic communication etc., and quilt
Various Modern communication standards are adopted, and such as 802.11n, 802.16e, 10GBASE-T etc., are that field of channel coding attracts people's attention in recent years
Study hotspot.
At present, widely used interpretation method is mainly message transmission class algorithm, such as belief propagation (Belief
Propagation, BP) etc..Although such method has realizes simple, the more low advantage of decoding complexity, exist and be easily subject to
The shortcomings of becate affects, there is error floor, is difficult to mathematical analyses.LDPC code linear gauge based on alternating direction multiplier method ADMM
Draw interpretation method to pass through to introduce auxiliary variable, devise and new be applied to LDPC code linear programming problem method for solving, effectively
The shortcoming overcoming above-mentioned message transmission class algorithm.And, the interpretation method based on alternating direction multiplier method ADMM can also be abundant
Using the sparse characteristic of LDPC check matrix, and there is maximum likelihood authentication feature.But traditional is linear based on ADMM
It is required for executing the Euclid's project taking in a large number in the planning each iteration of interpretation method, and convergence rate is slower, because
And when being applied to larger LDPC, decoding efficiency is not high.
Content of the invention
It is an object of the invention to the deficiency to above-mentioned prior art, propose a kind of based on accelerating alternating direction multiplier method
LDPC code linear programming interpretation method, to reduce the multiple complexity of the time in decoding iteration, improves decoding efficiency.
Realizing the object of the invention technical scheme is:On the basis of original decoding technique, by introducing accelerating module and changing
Become the renewal order of augmentation Lagrangian decomposition formula, reduce decoding iteration number of times, and avoid multiple euclidean in each iteration
Projection calculates, thus improving decoding speed.Its concrete steps includes as follows:
(1) decoding initialization:
1a) binary system LDPC code C for n to code length, under additive white Gaussian noise channel, message r according to receiving obtains
Obtain the coefficient gamma of linear programming object functioni=log (Pr (ri|ci=0)/Pr (ri|ci=1)), i ∈ { 1,2 ..., n }, wherein,
ciRepresent the symbol sending, Pr () represents the event occurrence rate representing in bracket;
1b) according to coefficient gammaiBy piecewise function Obtain initial solution x decoding;
1c) setting accelerated factor α=1, auxiliary solution vectorIterationses k=0, setting iteration maximum times N, appearance
Difference ε, to each check-node j ∈ J, arranges Lagrange multiplier yj, auxiliary Lagrange multiplier vectorAuxiliary vector zj、
Transmission information Lj→iIt is null vector and length is dj, wherein, J is LDPC code check-node indexed set, djIt is check-node j institute
The number of verification variable node;
(2) Lagrange multiplier according to kth time iterationConciliate vector xk, calculate the auxiliary vector of+1 iteration of kth
zj:
Wherein, TjIt is the transition matrix being generated by check-node j,It is to be d by lengthjAnd all 0-1 containing even number 1
The many cell spaces of verification that vector is constituted,Represent vectorTo the many cell spaces of verificationEurope several in
Obtain project, auxiliary vectorWith Lagrange multiplier vectorContained element number is dj, and storage verification section successively
The respective value of the variable node that point j is verified;
(3) according to auxiliary vectorWith Lagrange multiplier vectorCalculate the check-node j transmission of+1 iteration of kth
Information to variable node i
Wherein, NcThe indexed set of j variable node that () is verified by check-node j,WithRespectively represent kth+
1 iteration auxiliary vectorWith kth time iteration Lagrange multiplier vectorThe corresponding value of middle variable node i;
(4) update+1 iterative solution vector x of kthk+1The value of middle all elements;
(5) to all check-node j ∈ J, according to solution vector xk+1Update the Lagrange multiplier vector of+1 iteration of kth
(6) pass through accelerated factor αk+1Revise solution vector xk+1With Lagrange multiplier vector
6a) calculate the accelerated factor of+1 iteration of kth
6b) according to accelerated factor αk+1, first calculate the auxiliary solution vector of+1 iteration of kthUpdate solution vector again
6c) to all of check-node j ∈ J, first calculate the auxiliary Lagrange multiplier vector of+1 iteration of kthUpdate the Ge Lang multiplier vector of+1 iteration of kth again
(7) judge whether iterationses k+1 reaches iteration maximum times N, if reaching, decoding terminates, kth is changed for+1 time
For solution vector xk+1Export as translating code word, otherwise execution step (8);
(8) according to solution vector xk+1And auxiliary variableVector is calculated to each check-node j ∈ J's
Infinite NormObtain maximum therein, if this maximum be less than tolerance ε; decode and terminate, by solution to
Amount xk+1Export as a result, otherwise k goes to step (2) after increasing 1.
The present invention decodes problem using the linear programming solving LDPC code based on alternating direction multiplier method, new by design
More new regulation and introduce accelerate process operation, compared with traditional decoding based on alternating direction multiplier method, both decreased consumption
When Euclid's project accelerate the convergence rate of iteration again, thus significantly reducing the time used by decoding, improve
The decoding efficiency of communication system or storage system.
Brief description
Fig. 1 be the present invention realize general flow chart;
Fig. 2 is the acceleration process sub-process figure revising solution vector and Lagrange multiplier in the present invention;
Fig. 3 is the decoding simulation performance figure with the present invention to Margulis LDPC code.
Specific embodiment
The realization of the present invention is to be carried out based on the linear programming Decoding model that alternating direction multiplier method solves, and specifically describes
As follows:
It is the LDPC code of n to a length, code word receive information after additive white Gaussian noise channel is vectorial r=
{r1,r2,…,rn, calculate log-likelihood ratioI ∈ { 1,2 ..., n }, wherein, ciRepresent and send
Symbol, Pr () represent bracket in represent event occurrence rate.
By log-likelihood ratio γiAs objective function coefhcient, linear programming Decoding model can be described as:
Wherein, vector x={ x1,x2,…,xnRepresenting the solution vector decoding, J is LDPC code check-node indexed set, djIt is
The number of the verified variable node of check-node j, zjBe length be djAuxiliary vector,It is to be d by lengthjAnd all containing idol
The many cell spaces of verification that several 1 0-1 vector is constituted.Transition matrix TjGenerated by check-node j, such as check matrix
Jth row hj={ 0,1,0,1,0,1,0 }, then homography is
The augmented Lagrangian of applying alternating direction multiplier method solve corresponding with above-mentioned linear programming model is writeable
For:
Wherein, ρ is penalty factor, yjIt is d for lengthjGlug bright sub- multiplier vector, symbol | | | |2Represent 2- norm
Computing.
With reference to Fig. 1, the present invention is implemented as follows:
Step 1, decoding initialization.
Decoding needs to arrange following auxiliary variable and auxiliary vector and carry out initialization operation to it:Setting accelerated factor
α=1, auxiliary solution vectorIterationses k=0, setting iteration maximum times N, tolerance ε, to each check-node j ∈
J, arranges Lagrange multiplier yj, auxiliary Lagrange multiplier vectorAuxiliary vector zj, transmission information Lj→iBe null vector and
Length is dj, the initial value of solution vector x is by piecewise function It is calculated, γiRepresent log-likelihood ratio.
Step 2, updates auxiliary vector zjValue.
To all of check-node j ∈ J, according to the Lagrange multiplier of kth time iterationConciliate vector xk, calculating kth+
The auxiliary vector of 1 iteration
Wherein, TjIt is the transition matrix being generated by check-node j, symbolRepresent a vector to the many born of the same parents of verification
BodyUpper Euclid's projection, implementing of this project can refer to document " Efficient iterative LP
decoding of LDPC codes with alternating direction method of multipliers”【IEEE
International Symposium of Information Theory.Jul.2013】.
Step 3, the message of the variable node i that check-node j is verified to it when calculating+1 iteration of kth:
Wherein, NcThe indexed set of j variable node that () is verified by check-node j,WithRepresent auxiliary respectively
VectorWith Lagrange multiplier vectorThe corresponding value of middle variable node i.
Step 4, the transmission message obtaining according to step 3With log-likelihood ratio γi, when calculating renewal+1 iteration of kth
All variable nodesValue:
Wherein, I is LDPC code variable node indexed set, diRepresent the check-node number of verification variable node i, NvI () is
The check-node indexed set of all verification variable node i, symbol Π[0,1]() represents Europe in interval [0,1] for the scalar
Project is obtained, the value after the project when the value of this scalar is more than 1 is 1, the projection when the value of this scalar is less than 0 is transported in several
Value after calculation is 0, and the value after value project when interval [0,1] of scalar is constant.The optimal value of penalty factor ρ can be by imitative
True experiment obtains, and its value is generally the constant in interval [2,5].
Step 5, updates the value of the Lagrange multiplier vector of+1 iteration of kth:
Wherein, vectorAnd auxiliary vectorContained element number, transition matrix TjLine number be check-node j institute
The variable node number d of verificationj.
Step 6, by accelerated factor αk+1Revise solution vector xk+1With Lagrange multiplier vector
With reference to Fig. 2, the realization of this step is as follows:
6a) update accelerated factor α of+1 iteration of kthk+1For
6b) according to accelerated factor αk+1, first calculate auxiliary solution vectorUpdate kth+1 again
The solution vector of secondary iteration
6c) to all of check-node j ∈ J, first calculate the auxiliary Lagrange multiplier vector of+1 iteration of kthUpdate the Ge Lang multiplier vector of+1 iteration of kth again
Step 7, decoding terminates to judge.
7a) judge whether to reach iteration maximum times N, if reaching, decoding terminates, and exports solution vector xk+1As transmission
Information is corresponding to translate code word, otherwise, execution step (7b);
7b) vector is calculated to each check-node j ∈ JInfinite NormAnd obtain
Maximum therein is designated asThis maximum is compared with tolerance ε:IfThen decoding terminates and exports solution vector xk+1As sending code word, otherwise, k returns step after increasing 1
Rapid 2.
The effect of the present invention can be further illustrated by following emulation:
1. simulated conditions
The modulation system of emulation is BPSK, and channel is additive white Gaussian noise awgn channel.
The code that emulation adopts is Margulis LDPC code, and it is (2640,1320) regular code, and code check isIts row is again
6, row are 3 again.
Emulation setting tolerance ε is 10-5, penalty factor ρ be 5, maximum iteration time N is set to 60,200,600.
2. emulation content
Under Gaussian channel, respectively with the interpretation method pair of existing BP interpretation method, ALP interpretation method and the present invention
The Margulis LDPC code error-correcting performance of code check is emulated, and result is as shown in figure 3, in figure gives 5 curves, wherein:
Represent under additive white Gaussian noise channel with circular curve, the interpretation method of the present invention sets greatest iteration time
Number N is 60 error-correcting performance simulation curve;
Foursquare curve is carried to represent under additive white Gaussian noise channel, the interpretation method of the present invention sets greatest iteration
Times N is 200 error-correcting performance simulation curve;
Curve with triangle represents under additive white Gaussian noise channel, and the interpretation method of the present invention sets greatest iteration
Times N is 600 error-correcting performance simulation curve;
Pentagonal curve is carried to represent under additive white Gaussian noise channel, with the error-correcting performance of existing ALP interpretation method
Simulation curve;
Carry criss-cross curve to represent under additive white Gaussian noise channel, imitated with the error-correcting performance of existing BP interpretation method
True curve.
As seen from Figure 3, the present invention can significantly improve entangling of interpretation method of the present invention by increasing maximum iteration time N
Wrong performance, but after increasing to 200 obtain gain very limited, that is, when maximum iteration time is for N=600 with existing
The error-correcting performance of ALP interpretation method is closely.
The present invention compared with existing BP interpretation method, signal to noise ratio be less than 2.5dB when, interpretation method error-correcting performance of the present invention
Poor, but the error-correcting performance slope of curve of the present invention is larger, and that is, with the increase of signal to noise ratio, error-correcting performance raising becomes apparent from.?
When signal to noise ratio is more than 2.6dB, error-correcting performance is substantially better than BP interpretation method.Meanwhile, error-correcting performance be 10-5When, BP decoding side
Method occurs in that error floor phenomenon, and now error-correcting performance increases with signal to noise ratio and improves slowly, and interpretation method of the present invention
This error floor phenomenon does not occur.
The foregoing is only presently preferred embodiments of the present invention, not in order to limit the present invention, all spirit in the present invention and
Within principle, any modification, equivalent substitution and improvement done etc., should be included in the range of the comprising of the present invention.
Claims (2)
1. a kind of LDPC code linear programming interpretation method based on acceleration alternating direction multiplier method, comprises the steps:
(1) decoding initialization:
1a) binary system LDPC code C for n to code length, under additive white Gaussian noise channel, obtains line according to message r receiving
The coefficient gamma of property object of planning functioni=log (Pr (ri|ci=0)/Pr (ri|ci=1)), i ∈ { 1,2 ..., n }, wherein, ciTable
Show the symbol of transmission, Pr () represents the event occurrence rate representing in bracket;
1b) according to coefficient gammaiBy piecewise functionObtain initial solution x decoding;
1c) setting accelerated factor α=1, auxiliary solution vectorIterationses k=0, setting iteration maximum times N, tolerance
ε, to each check-node j ∈ J, arranges Lagrange multiplier yj, auxiliary Lagrange multiplier vectorAuxiliary vector zj, transmission
Information Lj→iIt is null vector and length is dj, wherein, J is LDPC code check-node indexed set, djIt is that check-node j is verified
The number of variable node;
(2) Lagrange multiplier according to kth time iterationConciliate vector xk, calculate the auxiliary vector z of+1 iteration of kthj:
Wherein, TjIt is the transition matrix being generated by check-node j,It is to be d by lengthjAnd all containing even number 1 0-1 vector
The many cell spaces of verification being constituted,Represent vectorTo the many cell spaces of verificationEuclid projection
Computing, auxiliary vectorWith Lagrange multiplier vectorContained element number is dj, and store check-node j institute successively
The respective value of the variable node of verification;
(3) according to auxiliary vectorWith Lagrange multiplier vectorThe check-node j calculating+1 iteration of kth passes to change
The information of amount node i
Wherein, NcThe indexed set of j variable node that () is verified by check-node j,WithExpression kth+1 time respectively
Iteration auxiliary vectorWith kth time iteration Lagrange multiplier vectorThe corresponding value of middle variable node i;
(4) update+1 iterative solution vector x of kthk+1The value of middle all elements;
Wherein, ρ is penalty factor and meets ρ > 0, I is LDPC code variable node indexed set, diRepresent all verification variable node i
Check-node number, NvI () is the check-node indexed set of all verification variable node i, symbol ∏[0,1]() represents one
Euclid's project in interval [0,1] for the individual scalar;
(5) to all check-node j ∈ J, according to solution vector xk+1Update the Lagrange multiplier vector of+1 iteration of kth
Wherein,Represent the Lagrange multiplier vector of kth time iteration, TjIt is the transition matrix being generated by check-node j, xk+1For
The solution vector of+1 iteration of kth,Represent the auxiliary vector of+1 iteration of kth;
(6) pass through accelerated factor αk+1Revise solution vector xk+1With Lagrange multiplier vector
6a) calculate the accelerated factor of+1 iteration of kth
6b) according to accelerated factor αk+1, first calculate the auxiliary solution vector of+1 iteration of kthAgain
Update solution vector
6c) to all of check-node j ∈ J, first calculate the auxiliary Lagrange multiplier vector of+1 iteration of kthUpdate the Ge Lang multiplier vector of+1 iteration of kth again
(7) judge whether iterationses k+1 reaches iteration maximum times N, if reaching, decoding terminates, by+1 iterative solution of kth
Vector xk+1Export as translating code word, otherwise execution step (8);
(8) according to solution vector xk+1And auxiliary variableVector is calculated to each check-node j ∈ JInfinite model
NumberObtain maximum therein, if this maximum is less than tolerance ε, decodes and terminate, by solution vector xk+1Make
For result output, otherwise go to step (2) after k increasing 1.
2. interpretation method according to claim 1 is it is characterised in that pass through accelerated factor α in described step (6)k+1Revise
Solution vector xk+1With Lagrange multiplier vectorIn order to accelerate the convergence rate of decoding iteration.
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CN104393877B (en) * | 2014-12-03 | 2017-07-28 | 西安电子科技大学 | Irregular LDPC codes linear programming interpretation method based on weighting |
CN104682968B (en) * | 2015-03-14 | 2017-11-17 | 西安电子科技大学 | The linear programming interpretation method of high-speed low density parity check code |
CN105530014B (en) * | 2015-12-30 | 2019-03-08 | 西安电子科技大学 | Based on the LDPC code alternating direction multiplier interpretation method for simplifying projection operator |
CN105959015B (en) * | 2016-04-22 | 2019-01-29 | 西安电子科技大学 | LDPC code linear programming interpretation method based on minimum polyhedral model |
CN107689801B (en) * | 2017-09-07 | 2019-10-25 | 西安电子科技大学 | The early method of shutting down of LDPC code ADMM iterative decoding |
CN109618312B (en) * | 2019-01-18 | 2020-09-22 | 华北电力大学 | D2D relay network-oriented low-complexity online resource allocation optimization algorithm |
CN112910472B (en) * | 2021-01-21 | 2023-03-21 | 西安电子科技大学 | LDPC code punishment decoding method based on 2 norm box type ADMM |
Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2007082626A2 (en) * | 2006-01-17 | 2007-07-26 | Thomson Licensing | Method and apparatus for error correction decoding |
CN101615913A (en) * | 2009-07-17 | 2009-12-30 | 清华大学 | The quick convergence decoding algorithm of LDPC sign indicating number |
Family Cites Families (1)
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---|---|---|---|---|
US8341488B2 (en) * | 2008-08-04 | 2012-12-25 | Broadcom Corporation | Accumulating LDPC (low density parity check) decoder |
-
2014
- 2014-07-07 CN CN201410320942.8A patent/CN104092468B/en active Active
Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2007082626A2 (en) * | 2006-01-17 | 2007-07-26 | Thomson Licensing | Method and apparatus for error correction decoding |
CN101615913A (en) * | 2009-07-17 | 2009-12-30 | 清华大学 | The quick convergence decoding algorithm of LDPC sign indicating number |
Non-Patent Citations (2)
Title |
---|
Efficient Iterative LP Decoding of LDPC Codes with Alternating Direction Method of Multipliers;Xiaojie Zhang 等;《2013 IEEE International Symposium on Information Theory Proceedings(ISIT)》;20131008;826-831 * |
压缩感知中基于快速交替方向乘子法的l0-正则化信号重构;杨真真 等;《电子与信息学报》;20130430;第35卷(第4期);1501-1505 * |
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