CN104009944A - Device and method for estimating channel effect - Google Patents
Device and method for estimating channel effect Download PDFInfo
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- CN104009944A CN104009944A CN201310062724.4A CN201310062724A CN104009944A CN 104009944 A CN104009944 A CN 104009944A CN 201310062724 A CN201310062724 A CN 201310062724A CN 104009944 A CN104009944 A CN 104009944A
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Abstract
The invention provides a device and a method for estimating the channel effect. The method of the invention comprises the following steps: a receiving module receives a first data and a first reference data arriving in a first time segment, a second data and a second reference data arriving in a second time segment, and a third data and a third reference data arriving in a third time segment; an estimation module estimates channel effects corresponding to the first data, the third data, the first reference data, the second reference data and the third reference data; a coefficient calculation module performs a Wiener filter coefficient calculation program according to the channel effects corresponding to the first reference data, the second reference data and the third reference data to generate a set of time-domain interpolation coefficients; and an interpolation module interpolates by use of the channel effects corresponding to the first data and the third data according to the set of time-domain interpolation coefficients to generate a channel effect corresponding to the second data.
Description
Technical field
The present invention is relevant to digital signal broadcast technology, and be especially relevant to channel response (channel effect) how to estimate integrated service numerical digit terrestrial broadcasting (integrated services digital broadcasting-terrestrial, ISDB-T) signal.
Background technology
Along with the progress of the communication technology, the development of DVB-T broadcast is gradually ripe.Except transmitting via cable line, DVB-T signal also can see through the equipment such as base station or artificial satellite and be passed with the kenel of wireless signal.Integrated service numerical digit terrestrial broadcasting (ISDB-T) is one of standard being widely adopted in current this field.Wireless signal can be subject to unavoidably impact and the interference of its transmission environment in transmittance process.ISDB-T receiving terminal must evaluate corresponding channel response, and then eliminates the impact of channel response on signal content, and the beginning can correctly be understood the data that receive.
Each self-contained 204 orthogonal frequency division multiplex (MUX)s (the orthogonal frequency division multiplexing of each Frame (frame) in ISDB-T signal, OFDM) symbol (symbol), and the content bit of the each self-contained multiple subcarriers of each symbol (subcarrier) carrying.Fig. 1 is the signal content example arrangement of ISDB-T, and its transverse axis is frequency, and the longitudinal axis is symbol number (more evening of the larger person's of numbering transmitting time).The subcarrier of multiple that as shown in Figure 1, Frequency Index is 3 (for example 0,3,6,9 ...) can carry a dispersive vectoring signal (scatter pilot, SP) every four symbols.
Because the original contents of above-mentioned dispersive vectoring signal is that receiving terminal is known, therefore can judge as receiving terminal the foundation of channel response.For example, ISDB-T receiving terminal can first be found out the frequency domain channel response H of the dispersive vectoring signal that time index is 0, Frequency Index is 0
(t=0, f=0), and the frequency domain channel response H of the dispersive vectoring signal that time index is 4, Frequency Index is 0
(t=4, f=0).Subsequently, ISDB-T receiving terminal can utilize time domain interpolation (time-domain interpolation) to determine to be positioned at H
(t=0, f=0)and H
(t=4, f=0)between frequency domain channel response H
(t=1, f=0), H
(t=2, f=0), H
(t=3, f=0).Similarly, ISDB-T receiving terminal can utilize H
(t=1, f=3)and H
(t=5, f=3)interpolation goes out to be positioned at H between the two
(t=2, f=3), H
(t=3, f=3), H
(t=4, f=3).
Generally speaking, ISDB-T receiving terminal determines time domain interpolation coefficient according to the ratio in the time interval, for example, make H
(t=1, f=0)=H
(t=0, f=0)* 0.25+H
(t=4, f=0)* 0.75, namely make corresponding to H
(t=1, f=0)time domain interpolation coefficient be 0.25 and 0.75.The rest may be inferred, H
(t=2, f=0)=H
(t=0, f=0)* 0.5+H
(t=4, f=0)* 0.5, and H
(t=3, f=0)=H
(t=0, f=0)* 0.75+H
(t=4, f=0)* 0.25.In the situation that channel response can change fast along with time evolution (for example, in there is the communication environments of Du Bule effect), the mode of this selection time domain interpolation coefficient is easy to produce wrong interpolation result.
Summary of the invention
For addressing the above problem, the present invention proposes new channel response estimation unit and channel response method of estimation.By utilizing Weiner filter (Wiener filter) coefficient calculations program dynamically to determine time domain interpolation coefficient, compared to the prior art that determines interpolation coefficient with Fixed Time Interval ratio, can more really reflect according to estimation unit of the present invention and method of estimation the variation that channel response produces along with time evolution.
A specific embodiment according to the present invention is a kind of channel response estimation unit, wherein comprises a receiver module, an estimation module, a coefficients calculation block and an interpose module.One first data and one first reference data, one second data that arrive in one second time section and one second reference data that this receiver module arrives in order to be received in a very first time section, and one the 3rd data that arrive in one the 3rd time section and one the 3rd reference data.These first data, these second data and the 3rd data see through one first subcarrier transmission.This first reference data, this second reference data and the 3rd reference data see through one second subcarrier transmission.This estimation module is in order to estimate the each self-corresponding channel response of these first data, the 3rd data, this first reference data, this second reference data and the 3rd reference data.This coefficients calculation block is in order to carry out a Weiner filter coefficient calculations program according to this first reference data, this second reference data and corresponding these channel response of the 3rd reference data, to produce one group of time domain interpolation coefficient.This interpose module, in order to according to this group time domain interpolation coefficient, utilizes these first data to produce a channel response corresponding to these second data with each self-corresponding this channel response interpolation of the 3rd data.
Another specific embodiment according to the present invention is a channel response method of estimation.First the method carries out a receiving step, be received in one first data and one first reference data, one second data that arrive in one second time section and one second reference data that a very first time section arrives at, and one the 3rd data that arrive in one the 3rd time section and one the 3rd reference data.These first data, these second data and the 3rd data see through one first subcarrier transmission.This first reference data, this second reference data and the 3rd reference data see through one second subcarrier transmission.Then, the method is carried out an estimating step, estimates the each self-corresponding channel response of these first data, the 3rd data, this first reference data, this second reference data and the 3rd reference data.Subsequently, the method is carried out a calculation procedure, carries out a Weiner filter coefficient calculations program, to produce one group of time domain interpolation coefficient according to this first reference data, this second reference data and corresponding these channel response of the 3rd reference data.Then, the method is carried out an interpolation step, according to this group time domain interpolation coefficient, utilizes these first data to produce a channel response corresponding to these second data with each self-corresponding this channel response interpolation of the 3rd data.
See through following detailed description and accompanying drawings, can further understand the advantages and spirit of the present invention.
For there is to better understanding above-mentioned and other aspect of the present invention, preferred embodiment cited below particularly, and coordinate accompanying drawing, be described in detail below:
Brief description of the drawings
Fig. 1 is the signal content example arrangement of ISDB-T.
Fig. 2 is according to the functional block diagram of the channel response estimation unit in one embodiment of the invention.
Fig. 3 is according to the flow chart of the channel response method of estimation in one embodiment of the invention.
Symbol description
200: channel response estimation unit 22: receiver module
24: estimation module 26: coefficients calculation block
28: interpose module S31 ~ S34: process step
Embodiment
Be a channel response estimation unit according to one embodiment of the invention, its functional block diagram as shown in Figure 2.Channel response estimation unit 200 comprises receiver module 22, estimation module 24, coefficients calculation block 26 and interpose module 28.In practical application, channel response estimation unit 200 can be incorporated in various ISDB-T wireless receiving systems, also can independently exist.See through following explanation, persond having ordinary knowledge in the technical field of the present invention can understand, the application of channel response estimation unit 200 is not limited to ISDB-T system, but may extend to the wireless receiving system of the various time domain interpolation coefficients that need to determine channel response.Following examples mainly taking channel response estimation unit 200 in order to coordinate the situation of ISDB-T receiving terminal as example.
First, receiver module 22 is responsible for receiving and keeping in each symbol that sequentially arrives at ISDB-T receiving terminal, its content as shown in Figure 1, comprise and be carried on transmission and multiplex's configuration control (transmission and multiplexing configuration control, the TMCC) signal that data-signal, dispersive vectoring signal and the Frequency Index of the subcarrier that multiple frequencies are different are P.These symbols have continuity in time, and the less person's of symbol number arrival time more early.TMCC signal is in order to transmit the information such as modulation type, encoding rate, scrambling length, multiplex's scheme, for receiving terminal reference.In practice, along with the variation of ISDB-T transmission mode, the TMCC number of subcarriers in each symbol also may be different.Below explanation hypothesis P is the special value corresponding to a certain TMCC subcarrier.
In this embodiment, channel response estimation unit 200 utilizes TMCC signal and dispersive vectoring signal as the foundation of estimating unknown channel response.More particularly, channel response estimation unit 200 utilizes TMCC signal as reference signal, determines time domain interpolation coefficient, then produces the channel response of data-signal with the channel response interpolation of dispersive vectoring signal.Taking determine time index as 1, the frequency domain channel response H of the data-signal of Frequency Index as 0
(t=1, f=0)situation be example, first channel response estimation unit 200 utilizes time index to be respectively 0,1,4, and three TMCC signals that Frequency Index is P are as reference signal, determine one group of time domain interpolation coefficient.Subsequently, channel response estimation unit 200 is with the known frequency domain channel response H of dispersive vectoring signal
(t=0, f=0)and H
(t=4, f=0)interpolation produces H
(t=1, f=0).The function mode of channel response estimation unit 200 is below described in detail in detail.
Estimation module 24 is responsible for estimating the frequency domain channel response of each dispersive vectoring signal and TMCC signal.As discussed previously, the original contents of dispersive vectoring signal is that receiving terminal is known, and the content that therefore estimation module 24 can directly compare contents known and receive, to produce its frequency domain channel response.Relatively, the original contents of TMCC signal is not known to receiving terminal, and estimation module 24 can, first by each TMCC signal demodulation, decoding, reevaluate its frequency domain channel response.Because ISDB-T transmission end utilizes difference binary phase skew modulation (differential binary phase shift keying, DBPSK) produce TMCC signal, that is to say, TMCC signal only has+and 1 and-1 two kind, the decoded result correctness of TMCC signal is therefore quite high.The frequency domain channel response of the TMCC signal that accordingly, estimation module 24 produces also has quite high confidence level.Should be noted that, the deciding means of the frequency domain channel response of known signal is known to persond having ordinary knowledge in the technical field of the present invention, repeats no more in this.
Then, be respectively 0,1,4 according to estimation module 24 for time index, and the frequency domain channel response H that three TMCC signals that Frequency Index is P produce
tMCC0, H
tMCC1, H
tMCC4, coefficients calculation block 26 is carried out a Weiner filter (Wiener filter) coefficient calculations program, to produce one group of time domain interpolation coefficient.One of the characteristic of wiener filter coefficients calculation procedure is to make the amount of error in estimated result to be minimized.In this embodiment, coefficients calculation block 26 produces the first coefficient W being contained in this group time domain interpolation coefficient according to following equation
1with the second coefficient W
2:
Formula one is one of form of Wei Na-Hope equation (Wiener-Hopf equation).
Subsequently, interpose module 28 is according to this group time domain interpolation coefficient, the H that utilizes estimation module 24 to produce
(t=0, f=0)and H
(t=4, f=0)interpolation produces H
(t=1, f=0), its operation program can be represented as:
In an embodiment, coefficients calculation block 26 can more comprise a smoothing unit (not illustrating), is used to produce the first coefficient W
1with the second coefficient W
2before, lower column matrix is carried out to a smoothing program:
So that this matrix becomes the vertical hereby matrix (Toeplitz matrix) of a Mortopl, the computational complexity of simplified style one by this.For example, this smoothing program may be, but not limited to,, the mean value of the element in the upper left corner and the element in the lower right corner in compute matrix, and replace this two elements with this mean value.
If the smoothed vertical hereby matrix of Mortopl that turns to of the matrix in formula three, coefficients calculation block 26 can utilize a Li Wensen recurrence (Levinson recursion) algorithm to produce the first coefficient W accordingly
1with the second coefficient W
2.Should be noted that, the way of utilizing Li Wensen recurrence algorithm to simplify the equational solution of Wei Na-Hope is known technology, repeats no more in this.
As shown in Figure 1, the TMCC signal that the data-signal that time index is 0, Frequency Index is 0 and time index are 0, Frequency Index is P is contained in prosign, can be regarded as same time section and deliver to ISDB-T receiving terminal.Similarly, the TMCC signal that the data-signal that time index is 1, Frequency Index is 0 and time index are 1, Frequency Index is P is delivered to ISDB-T receiving terminal in same time section, and the TMCC signal that the data-signal that time index is 4, Frequency Index is 0 and time index are 4, Frequency Index is P is delivered to ISDB-T receiving terminal in same time section.Due to the frequency response characteristic in same time section and possible similar, channel response estimation unit 200 is with H
tMCC1with respect to H
tMCC0and H
tMCC4property association in time estimate H
(t=1, f=0)with respect to H
(t=0, f=0)and H
(t=4, f=0)property association in time.The rest may be inferred, be respectively 0,2,4 according to estimation module 24 for time index, and the frequency domain channel response that three TMCC signals that Frequency Index is P produce, coefficients calculation block 26 can be carried out a Weiner filter coefficient calculations program, the frequency domain channel response of the data-signal that be 2 to produce another group time domain interpolation coefficient, to be suitable for generation time index, Frequency Index is 0.Be different from the prior art that determines interpolation coefficient with Fixed Time Interval ratio, the way of channel response estimation unit 200 can reflect the variation that channel response produces along with time evolution on average more really.
Although it should be noted that in the above-described embodiments, the channel response that produces unknown channel response in order to interpolation is all that concept of the present invention is not limited to this corresponding to known signal (dispersive vectoring signal).For example, if channel response estimates that 200 have determined the channel response of the data-signal that time index is 2, Frequency Index is 3, and the channel response of the data-signal that time index is 4, Frequency Index is 3, also can be further according to one group of interpolation coefficient of TMCC signal deciding, in order to the channel response of the data-signal that generation time index is 3, Frequency Index is 3.
In addition the reference signal that, determines according to this interpolation coefficient is also not limited to TMCC signal.For example, at digital video terrestrial broadcasting (digital video broadcasting-terrestrial, DVB-T) in system, the continuous pilot signal (continual pilot, CP) that each symbol comprises also can determine as receiving terminal the reference signal of interpolation coefficient.
Another specific embodiment according to the present invention is a channel response method of estimation, and its flow chart as shown in Figure 3.First the method performs step S31, (for example in Fig. 1, time index is 0 to be received in one first data that a very first time section arrives at, Frequency Index is 0 dispersive vectoring signal) (for example in Fig. 1, time index is 0 with one first reference data, Frequency Index is the TMCC signal of P), (for example in Fig. 1, time index is 1 to one second data that arrive in one second time section, Frequency Index is 0 data-signal) (for example in Fig. 1, time index is 1 with one second reference data, Frequency Index is the TMCC signal of P), and one the 3rd data that arrive in one the 3rd time section (for example in Fig. 1, time index is 4, Frequency Index is 0 dispersive vectoring signal) (for example in Fig. 1, time index is 4 with one the 3rd reference data, Frequency Index is the TMCC signal of P).These first data, these second data and the 3rd data see through one first subcarrier transmission.This first reference data, this second reference data and the 3rd reference data see through one second subcarrier transmission.Then, the method execution step S32, estimates the each self-corresponding channel response of these first data, the 3rd data, this first reference data, this second reference data and the 3rd reference data.Subsequently, the method execution step S33, carries out a Weiner filter coefficient calculations program according to this first reference data, this second reference data and corresponding these channel response of the 3rd reference data, to produce one group of time domain interpolation coefficient.Then, the method execution step S34, according to this group time domain interpolation coefficient, utilizes these first data to produce a channel response corresponding to these second data with each self-corresponding this channel response interpolation of the 3rd data.
The various circuit operations of previously having described in the time introducing channel response estimation unit 200 change (for example simplifying the mode of wiener filter coefficients calculation procedure) and also can be applied in the channel response method of estimation that Fig. 3 illustrates, and its details repeats no more.
As mentioned above, the present invention proposes new channel response estimation unit and channel response method of estimation.By utilizing wiener filter coefficients calculation procedure dynamically to determine time domain interpolation coefficient, compared to the prior art that determines interpolation coefficient with Fixed Time Interval ratio, can more really reflect according to estimation unit of the present invention and method of estimation the variation that channel response produces along with time evolution.
By the detailed description of above specific embodiment, hope can be known description feature of the present invention and spirit more, and not with the above-mentioned specific embodiment being disclosed, category of the present invention is limited.On the contrary, its objective is that hope can contain in the category of the scope of the claims of being arranged in of various changes and tool equality institute of the present invention wish application.
Claims (12)
1. a channel response estimation unit, comprises:
One receiver module, one first data and one first reference data, one second data that arrive in one second time section and one second reference data that arrive in order to be received in a very first time section, and one the 3rd data that arrive in one the 3rd time section and one the 3rd reference data, wherein these first data, these second data and the 3rd data see through one first subcarrier transmission, and this first reference data, this second reference data and the 3rd reference data see through one second subcarrier transmission;
One estimation module, in order to estimate the each self-corresponding channel response of these first data, the 3rd data, this first reference data, this second reference data and the 3rd reference data;
One coefficients calculation block, in order to carry out a Weiner filter coefficient calculations program according to this first reference data, this second reference data and corresponding these channel response of the 3rd reference data, to produce one group of time domain interpolation coefficient; And
One interpose module, in order to according to this group time domain interpolation coefficient, utilizes these first data to produce a channel response corresponding to these second data with each self-corresponding this channel response interpolation of the 3rd data.
2. channel response estimation unit as claimed in claim 1, is characterized in that, this group time domain interpolation coefficient comprises one first coefficient W
1with one second coefficient W
2, this coefficients calculation block produces this first coefficient W according to following equation
1with this second coefficient W
2:
Wherein T
1represent corresponding this channel response of this first reference data, T
2represent corresponding this channel response of this second reference data, T
3represent corresponding this channel response of the 3rd reference data.
3. channel response estimation unit as claimed in claim 2, is characterized in that, this interpose module produces this channel response H corresponding to these second data according to following equation
2:
Wherein H
1represent corresponding this channel response of these first data, H
2represent corresponding this channel response of these second data.
4. channel response estimation unit as claimed in claim 2, is characterized in that, this coefficients calculation block comprises a smoothing unit, is used to produce before this first coefficient and this second coefficient, and lower column matrix is carried out to a smoothing program:
So that this matrix becomes the vertical hereby matrix of a Mortopl.
5. channel response estimation unit as claimed in claim 4, is characterized in that, this coefficients calculation block utilizes a Li Wensen recurrence algorithm to produce this first coefficient and this second coefficient.
6. channel response estimation unit as claimed in claim 1, it is characterized in that, these first data, these second data, the 3rd data, this first reference data, this second reference data and the 3rd reference data are sent by an integrated service numerical digit terrestrial broadcasting transmission end, and these first data and the 3rd data dispersive vectoring signal of respectively doing for oneself, this first reference data, this second reference data and the 3rd reference data are contained in a transmission and multiplex's configuration control signal.
7. a channel response method of estimation, comprises:
(a) be received in one first data and one first reference data, one second data that arrive in one second time section and one second reference data that a very first time section arrives at, and one the 3rd data that arrive in one the 3rd time section and one the 3rd reference data, wherein these first data, these second data and the 3rd data see through one first subcarrier transmission, and this first reference data, this second reference data and the 3rd reference data see through one second subcarrier transmission;
(b) estimate the each self-corresponding channel response of these first data, the 3rd data, this first reference data, this second reference data and the 3rd reference data;
(c) carry out a Weiner filter coefficient calculations program according to this first reference data, this second reference data and corresponding these channel response of the 3rd reference data, to produce one group of time domain interpolation coefficient; And
(d), according to this group time domain interpolation coefficient, utilize these first data to produce a channel response corresponding to these second data with each self-corresponding this channel response interpolation of the 3rd data.
8. channel response method of estimation as claimed in claim 7, is characterized in that, this group time domain interpolation coefficient comprises one first coefficient W
1with one second coefficient W
2, step (c) comprises according to following equation and produces this first coefficient W
1with this second coefficient W
2:
Wherein T
1represent corresponding this channel response of this first reference data, T
2represent corresponding this channel response of this second reference data, T
3represent corresponding this channel response of the 3rd reference data.
9. channel response method of estimation as claimed in claim 8, is characterized in that, step (d) comprises according to following equation and produces this channel response H corresponding to these second data
2:
Wherein H
1represent corresponding this channel response of these first data, H
2represent corresponding this channel response of these second data.
10. channel response method of estimation as claimed in claim 8, is characterized in that, step (c) is contained in and produces before this first coefficient and this second coefficient, and lower column matrix is carried out to a smoothing program:
So that this matrix becomes the vertical hereby matrix of a Mortopl.
11. channel response methods of estimation as claimed in claim 10, is characterized in that, step (c) comprises utilizes a Li Wensen recurrence algorithm to produce this first coefficient and this second coefficient.
12. channel response methods of estimation as claimed in claim 7, it is characterized in that, these first data, these second data, the 3rd data, this first reference data, this second reference data and the 3rd reference data are sent by an integrated service numerical digit terrestrial broadcasting transmission end, and these first data and the 3rd data dispersive vectoring signal of respectively doing for oneself, this first reference data, this second reference data and the 3rd reference data are contained in a transmission and multiplex's configuration control signal.
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108075993A (en) * | 2016-11-11 | 2018-05-25 | 扬智科技股份有限公司 | Adaptivity adjusts the method and its process circuit of filter coefficient |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20050094747A1 (en) * | 2003-10-29 | 2005-05-05 | Sung-Woo Park | Apparatus to estimate a channel using training sequence data for a digital receiver and a method thereof |
| CN101184080A (en) * | 2007-12-26 | 2008-05-21 | 北京创毅视讯科技有限公司 | Velocity sensitization type channel estimation unit and method for orthogonal frequency division multiplexing system |
| CN101827057A (en) * | 2010-01-28 | 2010-09-08 | 北京天碁科技有限公司 | Channel estimation method and channel estimator for orthogonal frequency division multiplexing (OFDM ) communication system |
| US8335284B1 (en) * | 2009-03-05 | 2012-12-18 | Qualcomm Atheros, Inc. | System and method for inter-channel interference reduction |
-
2013
- 2013-02-27 CN CN201310062724.4A patent/CN104009944B/en not_active Expired - Fee Related
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20050094747A1 (en) * | 2003-10-29 | 2005-05-05 | Sung-Woo Park | Apparatus to estimate a channel using training sequence data for a digital receiver and a method thereof |
| CN101184080A (en) * | 2007-12-26 | 2008-05-21 | 北京创毅视讯科技有限公司 | Velocity sensitization type channel estimation unit and method for orthogonal frequency division multiplexing system |
| US8335284B1 (en) * | 2009-03-05 | 2012-12-18 | Qualcomm Atheros, Inc. | System and method for inter-channel interference reduction |
| CN101827057A (en) * | 2010-01-28 | 2010-09-08 | 北京天碁科技有限公司 | Channel estimation method and channel estimator for orthogonal frequency division multiplexing (OFDM ) communication system |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108075993A (en) * | 2016-11-11 | 2018-05-25 | 扬智科技股份有限公司 | Adaptivity adjusts the method and its process circuit of filter coefficient |
| CN108075993B (en) * | 2016-11-11 | 2020-07-28 | 扬智科技股份有限公司 | Method for adaptively adjusting filter coefficient and processing circuit thereof |
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