CN103560864A - Blind channel self-adaptation method and device - Google Patents

Abstract

The invention discloses a blind channel self-adaptation method and device. The blind channel self-adaptation method comprises the following steps of estimating phase noise of input signals, estimating amplitude attenuation of the input signals, detecting pulse interference of the input signals, weighing a phase noise estimation value and an amplitude attenuation estimation value to obtain a channel quality estimation value, carrying out threshold comparison to obtain the self-adaptation information of a channel, and by utilizing the channel self-adaptation information, finishing a channel self-adaptation process in a self-adaptation sending mode through a sending end. The blind channel self-adaptation device comprises a phase angle calculation and quantization module, a demapping module, a phase noise estimation module, an amplitude calculation and quantization module, an amplitude attenuation and estimation module, an interference detection module, a weighing module, a channel self-adaptation module and a self-adaptation sending module. Through coefficient-variable weighing processing on phase noise and amplitude attenuation, the blind channel self-adaptation method and device improve the accuracy of channel estimation, are high in applicability, and are high in transmission efficiency. The sending end adjusts the parameters of sending signals in a self-adaptation mode according to the channel quality, and makes full use of the channel resources.

Description

A kind of blind Channel adaptive approach and device thereof

Technical field

The present invention relates to digital communicating field, be specifically related to a kind of blind Channel adaptive approach and device thereof that is applicable to multi-carrier reception system.

Background technology

At present, in general communication system, channel circumstance is all more severe, except signal itself is along with the increase decay of communication distance increases gradually, also exist various noise jamming, as Gaussian noise, impulsive noise etc., in addition, Multipath Transmission can produce serious influence to the receptivity of signal.So, want in channel so complicated and changeable, to obtain communication reliably, must take multiple channel interference protection measure, wherein, channel self-adapting is a kind of technology that improves systematic function generally adopting in existing communication system.Channel self-adapting technology is the estimated value according to current channel quality, transmitter adaptively modifying modulation system, signal bandwidth, coded system, transmitting power, power adaptive distribution etc., are guaranteeing, under the prerequisite of received signal quality, to utilize substantially channel resource to realize.

The prerequisite of channel self-adapting is the estimation of channel quality, its method mainly can be divided into two classes, one class is to obtain by calculating bit error rate (BER), the error rate (SER) or packet loss (PLR), but error rate is not only relevant with channel quality, also relevant with modulation system, coded system etc., so can not reflect exactly current channel quality condition, in addition, mistake of statistics rate need to send mass data.Another kind of is that Signal Interference and Noise Ratio (SINR, Signal to Interference plus Noise Ratio) by estimating received signal obtains, and at present, what most systems was used is all the method.Lot of domestic and international experts and scholars have also done a large amount of work to the method for the estimation of SINR, its method is mainly divided into two kinds, a kind of is based on data-aided non-blind estimating method, the reliability that the method needs a large amount of pilot signals or training sequence guarantee to estimate, based on a non-data-aided blind estimating method, the method adopts special algorithm directly to process to received signal.These two kinds of methods respectively have pluses and minuses, and non-blind estimating method estimated performance is relatively better, but has reduced efficiency of transmission, and the availability of frequency spectrum is lower, and in today of frequency spectrum resource growing tension, it is not that very high occasion is generally without the method that estimated performance is required.Blind estimating method makes full use of the characteristic of signal self to be estimated, do not need the auxiliary data of transmitting terminal, efficiency of transmission is high, there is wide application space, but the algorithm complex of at present direct blind estimation SINR is high, realizes difficulty, practical application is not strong, and performance also has much room for improvement.

Summary of the invention

The object of the present invention is to provide a kind of complexity is little, the availability of frequency spectrum is high, realization is simple and accuracy is high blind Channel adaptive approach and device thereof.

The technical scheme that realizes above-mentioned purpose is:

A kind of blind Channel adaptive approach of one of the present invention, comprises the following steps:

Step S0, phase noise is estimated, the phase deviation according to input signal at planisphere, respectively at time domain and frequency domain statistics phase noise;

Step S1, amplitude fading is estimated, according to the amplitude of input signal, is added up amplitude fading respectively on time domain and frequency domain;

Step S2, Interference Detection, based on default interference threshold, detects the impulse disturbances of input signal;

Step S3, weighting, according to default weight coefficient, phase noise and amplitude fading are processed in weighting, obtain the estimated value of channel quality;

Step S4, channel self-adapting, according to the estimated value of channel quality, based on preset channel thresholding, obtains channel self-adapting information;

Step S5, self adaptation sends, and according to the channel self-adapting information of receiving end feedback, makes a start and adjusts the transmission parameter of data.

Above-mentioned blind Channel adaptive approach, wherein, described step S0 comprises:

Calculate the phase value amount of input signal;

Phase quantization, based on Interference Detection, changes into some bits the phase value amount even amount obtaining;

According to the phase quantization result obtaining, the calculating phase deviation on planisphere, and on time domain and frequency domain, carry out respectively statistical average.

Above-mentioned blind Channel adaptive approach, wherein, the input signal of described step S0, for differential modulation mode, refers to differential ference spiral signal afterwards.

Above-mentioned blind Channel adaptive approach, wherein, described phase quantization result also, by non-uniform quantizing, completes demapping process, exports soft bit, processes to follow-up soft decoding.

Above-mentioned blind Channel adaptive approach, wherein, described step S1 comprises:

According to the real part of input signal and imaginary part, calculate amplitude;

Based on Interference Detection, the amplitude even amount obtaining is changed into some bits;

According to amplitude quantization result, on time domain and frequency domain, carry out respectively statistical average.

Above-mentioned blind Channel adaptive approach, wherein, the input signal of described step S1 has identical amplitude on the planisphere of making a start.

Above-mentioned blind Channel adaptive approach, wherein, described amplitude, its standard value is the arithmetic square root of the quadratic sum of real part and imaginary part.

Above-mentioned blind Channel adaptive approach, wherein, described step S2 specifically refers to: by the amplitude of comparator input signal and the size of default interference threshold, obtain disturbing index signal.

Above-mentioned blind Channel adaptive approach, wherein, described step S3 specifically comprises:

Step S30, deducts current phase noise by the maximum that phase noise occurs and obtains a new phase noise expression value;

Step S31, is normalized into amplitude fading with new phase noise expression value and has identical bit wide;

Step S32, the phase noise expression value that step S30 is obtained is multiplied by weight coefficient α, and the amplitude fading that step S31 is obtained is multiplied by weight coefficient β, and acquired results is added the estimated value that obtains channel quality.

Above-mentioned blind Channel adaptive approach, wherein, the span of described weight coefficient α and β is [0,1], and meets alpha+beta=1.

Above-mentioned blind Channel adaptive approach, wherein, described step S4 comprises:

Step S40, compares the size of symbol channel quality estimation value and default symbol thresholding and carries out symbol quality counting;

Step S41, compares the size of carrier channel quality estimated value and default carrier channel thresholding and carries out carrier-quality counting;

Step S42, the average of calculating carrier channel quality estimated value obtains the whole average of the quality of channel;

Step S43, the average of the count value based on step S40, S41 and step S42 rules out modulation system;

Step S44, selects effective subcarrier number, estimates sub-band decay, and calculates transmitting power.

Above-mentioned blind Channel adaptive approach, wherein, described step S5 comprises:

Step S50, the modulation system based on selecting, data-mapping on corresponding constellation point;

Step S51, selects only secured transmission of payload data on effective subcarrier or on sub-band;

Step S52 according to sub-band attenuation, keeping, under the constant prerequisite of the total transmitting power of frequency domain, reducing transmitting power on the good sub-band of quality, increases transmitting power on second-rate sub-band;

Step S53, raises whole transmitting power in time domain.

A kind of blind Channel self-reacting device based on the described blind Channel adaptive approach of one of the present invention of two of the present invention, comprises and calculates phase angle quantization modules, demapping module, phase noise estimation module, calculates amplitude quantization modules, amplitude fading estimation module, interference detection module, weighting block, channel self-adapting module and self adaptation sending module; Described calculating phase angle quantization modules connect demapping module and phase noise estimation module; Described phase noise estimation module connects described weighting block; Described calculating amplitude quantization modules connect described interference detection module and amplitude fading estimation module; Described amplitude fading estimation module connects weighting block; Described interference detection module connects phase noise estimation module and amplitude fading estimation module; Described weighting block connects described channel self-adapting module; Described channel self-adapting module connects described self adaptation sending module, wherein:

Calculate phase angle quantization modules, for calculating the phase angle of input signal, even amount is passed to described demapping module and phase noise estimation module after changing into some bits;

Demapping module, according to the phase angle quantized value receiving, realizes the inverse process of mapping by non-uniform quantizing, give follow-up decoder module;

Phase noise estimation module, the phase deviation based on phase angle quantized value on planisphere, statistical average phase noise on symbol and on carrier wave, result is passed to described weighting block;

Calculate amplitude quantization modules, for calculating the amplitude of input signal, even amount is passed to described amplitude fading estimation module and interference detection module after changing into some bits;

Amplitude fading estimation module, based on amplitude quantizing value, statistical average amplitude fading on symbol and on carrier wave, result is passed to described weighting block;

Interference detection module, by the amplitude of comparison signal and the size of default interference threshold value, while being greater than thresholding, output disturbs index signal to described phase noise estimation module and amplitude fading estimation module;

Weighting block, according to weight coefficient, phase noise and amplitude attenuation are processed in weighting, and the channel quality estimation value obtaining is passed to described channel self-adapting module;

Channel self-adapting module, the channel quality estimation value according to input, based on preset channel thresholding, compares, counts and judgement obtains channel self-adapting information, and result is passed to described self adaptation sending module;

Self adaptation sending module, according to the channel self-adapting information of input, by adjusting the transmission parameter of data, realizes channel self-adapting.

Above-mentioned blind Channel self-reacting device, wherein, described calculating phase angle quantization modules comprise calculating unit, phase angle and phase quantization unit, wherein:

Calculating unit, phase angle, for realizing rectangular coordinate to polar conversion, obtains the value of the phase angle of input signal;

Phase quantization unit, changes into some bits for the value even amount phase angle, passes to described demapping module and phase noise estimation module.

Above-mentioned blind Channel self-reacting device, wherein, described phase quantization unit comprises the first multiplier, the first divider and round unit, wherein:

The first multiplier is realized input phase angle and 2 ⁿmultiplication, n is quantization bit;

The first divider for by the output of the first multiplier divided by 2 π, make output normalize to [0,2 ⁿ];

Round unit and take out integer-bit output, output valve is [0,2 ^n-1] between integer.

Above-mentioned blind Channel self-reacting device, wherein, described demapping module comprises form stores unit and lookup unit, wherein:

Form stores unit, for storing phase angle to the index of mapped bits;

Lookup unit, for realizing phase angle to the Index process of mapped bits.

Above-mentioned blind Channel self-reacting device, wherein, described phase noise estimation module comprises phase deviation computing unit and phase noise statistic unit, wherein:

Phase deviation computing unit, based on Interference Detection index signal, for calculating the deviation of phase place on planisphere, by the first adder being connected in series successively, mould remaining unit, the first subtracter and the unit that takes absolute value form, wherein:

First adder is realized the signal and 2 of its input ⁿ¹addition, n1 is quantization bit;

The remainder number of the signal of its input is realized in the remaining unit of mould;

The signal that the first subtracter is realized its input deducts 2 ⁿ¹;

Take absolute value unit the signal normalization to 2 of its input ⁿ¹in scope;

Phase noise statistic unit, be used for statistical average phase noise on symbol and on carrier wave respectively, obtain symbol phase noise and Carrier Phase Noise, comprise the first accumulator, the second accumulator, Carrier Phase Noise memory, symbol phase noise memory, the second divider and the 3rd divider, wherein:

The first accumulator, for cumulative current sign Carrier Phase Noise and the corresponding Carrier Phase Noise of symbol before;

The second accumulator, for the cumulative all Carrier Phase Noises of current sign;

Carrier Phase Noise memory, for storing the cumulative sum of each symbol carrier phase noise, length equals carrier wave number;

Symbol phase noise memory, for storing the cumulative sum of each carrier wave symbol phase noise, length equal symbol number;

The second divider, realizes the division of cumulative sum and the symbol numbers of Carrier Phase Noise, obtains the average of Carrier Phase Noise;

The 3rd divider, realizes the division of cumulative sum and the carrier wave number of symbol phase noise, obtains the average of symbol phase noise.

Above-mentioned blind Channel self-reacting device, wherein, described calculating amplitude quantization modules comprise amplitude computing unit and amplitude quantization unit, wherein:

Amplitude computing unit, for calculating the amplitude of input signal;

Amplitude quantization unit, for amplitude quantization being become to some bits, gives described interference detection module and amplitude fading estimation module.

Above-mentioned blind Channel self-reacting device, wherein, described amplitude fading estimation module is identical with the composition of described phase noise statistic unit.

Above-mentioned blind Channel self-reacting device, wherein, described weighting block comprises phase noise processing unit, amplitude fading processing unit, the second multiplier, the 3rd multiplier and second adder, wherein,

Phase noise processing unit, deducts respectively symbol phase noise and the Carrier Phase Noise of input by the maximum of phase noise, obtain phase noise processing costs;

Amplitude fading processing unit, for keeping amplitude fading to have identical bit wide with phase noise processing costs, obtains amplitude fading processing costs;

The second multiplier, is multiplied by the processing costs of phase noise for realizing weight coefficient α;

The 3rd multiplier, is multiplied by amplitude fading processing costs for realizing weight coefficient β;

Second adder, for realizing phase noise processing costs after multiplication process and the weighting of amplitude fading processing costs, obtains symbol quality estimated value and carrier channel quality estimated value.

Above-mentioned blind Channel self-reacting device, wherein, described channel self-adapting module comprises comparator, counter and decision device, wherein:

Comparator, for relatively symbol channel quality estimation value and carrier channel quality estimated value and corresponding default symbol thresholding and the size of default carrier channel thresholding;

Counter, for counting the carrier wave number that is less than the symbol numbers of default symbol thresholding and is greater than default carrier channel thresholding;

Average module, for calculating the average of carrier channel quality estimated value;

Modulation system determining unit, for determining modulation system based on count value and average;

Effective subcarrier determining unit, the modulation system based on definite, determines corresponding effective subcarrier sequence number;

Calculate sub-band gain coefficient unit, for carrier channel quality estimated value is converted to corresponding sub-band gain coefficient;

Calculate transmitting power coefficient elements, the modulation system based on definite and channel quality estimation average, the coefficient of calculating transmitting power.

Above-mentioned blind Channel self-reacting device, wherein, described self adaptation sending module comprises modulation system selected cell, effective sub-carrier allocation unit, sub-band power distributing unit and transmitting power adjustment unit, wherein:

Modulation system selected cell, the modulation system of coming according to receiving end feedback, for data-mapping to corresponding constellation point;

Effectively sub-carrier allocation unit, feeds back according to receiving end effective subcarrier sequence number of coming, for effectively placing transmission data on subcarrier;

Sub-band power distributing unit, the sub-band decay gain coefficient of coming according to receiving end feedback, input sub-band signal is multiplied by the adjustment that corresponding gain coefficient is realized sub-band power;

Transmitting power adjustment unit, the transmitting power coefficient of coming according to receiving end feedback, guarantees be no more than under the prerequisite of maximum transmission power, and input signal is multiplied by the adjustment that transmitting power coefficient is realized transmitting power.

The invention has the beneficial effects as follows: blind Channel adaptive approach of the present invention, because not requiring transmission auxiliary data, thereby improved transmission rate, the availability of frequency spectrum of system is high; Meanwhile, for different systems, by using different weight coefficient processing phase noises and amplitude fading to estimate to obtain channel quality, make accuracy of estimation high, and simple; In addition, the present invention, by Interference Detection, has reduced impulse disturbances well.

Accompanying drawing explanation

Fig. 1 is the flow chart of one of the present invention's blind Channel adaptive approach;

The schematic flow sheet that Fig. 2 estimates for the phase noise that the embodiment of the present invention provides;

The mapping that Fig. 3 provides for the embodiment of the present invention and the process schematic diagram of demapping;

The process schematic diagram that Fig. 4 calculates for the phase deviation that the embodiment of the present invention provides;

The compute phase noise time domain that Fig. 5 provides for the embodiment of the present invention and the schematic diagram of frequency domain statistical average;

The schematic flow sheet that Fig. 6 estimates for the amplitude fading that the embodiment of the present invention provides;

The weighting procedure schematic diagram that Fig. 7 provides for the embodiment of the present invention;

The self adaptation transmission flow schematic diagram of making a start that Fig. 8 provides for the embodiment of the present invention;

Fig. 9 is the structured flowchart of the present invention's two blind Channel self-reacting device;

The calculating phase angle that Figure 10 provides for the embodiment of the present invention the structured flowchart of quantization modules;

The structured flowchart of the phase noise estimation module that Figure 11 provides for the embodiment of the present invention;

The structured flowchart of the weighting block that Figure 12 provides for the embodiment of the present invention;

Figure 13 (a) is the amplitude-versus-frequency curve of multipath channel in the embodiment of the present invention;

Under the multipath channel environment of Figure 13 (b) for emulation in the embodiment of the present invention, receive signal amplitude-versus-frequency curve;

Figure 13 (c) is phase of received signal noise characteristic curve under the multipath channel environment of emulation in the embodiment of the present invention;

Figure 14 receives average amplitude attenuation curve and the average phase noise curve of signal under the Gaussian channel environment of emulation in the embodiment of the present invention;

Figure 15 (a) is time domain waveform and the spectrum waveform of the reception signal of emulation in the embodiment of the present invention;

Figure 15 (b) is the average amplitude decay waveform of emulation in the embodiment of the present invention;

Figure 15 (c) is the average phase noise pattern of emulation in the embodiment of the present invention.

Embodiment

Below in conjunction with accompanying drawing, the invention will be further described.

Application scenarios of the present invention is half-duplex, symmetric channel, and receiving-transmitting sides adopts constant amplitude phase-modulation, and constellation mapping point is on same circle.

Refer to Fig. 1, one of the present invention's blind Channel adaptive approach, comprises the following steps:

Step S0, phase noise is estimated, the phase deviation according to input signal at planisphere, respectively at time domain (based on symbol) and frequency domain (based on carrier wave) statistics phase noise;

Step S1, amplitude fading is estimated, according to the amplitude of input signal, is added up amplitude fading respectively on time domain and frequency domain;

Step S2, Interference Detection, based on default interference threshold, detects the impulse disturbances of input signal;

Step S3, weighting, according to default weight coefficient, phase noise and amplitude fading are processed in weighting, obtain the estimated value of the quality of channel;

Step S4, channel self-adapting, according to the estimated value of channel quality, based on preset channel thresholding, obtains channel self-adapting information;

Step S5, self adaptation sends, and according to the channel self-adapting information of receiving end feedback, makes a start and adjusts the transmission parameter of data.

Wherein, as shown in Figure 2, step S0 specifically comprises:

Step S00, the phase angle of calculating input signal (being comprised of real part I and imaginary part Q), realizes input signal from rectangular coordinate to polar conversion; Specifically refer to calculate the value of arctan (Q/I), span be [0,2 π), wherein, if input signal has carried out differential modulation making a start, here by differential ference spiral value afterwards;

Step S01, the phase value amount even amount that step S00 is obtained changes into some bits, and compromise consideration resource consumption and performance are selected suitable quantization digit, use 7 bit quantizations in embodiment, and concrete quantization method is

wherein θ is input phase angle, and [] is rounding operation;

Step S02, the phase quantization value based on step S01 output, by non-uniform quantizing, completes demapping process, exports soft bit, facilitates follow-up soft decoding; In embodiment, selecting 3 bit quantizations, as shown in Figure 3, is the BPSK(binary phase shift keying that embodiment provides) and QPSK(quaternary phase shift keying) mapping and the process schematic diagram of demapping;

For BPSK modulation system, (a) in Fig. 3 is the signal constellation and mapping of making a start, (b) in Fig. 3 carries out the planisphere after 7 bit quantizations in receiving end step S01, and (c) in Fig. 3 is the planisphere of further non-uniform quantizing demapping, and non-uniform quantizing mode is as shown in table 1 below.Wherein, the first hurdle is corresponding to the 7bit quantized value of step S01, and the second hurdle is corresponding soft bit, and this quantification manner has carried out large step-length and quantized in the high region of confidence level, the long quantification of small step has been carried out in the region that confidence level is low, thereby has improved the error rate of demapping.

Uniform quantization value	Non-uniform quantizing value
		0<=x<=15 112<=x<=127	0
16<=x<=23 104<=x<=111	1
		24<=x<=28 99<=x<=103	2
29<=x<=31 96<=x<=98	3
		32<=x<=34 93<=x<=95	4
35<=x<=39 88<=x<=92	5
		40<=x<=47 80<=x<=87	6
48<=x<=63 64<=x<=79	7

Table 1

For QPSK modulation system, (d) in Fig. 3 is the signal constellation and mapping of making a start, adopt the quantification planisphere of (b) in Fig. 3, first bit and second bit are carried out respectively to non-uniform quantizing, similar with above-mentioned BPSK quantization method, (e) in Fig. 3 is the planisphere of first bit demapping, corresponding to table 2(a), (f) in Fig. 3 is the planisphere of second bit demapping, corresponding to table 2(b).

Uniform quantization value	Non-uniform quantizing value
		0<=x<=31	0
32<=x<=39 120<=x<=127	1
		40<=x<=44 115<=x<=119	2
45<=x<=47 112<=x<=114	3
		48<=x<=50 109<=x<=111	4
51<=x<=55 104<=x<=108	5
		56<=x<=63 96<=x<=103	6
64<=x<=104	7

Table 2(a)

Uniform quantization value	Non-uniform quantizing value
		94<=x<=127	0
0<=x<=7 88<=x<=95	1
		8<=x<=12 83<=x<=87	2
13<=x<=15 80<=x<=82	3
		16<=x<=18 77<=x<=79	4
19<=x<=23 72<=x<=76	5
		24<=x<=31 64<=x<=71	6
32<=x<=63	7

Table 2(b)

Above-mentioned demapping mode is a preferred embodiment, and this non-uniform quantizing mode can improve the performance of demapping; Also the modulation system of high-order more, or other demapping mode.

Step S03, the phase quantization value based on input sample point, calculates phase deviation, as shown in Figure 4, is the schematic diagram of integrating step S02 embodiment.

For BPSK modulation system, phase deviation be pi/2 to the maximum, corresponding to the quantized value of step S01, be 32, phase deviation computational process as shown in (a) in Fig. 4～(e), 7bit quantized result [0,127], first add 32, reference axis rotation pi/2, obtains [0,127], then remaining (MOD) 64 of mould, obtains [0,63], after deducting 32 [32,31], obtaining after taking absolute value [0,32], is phase noise estimated value.

For QPSK modulation system, phase deviation be π/4 to the maximum, corresponding to the quantized value of step S01, be 16, phase deviation computational process as shown in (f) in Fig. 4～(j), quantized result [0,127], first+16, reference axis rotation π/4, obtain [0,127], then remaining (MOD) 32 of mould, obtains [0,31], after deducting 32 [16,15], obtaining after taking absolute value [0,16], is phase noise estimated value.

In addition, if indicate this sampled point for there is large impulse disturbances, phase noise is directly arranged to deviation maximum, avoids interference the phase-detection error causing.For other modulation systems, the process of compute phase noise is similar.

Step S04, according to step, S03 obtains phase noise, and at time domain and frequency domain statistics phase noise, process schematic diagram is as shown in Figure 5 respectively.

In the present embodiment, the symbol numbers of blind estimation is M, and effectively subcarrier number is N, and the phase noise of each sampled point being obtained by step S03 is P_noise (i, j), and wherein i represents symbol sequence number, and j represents subcarrier sequence number, can obtain:

Frequency domain phase noise average is: $P\_\mathrm{noise}\_c\left(j\right)=[\underset{i=0}{\overset{M-1}{\mathrm{\Σ}}}P\_\mathrm{noise}(i,j)]/M;$

Time domain phase noise average is: $P\_\mathrm{noise}\_s\left(i\right)=[\underset{j=0}{\overset{N-1}{\mathrm{\Σ}}}P\_\mathrm{noise}(i,j)]/N;$

Wherein, 0≤i≤M-1,0≤j≤N-1.

Wherein, as shown in Figure 6, step S1 specifically comprises:

Step S10, the amplitude of calculating input signal, exact value is the arithmetic square root of the quadratic sum of real part (I) and imaginary part (Q)

in concrete system, be simplified operation, may get real part absolute value or imaginary part absolute value or both coefficient weightings, for example, if the point after constellation mapping concentrates on real axis or the imaginary axis, can only get real part absolute value or imaginary part absolute value as amplitude;

Step S11, according to the amplitude range of input signal, uniform quantization amplitude, quantization method and step S01 are similar, are quantified as 7bit in the present embodiment, if this sampled point exists large interference, are directly quantized into 0, and amplitude range can obtain according to average power;

Step S12, based on quantization amplitude, at time domain and frequency domain statistical average amplitude fading, method and step S04 are similar respectively, obtain frequency domain amplitude fading average Mag_c and time domain amplitude fading average Mag_s.

Wherein, step S2, is to detect whether this sampled point is to have large impulse disturbances, and the power of sampled point is compared with default interference threshold, if be greater than one of thresholding output, disturbs index signal.Default interference threshold setting able to programme, preferably, can be set to the 10dB of average energy value.

Wherein, as shown in Figure 7, step S3 specifically comprises:

Step S30, phase noise is processed, and deducts current phase noise obtain a new phase noise expression value by the maximum that phase noise occurs; Phase noise P_noise_c/P_noise_s value is larger, and channel quality is more bad, and Mag_c/Mag_s value is larger, and channel quality is better, represents the value of phase noise with Phase_c/Phase_s, and this value is larger, and channel quality is better:

Phase_c=（max(P_noise_c)-P_noise_c），

Phase_s=（max(P_noise_s)-P_noise_s）。

In the present embodiment, for BPSK modulation system, Phase_c=(32-P_noise_c), Phase_s=(32-P_noise_s); For QPSK modulation system, Phase_c=(16-P_noise_c), Phase_s=(16-P_noise_s).

Step S31, amplitude fading is processed, and this step is optional, in order to keep Phase_c/Phase_s and Mag_c/Mag_s to have identical bit wide, carry out cut position or increase position processing, amplitude fading is normalized into new phase noise expression value and has identical bit wide;

Step S32, weighting, the phase noise expression value that step S30 is obtained is multiplied by weight coefficient α, and the amplitude fading that step S31 is obtained is multiplied by weight coefficient β, and acquired results is added the estimated value that obtains channel quality; Weighting expression formula is as follows:

Channel_c(j)=α*Phase_c(j)+β*Mag_c(j)；

Channel_s(i)=α*Phase_s(i)+β*Mag_s(i)；

Wherein, 0≤i≤M-1,0≤j≤N-1;

Thereby obtain the estimated value (Channel_c/Channel_s) of channel quality, the span of weight coefficient α and β is [0,1], and meets alpha+beta=1, in concrete system, according to phase noise and amplitude fading impact in various degree to received signal, weight coefficient is adjusted flexibly, for example, in differential system, receive the impact that signal is mainly subject to phase noise, a kind of simple processing mode is α=1 to be set, β=0.

Wherein, step S4, according to the estimated value of channel quality (Channel_c/Channel_s), based on preset channel threshold value, statistics subcarrier quality, the frequency that time-domain symbol pulse occurs, estimate overall channel quality average, and rule out modulation system, select effective subcarrier number, estimate sub-band decay and calculate transmitting power, these channel self-adapting information are made a start.

In embodiment system, there are three kinds of optional modulation systems, respectively that robust-BPSK(data message repeated n doubly before mapping), BPSK, and QPSK, default two carrier channel thresholding Th_c1, Th_c2, and Th_c1<Th_c2, be worth littlely, phase noise is larger, by these two values, characterizes phase noise grades; Two symbol thresholding Th_s1, Th_s2, and Th_s1<Th_s2, be worth littlely, and amplitude fading is larger, by these two values, characterizes amplitude fading grades; Step S4 specifically comprises:

Step S40, by Channel_s (i) respectively with Th_s1, Th_s2 comparison, if Channel_s (i) is less than Th_s1, Cnt_s1 adds 1, if Channel_s (i) is less than Th_s2, Cnt_s2 adds 1; Wherein, Cnt_s is for adding up the symbol numbers of different amplitude fading grades, and Cnt_s1 counting is less than the symbol numbers of thresholding Th_s1, and Cnt_s2 counting is less than the symbol numbers of thresholding Th_s2.

Step S41, by Channel_c (j) respectively with Th_c1, Th_c2 comparison, if Channel_c (j) is greater than Th_c1, Cnt_c1 adds 1, carrier_map1(j) puts 1, otherwise sets to 0; If Channel_c (j) is greater than Th_c2, Cnt_c2 adds 1, carrier_map2(j) puts 1, otherwise sets to 0; Wherein, Cnt_c is for adding up the carrier wave number of out of phase noise grade, and Cnt_c1 counting is greater than the symbol numbers of thresholding Th_c1, and Cnt_c2 counting is greater than the symbol numbers of thresholding Th_c2; Carrier_map form is for recording subcarrier effective or invalid of out of phase noise grade, carrier_map1 is corresponding to the effective subcarrier mapping table under BPSK pattern, carrier_map2 is corresponding to the effective subcarrier mapping form under QPSK pattern, put this subcarrier of 1 expression effectively available, set to 0 represent that this subcarrier is invalid need not;

Step S42, the average of calculating Channel_c (j), obtains $\mathrm{Channel}\_\mathrm{avg}=[\underset{j=0}{\overset{N}{\mathrm{\&Sigma;}}}\mathrm{Channel}\_c\left(j\right)]/N;$ Channel_avg represents the average of total channel quality estimation value, can adjust transmitting power based on this.

Step S43, reference table 3 selects to satisfy condition modulation system, if do not meet the requirement of form, modulation system is selected robust-BPSK, if meet BPSK and QPSK modulation, relatively Cnt_c1 simultaneously, the size of Cnt_c2, if meet Cnt_c1>2*Cnt_c2, select BPSK modulation, otherwise select QPSK.

Table 3

In condition stub in above table 3, the number of parameter and large I are adjusted according to concrete system, have only provided one group here and have implemented parameter.

Step S44, has determined after modulation system, and the corresponding carrier_map of step S41 is effective subcarrier sequence number array, if be chosen as robust-BPSK, carrier_map is default setting; If be chosen as BPSK, effectively subcarrier sequence number array is carrier_map1, if be chosen as QPSK, effectively subcarrier sequence number array is carrier_map2; Channel_c is corresponding to the channel quality of subcarrier, and the quality of the larger corresponding frequency band of value is better, also can according to this value, calculate the grouping quality of subcarrier, and the channel quality of sub-band, can calculate sub-band power partition coefficient based on this value;

Certainly based on Channel_s and Channel_c, can also calculate other channel self-adapting information, such as coded system, interleaving mode etc., be not limited to the present embodiment.

Wherein, as shown in Figure 8, step S5 specifically comprises:

Step S50, modulation system based on selecting, data-mapping on corresponding constellation point, if channel quality is relatively good, a constellation point adopts many bit mappings, contrary, if channel quality is bad, a constellation point adopts few bit mapping, is guaranteeing, under the prerequisite of transmission quality, to realize the maximization of channel resource;

Step S51, according to effective subcarrier sequence number array carrier_map information, only at the upper valid data of placing of the good subcarrier of channel quality (or sub-band), improves the reliability of transmission quality;

Step S52, according to the channel quality Channel_c information of subcarrier, frequency domain increases the weight of sub-band (or subcarrier) power, power on subcarrier is carried out to reasonable distribution, keeping under the constant prerequisite of the total transmitting power of frequency domain, reduce the power on the good sub-band of quality, increase the power on second-rate sub-band, by reasonable distribution power, realize the raising of the performance of system;

Step S53, according to Channel_avg average and selected modulation system, time domain is adjusted transmitting power, the in the situation that of guaranteed performance, selects little transmitting power as far as possible, reduces power consumption.

Refer to Fig. 9, the present invention's two the blind Channel self-reacting device based on blind Channel adaptive approach, comprising: calculate phase angle quantization modules 01, demapping module 02, phase noise estimation module 03, calculate amplitude quantization modules 04, amplitude fading estimation module 05, interference detection module 06, weighting block 07, channel self-adapting module 08 and self adaptation sending module 09; Calculate phase angle quantization modules 01 connection demapping module 02 and phase noise estimation module 03; Phase noise estimation module 03 connects weighting block 07; Calculate amplitude quantization modules 04 connection interference detection module 06 and amplitude fading estimation module 05; Amplitude fading estimation module 05 connects weighting block 07; Interference detection module 06 connects phase noise estimation module 03 and amplitude fading estimation module 05; Weighting block 07 connecting channel adaptation module 08; Channel self-adapting module 08 connects self adaptation sending module 09, wherein:

Calculate phase angle quantization modules 01 for calculating the phase angle of input signal, and even amount changes into some bits, pass to demapping module 02 and phase noise estimation module 03; As shown in figure 10, calculate phase angle quantization modules 01 and comprise: calculating unit, phase angle 011 and phase quantization unit 012, wherein:

Calculating unit, phase angle 011 is for realizing rectangular coordinate to polar conversion, with CORDIC(rotation of coordinate numerical calculation method) algorithm realizes, and obtains the value of the phase angle of input signal, span be [0,2 π);

Phase quantization unit 012 changes into some bits the value even amount of phase angle, by the first multiplier 0121, the first divider 0122 with round unit 0123 and form, wherein:

The first multiplier 0121 is realized input phase angle and 2 ⁿthe multiplication of (n is quantization bit), also can realize multiplication by the n bit that moves to right; Corresponding to embodiment of the method step S01, n=7;

The first divider 0122 for by the output of the first multiplier 0121 divided by 2 π, make output normalize to [0,2 ⁿ];

Round unit 0123 and take out integer-bit output, output valve is [0,2 ^n-1] between integer.

Demapping module 02, according to phase angle quantized value, realizes the inverse process of mapping by non-uniform quantizing, give follow-up decoder module, and demapping module 02 comprises form stores unit and lookup unit, wherein:

Form stores unit, for storing phase angle to the index of mapped bits; In conjunction with above-mentioned embodiment of the method, if modulation system is robust-BPSK or BPSK, look-up table 1, if modulation system QPSK, look-up table 2(a) and table 2(b); In concrete system, generally there is plurality of optional modulation system, often will store a plurality of mapping tables;

Lookup unit, for realizing phase angle to the Index process of mapped bits.

Phase noise estimation module 03, the phase deviation based on phase angle quantized value on planisphere, statistical average phase noise on symbol and on carrier wave, as shown in figure 11, phase noise estimation module 03 comprises:

Phase deviation computing unit 031, for calculating the deviation of phase place on planisphere, is comprised of unit 0312, the first subtracter 0313 and the unit 0314 that takes absolute value more than the first adder 0311 being connected in series successively, mould, wherein:

First adder 0311 is realized the signal and 2 of its input ⁿ¹addition, n1 is quantization bit, associated methods embodiment, for robust-BPSK or BPSK, n1=5, for QPSK, n1=4;

The remainder number of the signal of its input is realized in the remaining unit 0312 of mould;

The signal that the first subtracter 0313 is realized its input deducts 2 ⁿ¹;

Take absolute value unit 0314 the signal normalization to 2 of its input ⁿ¹in scope.

Phase deviation computing unit 031 can associated methods embodiment step S03 implement.

Phase noise statistic unit 032, be used for statistical average phase noise on symbol and on carrier wave respectively, obtain symbol phase noise and Carrier Phase Noise, as shown in figure 11, by the first accumulator 0321, the second accumulator 0322, Carrier Phase Noise memory 0323, symbol phase noise memory 0324, the second divider 0325 and the 3rd divider 0326, formed, wherein:

The first accumulator 0321 is for cumulative current sign Carrier Phase Noise and the corresponding Carrier Phase Noise of symbol before;

The second accumulator 0322 is for the cumulative all Carrier Phase Noises of current sign;

Carrier Phase Noise memory 0323 is for storing the cumulative sum of each symbol carrier phase noise, and length equals carrier wave number;

Symbol phase noise memory 0324 is for storing the cumulative sum of each carrier wave symbol phase noise, length equal symbol number;

The second divider 0325 is realized the cumulative sum of Carrier Phase Noise and the division of symbol numbers M, obtains the average of Carrier Phase Noise;

The 3rd divider 0326 is realized the cumulative sum of symbol phase noise and the division of carrier wave number N, obtains the average of symbol phase noise.

Phase noise statistic unit 032 can associated methods embodiment step S04 implement.

Calculate amplitude quantization modules 04, for calculating the amplitude of input signal, and even amount changes into some bits, comprising:

Calculate amplitude unit, for calculating the amplitude of input signal, the exact value of amplitude is the arithmetic square root of the quadratic sum of real part (I) and imaginary part (Q)

this unit is by squarer, and adder and extraction of square root unit form, and are simplified operation, and amplitude may be got real part absolute value or imaginary part absolute value or both coefficient weightings, and now this unit comprises the unit that takes absolute value, multiplier and adder.

Amplitude quantization unit, for amplitude even amount is changed into some bits, similar with the composition of phase quantization unit 012 in Figure 10, comprise multiplier, divider and round unit.

Amplitude fading estimation module 05, based on amplitude quantizing value, statistical average amplitude fading on symbol and on carrier wave is identical with the composition of phase noise statistic unit 032 in Figure 11.

Interference detection module 06, the size of the amplitude of comparison signal and default interference threshold value, while being greater than thresholding, index signal is disturbed in output, comprises a comparator, and comparator is a subtracter, realizes the subtraction of interference threshold and amplitude.

Weighting block 07, according to weight coefficient, phase noise and amplitude attenuation are processed in weighting, obtain channel quality estimation value, as shown in figure 12, comprising:

Phase noise processing unit 071, deducts respectively symbol phase noise and Carrier Phase Noise by the maximum of phase noise, obtains phase noise processing costs, by a subtracter, realizes this module;

Amplitude fading processing unit 072, an amplitude fading value is processed in cut position or increasing position, makes it have identical bit wide with phase noise processing costs, obtains amplitude fading processing costs;

The second multiplier 073, realizes the multiplication of the processing costs of weight coefficient α and phase noise;

The 3rd multiplier 074, realizes the multiplication of weight coefficient β and amplitude fading processing costs;

Second adder 075, realizes phase noise processing costs after multiplication process and the addition of amplitude fading processing costs, obtains symbol quality estimated value and carrier channel quality estimated value;

Weighting block 07 can associated methods embodiment step S3 implement.

Channel self-adapting module 08, according to the estimated value of channel quality of input, based on preset channel thresholding, compares, counts and judgement obtains channel self-adapting information, and obtaining channel self-adapting information to self adaptation sending module, channel self-adapting module 08 comprises:

Comparator, for relatively symbol channel quality estimation value and carrier channel quality estimated value and corresponding default symbol thresholding and the size of default carrier channel thresholding;

Counter, for measuring the carrier wave number that is less than the symbol numbers of default symbol thresholding and is greater than default carrier channel thresholding;

Average module, for calculating the average of carrier channel quality estimated value;

Modulation system determining unit, for determining modulation system based on count value and average;

Effective subcarrier determining unit, the modulation system based on definite, determines corresponding effective subcarrier sequence number;

Calculate sub-band gain coefficient unit, for carrier channel quality estimated value is converted to corresponding sub-band gain coefficient;

Calculate transmitting power coefficient elements, the modulation system based on definite and channel quality estimation average, the coefficient of calculating transmitting power.

Step S4 in associated methods embodiment, channel self-adapting module 08 comprises two comparator C mp_1/Cmp_2, four counter Cnt_s1/Cnt_s2/Cnt_c1/Cnt_c2, two subcarrier mapping table carrier_map1/carrier_map2 and average module.

Comparator C mp_1 is for comparing the size of Channel_s (i) and Th_s1 and Th_s2; If Channel_s (i) is less than Th_s1, counter Cnt_s1 adds 1, if Channel_s (i) is less than Th_s2, counter Cnt_s2 adds 1;

Comparator C mp_2 is for comparing Channel_c(j) and Th_c1, and the size of Th_c2, if Channel_c (j) is greater than Th_c1, counter Cnt_c1 adds 1, carrier_map1(j) puts 1, otherwise sets to 0; If Channel_c (j) is greater than Th_c2, counter Cnt_c2 adds 1, carrier_map2(j) puts 1, otherwise sets to 0;

The average that average module is used for calculating Channel_c (j) obtains Channel_avg.

Modulation system determining unit is for selecting suitable modulation system, reference table 3, if do not meet the requirement of form, modulation system is selected robust-BPSK, if meet BPSK and QPSK modulation, relatively Cnt_c1 simultaneously, the size of Cnt_c2, if meet Cnt_c1>2*Cnt_c2, select BPSK modulation, otherwise select QPSK.

Effectively subcarrier determining unit, based on determining of modulation system, selects corresponding subcarrier mapping table carrier_map1/carrier_map2 or acquiescence carrier_map.

Calculate sub-band gain coefficient unit, the value of Channel_c is directly proportional to the channel quality of subcarrier, calculates the inverse of Channel_c, according to gain step size, is encoded into sub-band gain coefficient;

Calculate transmitting power coefficient elements, the value of Channel_avg and total channel quality are proportional, calculate the inverse of Channel_avg, and are encoded into transmitting power gain coefficient according to certain step-length.

Self adaptation sending module 09, for according to the channel self-adapting information of input, by adjusting the transmission parameter of data, realizes channel self-adapting, comprising:

Modulation system selected cell, the modulation system of coming according to receiving end feedback, selects corresponding modulation module, data-mapping on corresponding constellation point;

Effective sub-carrier allocation unit, according to receiving end, feed back the effective subcarrier sequence number (carrier_map) of coming, only, at effective subcarrier transmitting data, other carrier wave is placed dummy data or zero setting, in addition, this unit can be also a sub-frequency bands selected cell;

Sub-band power distributing unit, the sub-band decay gain coefficient of coming according to receiving end feedback, input sub-band signal is multiplied by the adjustment that corresponding gain coefficient is realized sub-band power, with multiplier, realizes;

Transmitting power adjustment unit, the transmitting power coefficient of coming according to receiving end feedback, guarantees be no more than under the prerequisite of maximum transmission power, and input signal is multiplied by the adjustment that transmitting power coefficient is realized transmitting power, with multiplier, realizes.

Use MATLAB instrument to carry out emulation to the present embodiment, Figure 13 (a) is the amplitude-versus-frequency curve of 15 multipath channels adopting in embodiment; Under the channel circumstance of Figure 13 (a), receive the amplitude-versus-frequency curve of signal as shown in Figure 13 (b).

Receive the phase noise characteristic curve of signal as shown in Figure 13 (c), from Figure 13 (b) and Figure 13 (c), can find out that the amplitude of reception signal can reflect the variation of multipath channel well, and phase noise reflection is very rough; Wherein, frequency is corresponding to the subcarrier sequence number in diagram.

Figure 14 is average amplitude attenuation curve and the average phase noise curve that receives signal in embodiment under Gaussian channel environment, can find out the increase along with signal to noise ratio, average amplitude pad value changes little, average phase noise changes obviously, so average phase decay can reflect the size of signal to noise ratio well.

As shown in Figure 15 (a) shows, time domain waveform and the spectrum waveform of the reception signal of the emulation in embodiment, the multipath channel environment of simulated environment based on Figure 13 (a), the white Gaussian noise of stack 0dB, two the large time domain impulse disturbances (impus_t1 and impus_t2) that superpose and the frequency domain impulse disturbances (impus_f) that superposes on fixing subcarrier, specifically as shown in Figure 15 (a) shows, channel circumstance is very severe.

Based on Figure 15 (a), Figure 15 (b) is the waveform of Symbol average amplitude fading (Mag_s in above-mentioned) and the waveform of carrier wave average amplitude decay (Mag_c in above-mentioned) of emulation in embodiment, can find out that Mag_s can reflect the interference (detect_t1 and detect_t2) of two large time domain pulses on symbol, Mag_c can reflect the variation tendency of multipath channel, based on Interference Detection, can reflect the subcarrier sequence number (detect_f place) that is greater than interference threshold.

Based on Figure 15 (a), Figure 15 (c) is the waveform of symbol phase noise (P_noise_s in above-mentioned) and the figure of Carrier Phase Noise (P_noise_c in above-mentioned) of emulation in embodiment, can find out that the value of P_noise_s on each symbol is basically identical, can not reflect the interference of large time domain pulse on symbol, this is that P_noise_c can clearly reflect the subcarrier sequence number (detect_f place) that is greater than interference threshold because transmitted signal has been carried out time-domain difference.

In sum, employing adds up respectively phase noise on symbol and on carrier wave and amplitude fading can reflect the variation of multipath and the variation of signal to noise ratio exactly, can identify the large pulse of time domain and the large pulse of frequency domain, the weighting based on the two, can realize channel self-adapting well.

Above embodiment is used for illustrative purposes only, but not limitation of the present invention, person skilled in the relevant technique, without departing from the spirit and scope of the present invention, can also make various conversion or modification, therefore all technical schemes that are equal to also should belong to category of the present invention, should be limited by each claim.

Claims (22)

1. a blind Channel adaptive approach, is characterized in that, comprises the following steps:

Step S0, phase noise is estimated, the phase deviation according to input signal at planisphere, respectively at time domain and frequency domain statistics phase noise;

Step S1, amplitude fading is estimated, according to the amplitude of input signal, is added up amplitude fading respectively on time domain and frequency domain;

Step S2, Interference Detection, based on default interference threshold, detects the impulse disturbances of input signal;

Step S3, weighting, according to default weight coefficient, phase noise and amplitude fading are processed in weighting, obtain the estimated value of channel quality;

Step S4, channel self-adapting, according to the estimated value of channel quality, based on preset channel thresholding, obtains channel self-adapting information;

Step S5, self adaptation sends, and according to the channel self-adapting information of receiving end feedback, makes a start and adjusts the transmission parameter of data.

2. blind Channel adaptive approach according to claim 1, is characterized in that, described step S0 comprises:

Calculate the phase value amount of input signal;

Phase quantization, based on Interference Detection, changes into some bits the phase value amount even amount obtaining;

According to the phase quantization result obtaining, the calculating phase deviation on planisphere, and on time domain and frequency domain, carry out respectively statistical average.

3. blind Channel adaptive approach according to claim 1 and 2, is characterized in that, the input signal of described step S0, for differential modulation mode, refers to differential ference spiral signal afterwards.

4. blind Channel adaptive approach according to claim 2, is characterized in that, described phase quantization result also, by non-uniform quantizing, completes demapping process, exports soft bit, processes to follow-up soft decoding.

5. blind Channel adaptive approach according to claim 1, is characterized in that, described step S1 comprises:

According to the real part of input signal and imaginary part, calculate amplitude;

Based on Interference Detection, the amplitude even amount obtaining is changed into some bits;

According to amplitude quantization result, on time domain and frequency domain, carry out respectively statistical average.

6. blind Channel adaptive approach according to claim 1 or 5, is characterized in that the input signal of described step S1 has identical amplitude on the planisphere of making a start.

7. blind Channel adaptive approach according to claim 5, is characterized in that, described amplitude, and its standard value is the arithmetic square root of the quadratic sum of real part and imaginary part.

8. blind Channel adaptive approach according to claim 1, is characterized in that, described step S2 specifically refers to: by the amplitude of comparator input signal and the size of default interference threshold, obtain disturbing index signal.

9. blind Channel adaptive approach according to claim 1, is characterized in that, described step S3 specifically comprises:

Step S30, deducts current phase noise by the maximum that phase noise occurs and obtains a new phase noise expression value;

Step S31, is normalized into amplitude fading with new phase noise expression value and has identical bit wide;

Step S32, the phase noise expression value that step S30 is obtained is multiplied by weight coefficient α, and the amplitude fading that step S31 is obtained is multiplied by weight coefficient β, and acquired results is added the estimated value that obtains channel quality.

10. blind Channel adaptive approach according to claim 9, is characterized in that, the span of described weight coefficient α and β is [0,1], and meets alpha+beta=1.

11. blind Channel adaptive approachs according to claim 1, is characterized in that, described step S4 comprises:

Step S40, compares the size of symbol channel quality estimation value and default symbol thresholding and carries out symbol quality counting;

Step S41, compares the size of carrier channel quality estimated value and default carrier channel thresholding and carries out carrier-quality counting;

Step S42, the average of calculating carrier channel quality estimated value obtains the whole average of the quality of channel;

Step S43, the average of the count value based on step S40, S41 and step S42 rules out modulation system;

Step S44, selects effective subcarrier number, estimates sub-band decay, and calculates transmitting power.

12. blind Channel adaptive approachs according to claim 11, is characterized in that, described step S5 comprises:

Step S50, the modulation system based on selecting, data-mapping on corresponding constellation point;

Step S51, selects only secured transmission of payload data on effective subcarrier or on sub-band;

Step S52 according to sub-band attenuation, keeping, under the constant prerequisite of the total transmitting power of frequency domain, reducing transmitting power on the good sub-band of quality, increases transmitting power on second-rate sub-band;

Step S53, raises whole transmitting power in time domain.

13. 1 kinds of blind Channel self-reacting devices based on blind Channel adaptive approach described in claim 1, it is characterized in that, comprise and calculate phase angle quantization modules, demapping module, phase noise estimation module, calculating amplitude quantization modules, amplitude fading estimation module, interference detection module, weighting block, channel self-adapting module and self adaptation sending module; Described calculating phase angle quantization modules connect demapping module and phase noise estimation module; Described phase noise estimation module connects described weighting block; Described calculating amplitude quantization modules connect described interference detection module and amplitude fading estimation module; Described amplitude fading estimation module connects weighting block; Described interference detection module connects phase noise estimation module and amplitude fading estimation module; Described weighting block connects described channel self-adapting module; Described channel self-adapting module connects described self adaptation sending module, wherein:

Calculate phase angle quantization modules, for calculating the phase angle of input signal, even amount is passed to described demapping module and phase noise estimation module after changing into some bits;

Demapping module, according to the phase angle quantized value receiving, realizes the inverse process of mapping by non-uniform quantizing, give follow-up decoder module;

Phase noise estimation module, the phase deviation based on phase angle quantized value on planisphere, statistical average phase noise on symbol and on carrier wave, result is passed to described weighting block;

Calculate amplitude quantization modules, for calculating the amplitude of input signal, even amount is passed to described amplitude fading estimation module and interference detection module after changing into some bits;

Amplitude fading estimation module, based on amplitude quantizing value, statistical average amplitude fading on symbol and on carrier wave, result is passed to described weighting block;

Interference detection module, by the amplitude of comparison signal and the size of default interference threshold value, while being greater than thresholding, output disturbs index signal to described phase noise estimation module and amplitude fading estimation module;

Weighting block, according to weight coefficient, phase noise and amplitude attenuation are processed in weighting, and the channel quality estimation value obtaining is passed to described channel self-adapting module;

Channel self-adapting module, the channel quality estimation value according to input, based on preset channel thresholding, compares, counts and judgement obtains channel self-adapting information, and result is passed to described self adaptation sending module;

Self adaptation sending module, according to the channel self-adapting information of input, by adjusting the transmission parameter of data, realizes channel self-adapting.

14. blind Channel self-reacting devices according to claim 13, is characterized in that, described calculating phase angle quantization modules comprise calculating unit, phase angle and phase quantization unit, wherein:

Calculating unit, phase angle, for realizing rectangular coordinate to polar conversion, obtains the value of the phase angle of input signal;

Phase quantization unit, changes into some bits for the value even amount phase angle, passes to described demapping module and phase noise estimation module.

15. blind Channel self-reacting devices according to claim 14, is characterized in that, described phase quantization unit comprises the first multiplier, the first divider and round unit, wherein:

The first multiplier is realized input phase angle and 2 ⁿmultiplication, n is quantization bit;

The first divider for by the output of the first multiplier divided by 2 π, make output normalize to [0,2 ⁿ];

Round unit and take out integer-bit output, output valve is [0,2 ^n-1] between integer.

16. blind Channel self-reacting devices according to claim 13, is characterized in that, described demapping module comprises form stores unit and lookup unit, wherein:

Form stores unit, for storing phase angle to the index of mapped bits;

Lookup unit, for realizing phase angle to the Index process of mapped bits.

17. blind Channel self-reacting devices according to claim 13, is characterized in that, described phase noise estimation module comprises phase deviation computing unit and phase noise statistic unit, wherein:

Phase deviation computing unit, based on Interference Detection index signal, for calculating the deviation of phase place on planisphere, by the first adder being connected in series successively, mould remaining unit, the first subtracter and the unit that takes absolute value form, wherein:

First adder is realized the signal and 2 of its input ⁿ¹addition, n1 is quantization bit;

The remainder number of the signal of its input is realized in the remaining unit of mould;

The signal that the first subtracter is realized its input deducts 2 ⁿ¹;

Take absolute value unit the signal normalization to 2 of its input ⁿ¹in scope;

Phase noise statistic unit, be used for statistical average phase noise on symbol and on carrier wave respectively, obtain symbol phase noise and Carrier Phase Noise, comprise the first accumulator, the second accumulator, Carrier Phase Noise memory, symbol phase noise memory, the second divider and the 3rd divider, wherein:

The first accumulator, for cumulative current sign Carrier Phase Noise and the corresponding Carrier Phase Noise of symbol before;

The second accumulator, for the cumulative all Carrier Phase Noises of current sign;

Carrier Phase Noise memory, for storing the cumulative sum of each symbol carrier phase noise, length equals carrier wave number;

Symbol phase noise memory, for storing the cumulative sum of each carrier wave symbol phase noise, length equal symbol number;

The second divider, realizes the division of cumulative sum and the symbol numbers of Carrier Phase Noise, obtains the average of Carrier Phase Noise;

The 3rd divider, realizes the division of cumulative sum and the carrier wave number of symbol phase noise, obtains the average of symbol phase noise.

18. blind Channel self-reacting devices according to claim 13, is characterized in that, described calculating amplitude quantization modules comprise amplitude computing unit and amplitude quantization unit, wherein:

Amplitude computing unit, for calculating the amplitude of input signal;

Amplitude quantization unit, for amplitude quantization being become to some bits, gives described interference detection module and amplitude fading estimation module.

19. blind Channel self-reacting devices according to claim 13, is characterized in that, described amplitude fading estimation module is identical with the composition of described phase noise statistic unit.

20. blind Channel self-reacting devices according to claim 13, is characterized in that, described weighting block comprises phase noise processing unit, amplitude fading processing unit, the second multiplier, the 3rd multiplier and second adder, wherein,

Phase noise processing unit, deducts respectively symbol phase noise and the Carrier Phase Noise of input by the maximum of phase noise, obtain phase noise processing costs;

Amplitude fading processing unit, for keeping amplitude fading to have identical bit wide with phase noise processing costs, obtains amplitude fading processing costs;

The second multiplier, is multiplied by the processing costs of phase noise for realizing weight coefficient α;

The 3rd multiplier, is multiplied by amplitude fading processing costs for realizing weight coefficient β;

Second adder, for realizing phase noise processing costs after multiplication process and the weighting of amplitude fading processing costs, obtains symbol quality estimated value and carrier channel quality estimated value.

21. blind Channel self-reacting devices according to claim 13, is characterized in that, described channel self-adapting module comprises comparator, counter and decision device, wherein:

Comparator, for relatively symbol channel quality estimation value and carrier channel quality estimated value and corresponding default symbol thresholding and the size of default carrier channel thresholding;

Counter, for counting the carrier wave number that is less than the symbol numbers of default symbol thresholding and is greater than default carrier channel thresholding;

Average module, for calculating the average of carrier channel quality estimated value;

Modulation system determining unit, for determining modulation system based on count value and average;

Effective subcarrier determining unit, the modulation system based on definite, determines corresponding effective subcarrier sequence number;

Calculate sub-band gain coefficient unit, for carrier channel quality estimated value is converted to corresponding sub-band gain coefficient;

Calculate transmitting power coefficient elements, the modulation system based on definite and channel quality estimation average, the coefficient of calculating transmitting power.

22. blind Channel self-reacting devices according to claim 13, is characterized in that, described self adaptation sending module comprises modulation system selected cell, effective sub-carrier allocation unit, sub-band power distributing unit and transmitting power adjustment unit, wherein:

Modulation system selected cell, the modulation system of coming according to receiving end feedback, for data-mapping to corresponding constellation point;

Effectively sub-carrier allocation unit, feeds back according to receiving end effective subcarrier sequence number of coming, for effectively placing transmission data on subcarrier;

Sub-band power distributing unit, the sub-band decay gain coefficient of coming according to receiving end feedback, input sub-band signal is multiplied by the adjustment that corresponding gain coefficient is realized sub-band power;

Transmitting power adjustment unit, the transmitting power coefficient of coming according to receiving end feedback, guarantees be no more than under the prerequisite of maximum transmission power, and input signal is multiplied by the adjustment that transmitting power coefficient is realized transmitting power.

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